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16-Channel
Mixing Desk, Pt.2
In this second article on our new 16-Channel
Mixing Desk, we present the details of the
circuitry. The design is based largely on the
LM833 low noise dual op amp instead of the
5534 used in previous mixer designs.
By JOHN CLARKE & LEO SIMPSON
To be able to easily follow the circuit description, you will need to
refer to the description of the block
diagram, Fig.1, in the first article in
this series.
Now let's look at Fig.2 which is
the circuitry used on each of the 16
input channel boards. This is
depicted schematically along the
top of the block diagram, Fig.1.
The input signals come from pins
2 and 3 of a 3-pin XLR socket and
are fed via 33µF capacitors to the
inputs of ICla which is half of an
60
SILICON CHIP
LM833 dual low noise op amp.
Switch S1, a 3-pole 3-position
switch, switches the feedback network (Slc), the input attenuator
(Slb) and pin 2 of the input socket
for the balanced or unbalanced input condition (Sla).
Let's see how these conditions
come together. When switch S1 is
in setting 1, the input channel is
connected to suit balanced microphone outputs. In effect, ICla operates as an inverting amplifier
for signals from pin 2 of the XLR
socket and as a non-inverting amplifier for signals from pin 3 of the
XLR socket. In both cases, the
gain is determined by the two
resistors connected to the noninverting input, pin 2; ie, 10k0 and
lkO.
Gain for the inverting signal path
is 10k0/1k0 = 10 while gain for the
non-inverting signal is 100/lkO + 1
= 11. To compensate for this difference in path gain, a resistive attenuator is connected in series with
the signal to pin 3 of ICla. This attenuates the signal by a factor of
0.909. When multiplied by the nonFig.2 (opposite): this is the circuitry
for each of the 16 input channels.
IC1a & ICtb are input preamplifier
and buffer stages, IC2a a 3-band tone
control stage, IC2b the post fade
buffer and IC3a, D1, D2, Qt & Q2 the
headphone driver stage. IC4, IC3b &
IC5 provide overload indication.
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All the circuitry ,shown in Fig.2 is accommodated on a single PCB. There are 16 of these boards altogether - one for
each input channel. Note how the pots are mounted directly on the board to cut down on the internal wiring.
inverting gain of 11, it gives an
overall gain of 10, the same as for
the inverting gain. Hence, the circuit provides a perfectly balanced
input.
The input impedance is 1.BkO
which comprises the lkO input
resistor network in the inverting
signal path and the lkO input
divider in the non-inverting signal
path, with both shunted by lOkO
resistors to earth.
Line balanced
& unbalanced
In position 2 of switch S1, the input channel is connected to suit
balanced line inputs. The gain is
reduced by a factor of 10 by switching the 1.2k0 resistor across the
1OkO resistor between pins 1 and 2
of ICa (Slc). This provides a gain of
1.07 for the inverting signal path
and a gain of 2.07 for the non inverting signal path.
This disparity of gain is compensated for by the switched attenuator (Slb) in the non-inverting
signal path which reduces the
signal by a factor of 0.4825. When
multiplied by the non-inverting gain
of 2.07, the overall gain is 0.999
which is pretty close to the inverting gain of 1.07. Thus, by virtue of
This board accommodates all the effects send, effects return & foldback
circuitry shown in Fig.3 .. There are two such boards in the mixer. As before,
the pots are soldered directly to the PCB to simplify the wiring.
62
SILICON CHIP
the selection of feedback resistors
and the attenuator associated with
S1b, the circuit gives balanced input conditions for both line and
microphone sources.
In position 3 of switch S1, the input channel is connected for unbalanced inputs. The feedback and
input attenuator is the same as for
the balanced condition while the
difference is that pin 2 of the XLR
socket is grounded.
Pre-fade attenuator
Following the preamplifier stage
is a non-inverting op amp stage
comprising ICl b. This is labelled on
the circuit as an input buffer and
attenuator but most mixer operators would think of it as a "prefade attenuator". It enables the
signal levels to be set up on each input channel.
The gain of this stage is variable
from 100 to unity by means of VRl.
This stage is followed by IC2a
which is a 3-band Baxandall tone
control stage. VR2 provides the
bass control function and has no effect on frequencies above about
300Hz by virtue of the .015µF
capacitor shunting it. VR4 provides
the treble control function and has
little effect on frequencies below
about 2kHz, by virtue of the
.0015µF capacitor in series with the
pot wiper. VR3 provides a midchannel control by virtue of the .002 7µF
capacitor shunting the control and
the .012µF capacitor in series with
the pot wiper.
2.2
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RETURN
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CH2/CH4
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22k
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15k
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2.2k
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39pF
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100k
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Fig.3: the effects and foldback circuitry. IC6a & IC6b process the effects return signal while VR10 pans the
signal between the CH1/CH3 and CH2/CH4 buses. IC7a & IC8a are the effects sum and foldback sum
amplifiers, while IC7b and IC8b function as line amplifiers.
Headphone driver
The output of IC2a then feeds the
foldback send control VR5 and the
main fader control VR6 (bottom, left
of the diagram). Following VR6 is
the post fade buffer, IC2b, which
has a gain of 2. It feeds the effects
send control VR7, the pan control
VRB and the headphone monitor
stage, IC3a. This uses two transistors, Ql and QZ, to boost the output current to give sufficient drive
for any stereo headphones, high or
low impedance, that may be used.
Diodes Dl and D2, in conjunction
with the 330 emitter resistors, set
and stabilise the quiescent current
through Ql and QZ, to eliminate
crossover distortion.
Peak detector
As well as driving the headphone
monitor for each channel, the signal
from the emitters of Ql and Q2 also
feeds the peak detector which
monitors for signal overload.
IC4 and D3 function as a precision full wave rectifier. Its output is
fed to the inverting ( - ) input of
IC3b which functions as a corn-
parator with hysteresis set by the
220k0 feedback resistor from pin 7
to pin 5. The non-inverting ( +) input is fed from a lOkO trimpot. This
is adjusted to set the input signal
level above which the comparator
output, pin 7, goes low. When this
happens, the 7555 timer, IC5, is
triggered and turns on LED 21 for
around 24 milliseconds which is
quite long enough to be seen.
Thus even the briefest of overloads will be registered by the circuit. And because IC4 functions
as a full wave rectifier, peak
MARCH 1990
63
There's quite a lot of wiring inside the mixer, despite the fact that all rotary
pots are directly soldered to the boards. Most of this wiring is repetitive and
includes power supply connections, wiring to the 20 slider contr.ol~, and
input/output socket connections. Note that several boards are m1ssmg from
this photo.
overloads on both positive and
negative half cycles of the audio
waveform will be registered.
Power supply connections
Note that the positive and negative power supply connections for
ICl and ICZ are not shown on their
respective op amp symbols. They
were omitted for clarity. However,
these connections are shown on the
supply rails, on the lefthand centre
of the diagram, together with the
various bypass capacitors on the
rails.
Note the 4. 70 resistors in series
with both the positive and negative
supply rail inputs. These provide a
degree of supply decoupling, in conjunction with the 100µF bypass
capacitors. As well, the 4.70
resistors will act as fuses in the
unlikely event of a short on the
board. If this happened, only one input channel would be disabled
rather than possibly the whole mixer circuit.
Effects and foldback
The effects and foldback buffer
stages are shown in Fig.3. Note that
all of Fig.3 is accommodated on one
printed board, of which there are
64
SILICON CHIP
two. These stages are all based on
the LM833 dual low noise amplifier. They are all quite straightforward but you should look at the
block diagram, Fig.1, to understand
how they fit into the overall
scheme.
IC6a, the effects return circuit, is
a non-inverting unity gain buffer.
IC6b, the effects pan driver, is a
non-inverting amplifier with a gain
of 2.
IC7a and IC8a, the effects sum
and foldback sum amplifiers, are
inverting amplifiers, each with a
gain of 17. IC7b and IC8b, the effects and foldback line amplifiers,
are non-inverting amplifiers, each
with a gain of 7.8.
Note that the supply connections
to IC6 and IC8 have again been
omitted for clarity but they are
shown on the supply bus, at the
lower lefthand corner of the circuit.
Now let's have a look at the
2-page circuit diagram, Fig.4. This
is the circuitry for the 5-band
equalisers and LED VU monitors. It
also includes the master fader, the
sum and post fade amplifiers and
the headphone monitor stages.
All of Fig.4 is accommodated on
one printed circuit board, of which
there are four.
IC9a is shown as the "sum
amplifier" connected to the CHl
bus but remember that there are
four of these boards so it could
equally apply to the other three output channels. That is why it is
shown as 1 of 4. You will find this
note on several parts of the circuit
as a reminder that the same circuit
is on four boards.
IC9a is an inverting amplifier
with a gain of 34 (ie, 75k0/2.2k0). It
drives the master fader VR13 and
then the post fade amplifier IC9b
which is a non-inverting amplifier
with a gain of 4 (ie, 6.8k0/2.2k0 +
1).
Five band equaliser
IC10b, IC12 (a TL074 quad Fetinput op amp) and IC13 (a single
Fet-input op amp) make up the five
band equaliser. The five op amps in
IC12 and IC13 are all connected as
gyrators which are the equivalent
of inductors. The gyrators act
together with a series capacitor to
form broad tuned circuits centred
on 60Hz, 240Hz, lkHz, 3.5kHz and
lOkHz, and give boost and cut of
± 12dB.
Fig.4 (overleaf): the circuitry for the
5-band equalisers, output channel
monitors and LED VU meters. The VU
meter uses cascaded LM3915s (IC14
& IC15) and these are multiplexed
between dot and bar modes to display
peak and average signal levels.
. drasticallY
ust be
. ,,
Everything d -- stocks rn . of profit! ..
reduce
d irrespective
cleare
SH1
SH2
SH3
SH4
SH5
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SH14
SH15
SH16
SH17
SH18
SH19
SH20
SH21
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SH29
SH30
SH31
SH32
SH33
SH34
SH35
SH36
SH37
SH38
SH39
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SH41
SH42
SH43
7 400 Quad 2-lnput NANO Gate
10 for
7 403 Quad 2-lnput Open Drain
NANO Gate
10 for
7 404 Hex Inverter
10 for
7 408 Quad 2-lnput AND gate
10 for
7 41 0 Triple 3-lnput NANO gate
10 for
7 442 BCD to Decimal Decoder
10 for
7476 Dual J-K Flipflops with Preset
and Clear
10 for
7 41 56 Dual 2-Line to 4-Line
Decoder/Demultiplexer
10 for
7 4188 256-Bit PROM, Open Collector
Output
10 for
75136
10 for
75451 Dual Peripheral Driver Positive
AND Gate
10 for
7 4LS02 Quad 2-lnput NOR Gate
10 for
7 4LS04 Hex Inverter
10 for
74LS27 Triple 3-lnput NOR Gate
10 for
74LS51 Dual 2 Wide 2-lnput
AND/OR Invert Gate
10 for
7 4LS86 Quad 2-lnput Exclusive
OR Gate
10 for
7 4LS92 Low Power Divide By
12 Counter
10 for
7 4LS113 Dual J-K Flipflop with
Preset
10 for
7 4LS1 23 Dual Monostable
Multivibrator
10 for
74LS157 Quad 2-lnput Multiplexer
10 for
74LS161 Synch 4-Bit Binary
10 for
Counter
7 4LS 1 63 Synchronous 4-Bit Binary
10 for
Counter
7 4LS169 Synchronous 4-Bit Binary
10 for
Up/Down Counter
74LS175 Quad D Flipflop
10 for
74LS367 Hex Bus Driver With 3-State
10 for
Outputs
7 4S04 Ultra High Speed Hex
10 for
Inverter
7 4S112 Fast J-K Flipflop With Preset
and Clear
10 for
7 4S113 Fast J-K Flipflop With
10 for
Preset
7 4S188 Schottky, 256-Bit PROM,
10 for
Open Collector Output
7 4S241 Octal Buffers/Line Dr/Rx,
3-State Outputs
10 for
4020 CMOS 1 4-Bit Binary Counter
10 for
4049 CMOS Hex Inverter/Buffer
10 for
$
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$
2.00
2.00
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2.00
$ 2.00
BLACKTOWN
i ,~2, STORE
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SH44
SH45
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$
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$
$
2.50
2.00
2.00
2.00
$ 2.00
SH57
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SH60
$ 2.00
SH61
$ 2.00
SH62
$ 2.00
$ 2.00
$ 3.00
SH63
SH64
SH65
SH66
$ 2.50
$ 2.50
$ 3.00
$ 2.00
SH67
SH68
SH69
$2.00
SH70
$ 2.00
SH71
$ 2.00
SH72
$ 2.00
$ 3.00
$ 2.50
$ 2.00
$ 2.00
6800P IC-CMOS 8-Bit Microprocessor,
$ 1.50ea
1MHz
6821 IC-CMOS PIA Peripheral Interface
$ 1.50ea
Adaptor
2114P20 IC-MOS Static 4K RAM, 200ns
$ 0.80ea
$ 0.60ea
2114P30 IC-MOS Static 4K RAM, 300ns
ML8205 Dual Tone Ringer
10 for $ 1.00
TR1865 Disc Controller
$ 1.00ea
WD2795A Disc Controller
$ 1.00ea
10 for $ 1.00
8T26AN
HT1-201-5
10 for $ 1.00
$ 0.60ea
7805/LM309, T03 Voltage Regulator
$ 0.60ea
7815, T03 Voltage Regulator
AMPLE PARKING IN
ADJACENT STREETS
~
$ 2.00
SH73
SH74
SH75
SH76
SH77
SH78
SH79
SH80
SH81
SH82
SH83
SH84
SH85
SH86
Transistor, B0679 NPN, T0220
10 for
Transistor, B0680 PNP, T0220
10 for
IC, LM348 Op. Amplifier
10 for
Benelec Analog Multimeter 20kohm Per Volt,
With Case and Leads
IEC Panel Mounting Socket
IEC Switched & Fused Panel Mounting Plug
IEC Panel Plug with Filter & Fused
PSU Smoothing & Filter Unit
'Amiga' Computer Lead, Centronics to 25 'D'
Female
Hand Held Cassette Microphone-Stop/Start
5-pin 'DIN' In line Male Plug
10 for
5-pin 'DIN' In line Female Plug
10 for
5-pin 'DIN' 2-metre Lead, Male to Male,
Flat Cable
5-pin 'DIN' 5-metre Lead, Male to Male,
Flat Cable
5-pin DIN 9-metre Lead, Male to Male,
Flat Cable
IEC Mains Lead, Female In-Line to 2-Pin Plug
9-Way 'D' Female Plug Lead to 7-Pin
Fem.Ski. 2 Metres
Telephone 'Curly-Cord' with US Telephone
Plug
Transformer, 240V to 15V 200mA
Power Pack, 240VAC to 15VDC 500mA
('OZ' Adapt. Req)
50-Way 'D', Male & Female Connectors
1 2 Assorted Multi-turn Trimpots
SONY 3.5-inch Single Sided Disc Drive
400K
MITSUMI 3.5-inch Single Sided Disc Drive
360K
CROUZET Syncronous Motor, 240VAC
60 RPM
Motorized Paper Tape Assy. With 30VDC
Motor (OK for 1 2V)
Telecom 'Commander' Interface Boards,
Lots of 1 2V Relays
1 2-Digit Numeric Array Displays , MFTD by
NSD
Burroughs 12-Key Keypad in Case With
Lead
'SHURE' Precision Stylus Force Gauge
SUPER PACKS 1 OO's 1/4, 1/2 and 1 watt
resistors
SUPER PACKS 1 OO's Assorted Electro's
SUPER PACKS Approx. 30 Assorted
Potentiometers
SUPER PACKS 1 OO's Assorted Disc
Ceramic Caps
SUPER PACKS 100 Power Diodes,
100V 1.5A
Mini Relays, 5V DPDT Changeover
Mini Relays, 12V Single Pole Changeover
'SAFT' Sub 'C' Nicad Batteries, 1.5Ah
'SAFT' 'AA' Lithium Batteries, 3.6V,
Wire Ends
30 Assorted Resistor Networks, SIL & DIL
Philips Drive Motors, Dual Spindle, 15V DC
40 x 40mm
BNC Male to Female Leads, 3 Mir Length
41 64 DRAM, 1 50 n/sec
Mail Charges:
$15-$19.95 . . .. . . ..•.... $5
$20·$39.95 ... .. .•...... $7
$40·$69 .............. . $8
$70-$99 ..... . ........ $10
$100 and over ... ...... $15
Large or overweight articles sent
Skyroad Freight Forward,
Trading Hours:
Mon-Frl . . . . . . . 9am•5.30pm
Sat ........... 9.30am-1 pm
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6.50
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1.50
1.50
$ 2.75
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SH47
Benelec 20kohmlvolt
" '=t~·
IEC switched & fused
panel mounting plug
V.
'
H50
IEC panel plug with filter
& fuse
$ 1.25
$ 1.00
$ 1.95
· SH66
Sony 3.5-lnch single
sided disc drive (400K)
$ 9.50
$ 0.75pr
$ 4.00
$12.50
$15.00
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Mitsumi 3.5-lnch single
sided drive (360K)
$ 3.00
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$ 6.00
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Burroughs 12-key keypad
·-a-·· · ·
..
SH84
Philips dual spindle drive
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$ 3.50
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S~51
PSU smoothing & filter
unit
SHERIDAN ELECTRONICS
286 Cleveland Street, Surry Hills, NSW 2010
Ph: (02) 699 5922 or (02) 699 6912. Fax: (02) 698 3694
Mail orders to: PO Box 226, Strawberry Hills, NSW 2012
NOTE: Wo accept Bankcard, Mastercard and Visa. Howerer, we cannot
glre quantity discounts on credit card purchases or account orders,
Minimum tor account orders Is $15 excluslre of postage and packing.
All prices Include Salos Tax. All prices quoted are tor this month only
or unt/1 stocks last
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4.7k:S
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100k LIN
BOOST
4.7k
100k
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SUM AMPLIFIER ANO POST FADE AMPLIFIER
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22pF
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II
3
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BALANCED LINE
OUTPUT
~
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16VW+
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The power supply board provides ± 15V rails to power the op amps, together
with a + 5V supply to run all the LEDs in the VU meters. The three 3-terminal
regulators are bolted to small heatsinks.
For a detailed description of how
gyrator and equaliser circuits
work, see the articles on the Studio
Series 1/2-Octave 20-Band Stereo
Equaliser described in the August
and September 1989 issues.
Balanced output stage
The output of the 5-band equaliser, at pin 7 of op amp IC10b, feeds
the balanced output stage which
comprises op amps ICl la and
ICl 1b. This acts in the following
way: ICl 1b acts as a non-inverting
unity gain buffer which feeds pin 3
of the XLR output socket. It also
feeds IClla which is connected as
an inverting op amp with a gain of
68
SILICON CHIP
- 1. This gives a signal 180° out of
phase with the input. It drives pin 2
of the XLR socket. Both output
signals are coupled via 4 7µF
capacitors.
As well as driving the balanced
output stage, the output of IC10b
also drives the headphone monitor,
comprising IC10a, Q3, Q4, D4 and
D5. This stage is identical to those
used for each input channel, as
described above.
VU metering
The signal metering circuitry is
based on the National Semiconductor LM3915 dot/bar display driver.
Used by itself, the LM3915 is
capable of driving 10 light emitting
diodes to give a moving dot or
bargraph display with a signal
range of 30dB. To give a moving dot
display (ie, only one LED on at a
time), pin 9 is pulled below the V +
line at pin 3. To give a bargraph
display, pin 9 is connected directly
to pin 3.
In the circuit under discussion,
we have two LM3915s cascaded to
cover a signal range of 60dB. To
enable them to display a bargraph
for the average signal level and a
dot (single LED) for the peak signal
level, the LM3915s are switched
rapidly between the two modes and .
the signal fed to their inputs (pin 5)
is switched at the same rate.
This switching, or multiplexing,
is accomplished by a 4066 4-way
analog switch, IC21. Its four switch
sections are opened and closed by
the square wave signal generated
by IC20, a 7555 timer. This is connected to give a 50% duty cycle
square wave by charging and
discharging the .0lµF capacitor at
pin 6 via the 100k0 resistor connected from pin 3. The frequency of
this waveform is about 450Hz.
Signal detection
The signal from the output of the
equaliser (pin 7, IC10b) is fed to
IC16, a non-inverting amplifier with
gain adjustable by trimpot TRIM2.
IC16's output is fed to ICl 7 which is
Below: four of these 5-band equaliser
plus LED VU meter boards are used ·
in the mixer (one for each output
channel). This board carries all of the
circuitry shown in Fig.4.
OUT
2500
25VW
2500
25VW
240VAC
+ 2500
25VW
+
-
-
1
25VW
-
1
25VW
+
+
-
.,.
-
2500
25VW
OUT
E •
+15V
-1 5V
FO"-'-UT_ _ _ _ _ ___,,_ +5V
nh,
CASE
012-015
4x1N4002
2200
16VW
+ 2200
_ 16VW
+
-
1
16VW
.,.
Fig.5: the power supply uses a large toroidal transformer with two secondary windings. A 30V
centre-tapped secondary feeds bridge rectifier D8-D11 and this drives positive and negative
3-terminal regulators to give ± 15V supply rails. The other secondary feeds bridge rectifer
D12-D15 and this drives a 7805 3-terminal regulator to give a + 5V supply.
another fullwave precision rectifier
(ie, it responds to both the positive
and negative half cycles of the
waveform and it has very good
linearity). Its output is fed via a
68k0 resistor to a lµF filter capacitor to give a DC voltage which is
proportional to the average signal
level over any time period of approximately 68 milliseconds. This
DC voltage is the one used to produce the bargraph display.
To obtain the peak signal level at
any time, the rectified signal from
the cathode of D6 is fed to IC18
which functions as a sample and
hold circuit. The l0µF capacitor,
combined with the 36k0 and 62k0
resistors, has a time constant of one
second so that even brief signal
peaks are "caught" and displayed.
Switching between
display modes
To understand how the switching
between the two modes occurs,
essentially all you need to know is
that each 4066 analog switch is
switched on when its control pin is
taken high. Hence, when the output
of IC20 is high, switches IC21a,
IC21b and IC21c are on and IC2ld,
is off. This places the LM3915s in
bargraph mode and the averaged
signal from the lµF capacitor on
pin 8 of IC21c is fed to pin 5 of IC15,
the LM3915 displaying the top 30dB
of signal range.
The same DC signal is fed to
ICl 9, an op amp with a gain of 31
( + 30dB) to drive pin 5 of IC14, the
LM3915 displaying the lower 30dB
of signal range.
When the output of IC20 is low,
switches IC2la, IC21b and IC21c
are all off (ie, non-conducting) while
IC21d is on. This feeds the peak DC
signal through to the LM3915s,
which are now in dot mode.
Power supply
Fig.5 shows the power supply
which has more in common with a
power amplifier than a small signal
device. It uses a hefty toroidal
power transformer and a substantial amount of filter capacitance.
A centre-tapped 30V (15V +
15V) secondary feeds a bridge rectifier consisting of diodes DB to Dl 1.
The positive and negative outputs
of the bridge rectifier each feed two
2500µF filter capacitors. The
resulting positive and negative DC
rails feed 3-terminal regulators to
obtain balanced supply rails of
± 15V.
A separate regulated 5V supply
rail is required to run all the LEDs
of the four dot/bargraph displays.
This is obtained from an BV winding on the transformer which
feeds a bridge rectifier consisting
of diodes D12 to D15. The DC output
is filtered by two 2200µF capacitors which then feed a 7805
3-terminal regulator.
RF breakthrough
To minimise RF breakthrough in
all parts of the circuitry, you will
notice that many of the feedback
resistors of the op amps are
shunted with capacitors ranging
between 39pF and 220pF. This is to
roll off the response a hove the
audio range. You will also note a
number of rolloff networks involving lkO series stopper resistors and
150pF shunt capacitors. Again,
these are there to roll off any supersonic and RF signals so that they do
not break through into audibility.
This is most important for a professional mixer design which is
often used in proximity to vicious
electrical noise sources.
Next month we will describe the
construction of the printed circuit
board modules and, if space permits, describe the wiring of the mixer control panel.
~
MARCH 1990
69
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