This is only a preview of the May 1994 issue of Silicon Chip. You can view 31 of the 96 pages in the full issue, including the advertisments. For full access, purchase the issue for $10.00 or subscribe for access to the latest issues. Articles in this series:
Items relevant to "Fast Charger For Nicad Batteries":
Items relevant to "Two Simple Servo Driver Circuits":
Items relevant to "An Induction Balance Metal Locator":
Items relevant to "Dual Electronic Dice":
Items relevant to "Multi-Channel Infrared Remote Control":
Items relevant to "Computer Bits":
Articles in this series:
Articles in this series:
|
Vol.7, No.5; May 1994
FEATURES
4 Electronic Engine Management, Pt.8 by Julian Edgar
Books & journals
THIS FAST NICAD CHARGER
will charge two or four cells
in rapid time. It’s built around
a special IC & automatically
throttles back when the cells are
fully charged – see page 18.
8 The Fingerscan ID System by Leo Simpson
Just plunk your digit on the window
14 Passive Rebroadcasting For TV Signals by Mike Pinfold
One way of overcoming TV reception problems
PROJECTS TO BUILD
18 Fast Charger For Nicad Batteries by Darren Yates
It charges four “AA” cells in 50 minutes
24 Two Simple Servo Driver Circuits by Nenad Stojadinovic
Build them for servo testing or direct control
34 An Induction Balance Metal Locator by John Clarke
Use it to find coins, watches & other valuables
54 Build A Dual Electronic Dice by Darren Yates
BASED ON A SINGLE IC, this
simple unit can be used to test
servos or used to control a servo
in applications where a radio
link is not required. We show you
how to build it starting page 24.
VERTICAL POLARISATION
HIGH SIGNAL AREA
ANY POLARISATION
Easy-to-build circuit has auto switch-off
64 Multi-Channel Infrared Remote Control by Brian Roberts
60dB PATH
LOSS
PASSIVE
RE-BROADCAST
SYSTEM
LOW SIGNAL AREA
Add remote control to your tuner, tape deck or other appliances
SPECIAL COLUMNS
58 Serviceman’s Log by the TV Serviceman
Always look on the grim side
DO YOU HAVE A PROBLEM with
weak TV reception. Our article
on page 14 shows you how to
deliver a TV signal from a remote
antenna up to 1km away.
74 Computer Bits by Darren Yates
What’s your free disc space?
80 Vintage Radio by John Hill
Trash or treasure – recognising the good stuff
86 Amateur Radio by Garry Cratt
The Rhombic: a high gain wire antenna for HF
88 Remote Control by Bob Young
How to service servos & winches, Pt.2
DEPARTMENTS
2
3
32
53
70
79
Publisher’s Letter
Mailbag
Circuit Notebook
Order Form
Product Showcase
Bookshelf
84
91
93
94
96
Back Issues
Ask Silicon Chip
Notes & Errata
Market Centre
Advertising Index
ADD THE CONVENIENCE of
remote control to your tuner, tape
deck or to some other appliance
with this easy-to-build project.
A separate low-cost transmitter
is used to program a universal
remote control. Details page 64.
Cover design: Marque Crozman
May 1994 1
Publisher & Editor-in-Chief
Leo Simpson, B.Bus.
Editor
Greg Swain, B.Sc.(Hons.)
Technical Staff
John Clarke, B.E.(Elec.)
Robert Flynn
Darren Yates, B.Sc.
Reader Services
Ann Jenkinson
Sharon Macdonald
Advertising Enquiries
Leo Simpson
Phone (02) 979 5644
Mobile phone (018) 28 5532
Regular Contributors
Brendan Akhurst
Garry Cratt, VK2YBX
Marque Crozman, VK2ZLZ
John Hill
Jim Lawler, MTETIA
Bryan Maher, M.E., B.Sc.
Philip Watson, MIREE, VK2ZPW
Jim Yalden, VK2YGY
Bob Young
Photography
Stuart Bryce
SILICON CHIP is published 12 times
a year by Silicon Chip Publications
Pty Ltd. A.C.N. 003 205 490. All
material copyright ©. No part of
this publication may be reproduced
without the written consent of the
publisher.
Printing: Macquarie Print, Dubbo,
NSW.
Distribution: Network Distribution
Company.
Subscription rates: $49 per year
in Australia. For overseas rates, see
the subscription page in this issue.
Editorial & advertising offices:
Unit 34, 1-3 Jubilee Avenue, Warrie
wood, NSW 2102. Postal address:
PO Box 139, Collaroy Beach, NSW
2097. Phone (02) 979 5644. Fax
(02) 979 6503.
PUBLISHER'S LETTER
We must reject any move
to reduce our mains
voltage to 230V.
You may recall that month I discussed the
move to reduce our mains voltage from a
nominal 240V to 230VAC. The main advan
tage to Australia is supposed to “improve the
opportunities for the electrical equipment
we produce, opening up the world to our
industry”. I pointed out that Australians
would pay a very high price for this in terms
of higher electricity distribution costs and so on.
Well this month, I felt I should return to the topic in case some people thought
that it was an “April Fool” story or that it would not affect them directly. It
certainly will. Consider, for example, that any heating appliance which you
presently have will not get as hot on 230 volts and the difference will be quite
noticeable. Your stove hotplates will be noticeably less hot and there will be
a consequent increase in cooking times. The same applies to your microwave
oven, convection oven, even your toaster, electric iron and so on. All of these
heating appliances will either take longer to come up to a selected temperature
or in the case of appliances which aren’t thermostatically controlled, they just
won’t get as hot.
Nor will your lights be as bright and you will find the need to replace all light
bulbs with new ones rated for 230V AC if you want the same brilliance as you
had before. That is bad enough but if you are using 12V halogen lamps which
need to run at close to their rated voltage to work properly, then they will be
noticeably dimmer - they will no longer sparkle at all. Again, the only solution
may be to change all halogen lamps or worse, change the 12V transformers.
If you have fluorescent lights, they will take noticeably longer to start, particularly on cold mornings - so you’ll have more of that annoying flick-flick-flickering each time you turn them on. And when they do come on, they won’t be
as bright either.
Nor will your refrigerator and freezer work as well and they will cost more
to run.
Still not convinced? What about that old colour TV you’ve had for many years?
It’s been working fine and you don’t have any real reason to update at this stage.
Well, when you run it from 230 volts AC, you will no doubt find that its picture
will shrink and that will certainly take the gloss off its performance. New TV
sets will not be affected at all by this change because their power supplies can
cope with a large range of mains voltages but people who can’t afford to update
their equipment are going to be disadvantaged.
No, the more I think about this proposal to reduce our mains voltage to 230
volts AC, the more I think it is harebrained. If you agree, don’t just nod your
head and turn the page. Either write to us or write to the Minister for Energy
in your state. It’s likely they haven’t heard of the proposal yet. Get them to nip
it in the bud!
Leo Simpson
ISSN 1030-2662
WARNING!
SILICON CHIP magazine regularly describes projects which employ a mains power supply or produce high voltage. All such projects should
be considered dangerous or even lethal if not used safely. Readers are warned that high voltage wiring should be carried out according to the
instructions in the articles. When working on these projects use extreme care to ensure that you do not accidentally come into contact with
mains AC voltages or high voltage DC. If you are not confident about working with projects employing mains voltages or other high voltages,
you are advised not to attempt work on them. Silicon Chip Publications Pty Ltd disclaims any liability for damages should anyone be killed
or injured while working on a project or circuit described in any issue of SILICON CHIP magazine. Devices or circuits described in SILICON
CHIP may be covered by patents. SILICON CHIP disclaims any liability for the infringement of such patents by the manufacturing or selling of
any such equipment. SILICON CHIP also disclaims any liability for projects which are used in such a way as to infringe relevant government
regulations and by-laws.
Advertisers are warned that they are responsible for the content of all advertisements and that they must conform to the Trade Practices Act
1974 or as subsequently amended and to any governmental regulations which are applicable.
2 Silicon Chip
MAILBAG
Solar regulator
I read with interest the article on the
solar panel regulator in the January
1994 issue. This is a step in the right
direction and I am sure that it will
contribute to greater use of solar energy
in the future.
One small point disturbs me, however. At the end of the article, instructions are given to adjust for a battery
voltage of 13.8V. Presumably this
regulator will be used with lead-acid
batteries of the automotive type, in
which case the battery will never be
charged to full capacity.
Both car and battery manufacturers
recommend that regulators be set at a
minimum of 14.2V and not to exceed
14.5V. For long battery life and minimum water top-up requirements, it
may be desirable to revert to 13.8V
after a period of moderate gas
sing
and this would lead to a slightly more
complex design for the regulator.
Maybe there will be another article
on the subject?
M. Findlay,
Badgerys Creek, NSW.
Information on
guitar amplifiers
With reference to the “IF generator is
nifty” letter from L.T. from Eaglehawk,
Victoria (Ask SC column, December
1993), he (?) asked for a course on antique musical instruments, specifically
guitar amplifiers.
In 1989, I purchased a paperback
book from McGill’s bookshop in Melbourne, called “The Tube Amp Book
II” by R. Aspen Pittman. As far as I can
tell, it is published by Groove Tubes,
13994 Simshaw Avenue, Sylmar, California 91342, USA. My edition was
published in 1988.
There are 400 pages to this book and
it has 32 pages of photos of various
guitar amplifiers and a few other items.
There is a considerable rundown on
the history and technical details of
many amplifiers, including 10 pages
listing valve types used in various
makes and models.
There is a small cross reference
list of US/industrial/European type
equivalents, a list of Groove Tube com-
panies and instrument manufacturers
(worldwide list) and most importantly,
277 pages of circuits of all the big
name guitar amplifiers. If this book is
still available it should be just what
is needed.
As a regular reader, let me compliment you on your excellent magazine. I
am a collector of early radio equipment
and a technician by trade, so I read the
Vintage Radio and Serviceman’s Log
columns first, followed by the rest of
the magazine articles.
I am a member of the Historical
Radio Society of Australia and a local
vintage radio club (The North East
Vintage Radio Club). About 17 of our
(local) members went across to see
John Hill’s museum in Maryborough
a few weeks ago. How I wish I had
as many of my radios restored and
somewhere to display them like that!
E. Irvine,
Benalla, Vic.
Adjustable compressor wanted
I was interested to see a section
in a sound mixing instruction book
devoted to compressors and limiters
which are used in the music industry.
They had adjustable attack and delay,
adjustable levels, and even adjustable
“knee” or cutoff (or percentage compression). I am told that these cost
$400 yet they are ideal for setting up
automatic sound control of individual music instruments and for public
address.
What strikes me is that we have endless amplifier kits yet I know of no kit
that resembles this professional music
industry device. I see big advantages
in its use in pulpit microphone control
and tried to use an opto-coupled FET
in a home brew circuit but it needs
heaps of redesigning.
May I suggest this type of compressor for a project of in SILICON CHIP?
Glen Host,
Doubleview, WA.
Easier calibration for the
Digital Tachometer
I recently built the Digital Tachometer from the August 1991 issue and
it works well.
SILICON CHIP,
PO Box 139,
Collaroy, NSW 2097.
As I only had a 6V AC plugpack, I
reduced the 4.7kΩ calibration resistor
to 2.7kΩ and wired it permanently to
a chassis mount socket on the inside
of the case.
When I adjusted the 50kΩ pot (VR1)
to calibrate the unit, I found it difficult
to obtain an exact 1000 rpm because
of the “touchiness” of the adjuster.
Here I might mention that I am using
a 56kΩ resistor for RX to suit a 6-cylinder motor.
The nearest adjustment which I
could obtain was near the centre point
of the 50kΩ pot and this subsequently
measured approximately 35kΩ.
The 35kΩ and 56kΩ resistances
added up to 81kΩ and so I decided to
substitute a 75kΩ resistor for RX and
use a 10-turn 10kΩ trimpot for VR1
to make the adjustment much less
critical. This trimpot was glued to the
edge of the PC board using two-part
epoxy and wired to VR1’s pads on the
PC board via flying leads.
Chris Potter,
Kilsyth, Vic.
Serviceman column is useful
One of the most enjoyable features
are the cartoons that appear in the
Serviceman column every month.
They certainly put some fun back
into what can be a dry and serious
profession. Additionally, I have used
the information in this column to
help assist me in repairing TVs and
videos – even one annoying fault in
my mother’s video!
After having repaired several valve
radios by reading the Vintage Radio
column, I wonder how easy the current
generation of electronic equipment
will be to service in the next 20 years.
About three months ago, I helped
one of our apprentices repair an elderly colour TV that he found on the
footpath during a council cleanup.
The manufacturing date stamp was
for 1975! After repairing several minor
faults, it was as good as ever!
Finally, I am eagerly awaiting the
completion of the extra add-on for the
colour video fader described last year.
Mark Allen,
Artarmon, NSW.
May 1994 3
Electronic
Engine
Management
Pt.8: Books & Journals – by Julian Edgar
Finding appropriate texts and
journals which deal with electronic
engine management is difficult. Most
material written on electronics in cars
is either too simple (being directed at
apprentice mechanics) or too generalised to be of help when dealing with
a specific car.
However, there are some references
which are useful. Buying the books
outright can be expensive but TAFE
libraries will often respond to requests
to buy specific books if they lack material in that area and if the college
teaches automotive subjects. TAFE
libraries are the best source of material
of this whole subject area and they also
allow free public membership.
Generalised texts
There are several books that give a
good general treatment of electronics
Gregory’s produce very useful references on various cars. In the foreground is
a standard Gregory’s workshop manual, which has engine management fault
diagnosis material in it. The background book (EFI & Engine Management)
contains material on the engine management & EFI systems in all Australian
cars from 1980-1990.
4 Silicon Chip
in automotive applications. “Understanding Automo
tive Electronics”,
“Automotive Computers and Control
Systems” and “Automotive Electronic
Systems” (full details of the books
cited are at the end of this feature) are
just three examples. The first two are
published in the United States while
the latter book is British.
All three books give an overview
of both analog and digital automotive
systems. The first book is probably
more useful from purely an electronics perspective, with the second
book also examining aspects such as
diagnostics and the testing of systems
in American vehicles. The latter book
provides probably the best of both
worlds!
A very different type of book – but
still useful – is pub
lished by the
Australian Government for use by
apprentices. Called “Engine Petrol
Injection”, it covers all aspects of elec
tronic fuel injection (EFI) and is aimed
at mechanics. Electronic engine management (which incorporates both fuel
and ignition control) is not covered,
however. Very clear diagrams are used
throughout the book, especially on the
mechanical aspects of EFI.
The book is available from Commonwealth Government bookshops
for about $15 and is a bargain.
Bosch
The next step is to look at material
Above: these three generalised texts all provide excellent
background material on the subject of electronic engine
management & automotive computers.
produced by the original manufacturers of the equipment. Bosch invented
electronic fuel injection and engine
management, and has published a
series of books and booklets dealing
with the topic. Their material is generally excellent.
The Bosch “Automotive Handbook”
is the Bible among car designers and
serious amateur modifiers. Pocket size,
it packs an incredible amount of information into its 700 pages. It’s written
in a sort of technical shorthand, with
each paragraph containing many
points. The actual sections dealing
with electronics in car applications
form a relatively small component
of the book but it is worth buying for
these sections alone. It is available
from the Society of Automotive Engineers in Canberra (02 449 6551) and
costs around $45.
Also produced by Bosch is a series of
booklets dealing specifically with each
of that company’s engine management
and fuel injection systems. Booklets
are available on L-Jetronic, Motronic,
Engine Electronics, and so on. Each
This book provides a good introduction to EFI, with
very clear diagrams used throughout. It is pitched at the
apprentice mechanic level & is excellent for beginners.
booklet is about 40 pages long. They
are very expensive but most TAFE
colleges which deal in automotive
electronics stock the booklets in their
libraries.
Specific car systems
When you require information on
specific car systems there are two
sources. The first are books which
have been written to cover a variety
of manufacturers’ systems. Gregory’s
have published “EFI and Engine
Management”, a good book which
covers most of the common cars sold
in Australia in the period 1980-1990.
It costs about $60.
The information includes such material as accessing and reading fault
codes, wiring diagrams, sensor types,
and so on. Also provided is a 40-page
summary of how EFI works, the common inputs and outputs, and how
to test sensors. In all, it provides an
excellent summary of the procedures
used for maintenance and simple
fault-finding.
Gregorys’ individual car workshop
manuals also contain this material on
a specific-car basis but in an abbreviated form.
Workshop manuals
The other way of obtaining material
on a specific car is to use the manufacturer-produced workshop manual.
These vary sub
stantially in quality
and depth, both from manufacturer
to manufacturer and from model to
model.
The best manuals will devote a
whole volume to engine management.
This generally includes a discussion
on how each of the input sensors
works, their response curves, and
so on. Pin-outs of the ECM will be
included and typical voltages and/or
waveforms specified.
Not all manufacturers go to this trouble though, with some giving just fault
codes and simple testing procedures.
Often, the first model to introduce a
new management system will have
an extensive discussion of it in the
workshop manual, with subsequent
models having only a brief coverage.
May 1994 5
The Bosch Automotive Handbook has an incredible
amount of information packed into it – some of which is
on car electronics. It’s worth buying for this aspect alone.
Examples of good manufacturer-developed workshop manuals include
the Holden VL Commodore, Mazda
RX-7 twin turbo, Subaru Liberty and
Ford L-Jetronic Falcon. The manuals
are available directly from the manu-
More specific information on the various Bosch systems is
available in their Technical Instruction booklets. They’re
expensive to buy, though.
facturer – though some sweet-talking
may be required before they will sell
them to a private individual – and from
TAFE libraries. The cost is usually
quite reasonable – the Subaru Liberty
manual, for example, comprises six
Factory workshop manuals often provide an in-depth analysis of the engine
management system used in that model. The Subaru Liberty manual, for
example, comprises six volumes, one of which is devoted to engine management.
6 Silicon Chip
volumes, each up to 300 pages long,
and costs $140. This covers the whole
of the car of course – not just the engine
management.
Modifications
Books on the topic of fuel injection
modification are very rare and those
which are available also become
quickly dated. There don’t seem the be
any books which cover programmable
injection, for example.
“Tuning New Generation Engines
for Power And Economy” (about $45)
covers all aspects of modern engine
modification – including a chapter
on fuel injection. This book is already
dated (it was first published in 1988)
in that it deals solely with fooling the
computer inputs in order to change
the outputs. Fitting high-flow injectors and then using an air-bypass
around the vane airflow meter so that
over-fuelling at low loads doesn’t
occur is discussed in some detail, for
example. However, some good points
are made about fuel flow, injector capability, and so on.
Bosch Fuel Injection and Engine
Management is an American book
which gives an excellent overview of
both mechanical and electronic injection and management systems. Much of its material is drawn straight from
the Bosch manuals and is therefore clear and accurate. A
chapter on modification is included. This book is a good
buy at about $60.
Also available are some books which cover modifications to specific fuel injection systems. Published in the
United States, some are relevant to use when Australian
cars use the same engine management systems. Since both
Ford and Holden are US-owned, books dealing with EEC
(Ford) and GM-Delco (Holden) systems are useful. An
example is How to Tune and Modify Ford Fuel Injection,
which covers the EEC-IV system.
Journals
Various US, British and Australian engineering periodicals cover electronics in cars. The Australian journal
“The Automotive Engineer” (published by the Australian
Society of Automotive Engineers) is really aimed more
at mechanics than engineers and tends to cover material
at about the same level as the well-known “Gregory’s
manuals. It provides coverage each time a new car is
released, concentrating mainly on the technical aspects
of the vehicle and its engine.
The Society of Automotive Engineers in the United
States also publishes material on electronics in cars. The
best way to obtain this is in the collected papers which
are published occasionally and which deal with one
topic. “Engine Management and Driveline Controls”, for
example, was published in 1989 and has a collection of
engineering papers dealing with these topics.
Other collections are also available. Once again, TAFE
libraries sometimes carry these publications.
This early Ford manual gives good background
information & is applicable to all L-Jetronic EFI cars.
Bibliography
Here is a list of books containing good material on
elec
tronic engine management. There must be many
others and I would welcome feedback from any reader
who knows of other relevant references – especially in
the area of modification.
(1). Australian Automotive Industry Training Council,
Engine Petrol Injection, Australian Government Publishing Service; Basic Training Manual 17-8, 1992.
(2). Bell, A. G., Tuning New Generation Engines for
Power and Economy; Haynes Publishing, 1988.
(3). Bosch, Automotive Handbook; Robert Bosch
GmbH, 1986
(4). Bosch, Technical Instruction – L-Jetronic; Robert
Bosch GmbH, 198?
(5). Bosch, Technical Instruction – Motronic; Robert
Bosch GmbH, 1983.
(6). EFI and Engine Management; Gregory’s Scientific
Publications, 1990.
(7). Mellard, T., Automotive Electronic Systems; Heinmann Newnes, 1987.
(8). Probst, C. O., Bosch Fuel Injection and Engine
Management; Robert Bentley, 1989.
(9). Ribbens, W. & Mansour, N., Understanding Automotive Electronics; Texas Instruments, 1984.
(10). Watson, B., How To Tune and Modify For Fuel
Injection; Motorbooks International, 1992.
(11). Weathes, T. & Hunter, C., Automotive Computers
SC
and Control Systems; Prentice-Hall, 1984.
This is one of the few books available which looks at
modifications to EFI systems. It is now getting a little
dated but is still useful.
May 1994 7
Fast & easy proof-positive identification
The Fingerscan
Personal ID System
Fujitsu Australia has announced a marketing
agreement with Bio Recognition Systems for the
Fingerscan personal identification system which
was designed & developed in Australia. Fujitsu
will market the system world-wide.
By LEO SIMPSON
Many readers will recall our report
on the Fingerscan system which was
featured in the May 1990 issue of
SILICON CHIP. It has now been refined
and repackaged and the software
rewritten for Windows applications.
The Fingerscan system has wide
application in small or large businesses, anywhere where personal
security is required, whether it is for
entry into a carpark or building, or for
access to a computer system or to a
restricted area.
For those who are not familiar with
the Fingerscan system, we shall provide an updated description. Finger
scan is an electronic finger scanning
device which records and stores your
finger image in computer memory.
The photos accompanying this article
show it used in two applications, one
for access to a computer instead of the
normal password system
and the other, Fujitsu’s
immediate application as
a time and attendance
clock for retail stores and
factories.
As shown in the photos,
with both units you just
place your finger over a
small plastic window. The
unit then scans your finger
and shortly after you are
either identified or asked
to try again. According to
the developers, Bio Recognition Systems, the Finger
scan “is based on digital
holography and involves
an electro-optical scanner
about the size of a thumb
print which reads three-dimensional data from the
finger such as skin undula
Originally used in our May 1990 issue, this
tions, ridges and valleys,
photo shows Fingerscan being used instead of
reflections and other living
the more traditional password to control access
characteristics.
to a computer system. It makes unauthorised
“One of the living characaccess virtually impossible.
8 Silicon Chip
teristics is the blood flow pattern within the finger. Building on these various
three-dimen
s ional data, a unique
personal pattern is built up. This pattern is not a fingerprint and does not
rely on print data. A fingerprint is a
two-dimensional pattern which relies
upon certain key minutiae to identify
one print from another.
The heart of the system is a CCD
(charge coupled camera) which takes
three scans of the finger. For each separate scan, the finger is lit by different
coloured LEDs: red for the first, orange
for the second and green for the third.
Each of the LEDs illuminates the finger
from a slightly different angle so that
the image detail recorded by the CCD
camera is not the same.
The analog picture information
from the CCD camera is converted
into digital data and processed in
a module which employs a 68000
microprocessor and a large custom
gate array. The data is compressed
and stored as a 1242 byte template
file. By comparison, a finger image
file takes up about 150 kilobytes. A
template file can only be compared
with a newly presented finger image
to provide identification.
This has three results which are
important for privacy implications:
(1) a finger image cannot be recreated from a template file;
(2) A template cannot be compared
with any other template and therefore
the system can only be used with
the cooperation of users who must
put their live finger on the scanner
in order to be matched with a stored
template; and
(3) A person has a choice of 10
fingers to use, none of which is the
same.
Therefore, a person could use a
different finger for different applications where Fingerscan was in use.
This is the new version of Fingerscan, developed in Australia as a Time &
Attendance clock for Fujitsu. It uses a CCD camera to create and store a
3-dimensional record of a person’s finger.
For example, a person could use the
index finger for time and attendance
at their place of work, the left thumb
for a bank account and the ring finger for computer access. A person is
therefore recognis
able only within
a closed system and only if they so
choose.
Users are enrolled in a Fingerscan
system in about 25 sec
onds. Each
subsequent positive identifications
takes less than half a second. The
false acceptance rate is claimed to be
.0001% (ie, one in a million), while
the false rejection rate is less than 1%.
The Fingerscan unit comes in various memory sizes. The base model
has 512Kb of memory which can be
increased up to 2Mb, allowing for
storage of up to 1200 finger records
as well as a transaction log. The unit
can also retrieve finger records when
networked from a remote PC or other
host computer. There is therefore no
real limit to the number of users that
can be registered on a system.
The keyboard has 16 keys which
includes six function keys that can be
programmed to suit the application.
The readout is a backlit 2-line by 16character alphanumeric display.
Fingerscan comes with a variety of
interfaces. It has four TTL alarm inputs
and four TTL outputs, RS232 or RS485
serial outputs and an optional smart
card interface. It can also operate a
doorlock using the built-in doorlock
relay driver.
Mr John Parselle, managing director
of Bio Recognition Systems, made the
following comments on the agreement
with Fujitsu: “Our new design came
about because we had a major client
with an offshore subsidiary who required a much more responsive bio
metric device than our existing model.
We successfully applied for a Federal
Government Discretionary Grant to redesign Fingerscan to meet this export
opportunity. The initial order is for 250
units but we have great expectations
of increasing this to several thousand
in the short term. We subsequently
designed the second Fingerscan unit
specifically as a Time and Attendance
clock for Fujitsu Australia and signed
the marketing agreement with Fujitsu
Australia to jointly market both new
Fingerscan products.
For further information on the
Fingerscan ID system contact Fujitsu
Australia Ltd, 376 Lane Cove Road,
North Ryde, NSW 2113. Phone (02)
SC
887 9222.
May 1994 9
SILICON
CHIP
If you are seeing a blank page here, it is
more than likely that it contained advertising
which is now out of date and the advertiser
has requested that the page be removed to
prevent misunderstandings.
Please feel free to visit the advertiser’s website:
dicksmith.com.au
SILICON
CHIP
If you are seeing a blank page here, it is
more than likely that it contained advertising
which is now out of date and the advertiser
has requested that the page be removed to
prevent misunderstandings.
Please feel free to visit the advertiser’s website:
dicksmith.com.au
SILICON
CHIP
If you are seeing a blank page here, it is
more than likely that it contained advertising
which is now out of date and the advertiser
has requested that the page be removed to
prevent misunderstandings.
Please feel free to visit the advertiser’s website:
dicksmith.com.au
SILICON
CHIP
If you are seeing a blank page here, it is
more than likely that it contained advertising
which is now out of date and the advertiser
has requested that the page be removed to
prevent misunderstandings.
Please feel free to visit the advertiser’s website:
dicksmith.com.au
Passive
rebroadcasting
for TV signals
Do you have a problem with weak TV
reception & no possibility of “line of sight”
to the TV transmitter. If so, then this article
on delivering a TV signal over a distance of
up to 1km will be of interest.
By MIKE PINFOLD
A letter featured on page 93 of the
August 1993 issue prompted me to
put pen to paper. It referred to the
possibility of passively re-broadcasting TV signals picked up in a high
signal strength area by beaming them
down into a low signal area. This was
to be done by coupling two television
antennas back to back with a length of
low loss coaxial cable.
At first thought, the idea seems a
good one but with simple propagation
theory and antenna maths it can be
demonstrated that it has only limited
potential. The letter also mentioned
the use of a masthead amplifier and the
matching of a long feedline from the
high signal area down some distance
to the TV set. But first, let’s address the
problem of passive re-transmission of
TV signals.
There are a number of mathematical
formulas that enable one to calculate
field strength at a distance from a
transmitter. The first of these is used
to calculate the power density “P” at
a point “r” metres from an isotropic
radiator:
P = Pt/4πr2
where
P = received power in watts/square
metre;
Pt = transmitted power in watts; and
r = distance in metres between transmitter and the reference point.
This formula shows the in14 Silicon Chip
This photo shows the author’s original open wire feeder system in use with a
vertically polarised VHF antenna in a remote part of New Zealand.
verse-square nature of radio waves.
The energy level reduces in proportion
to the square of the distance. Note that
the frequency of the signal does not
enter this equation. The electric field
intensity “E” of a radio signal “r” metres from a point of “P” watts is given
by the equation:
E = √(30Pt)/r
where
E = the intensity in volts per metre;
Pt = the transmit power in watts; and
r = the distance in metres.
The power density of a signal and
the electric field intensity are related
by the equation:
Pr = E2/120π
where
Pr = received power density in watts
per metre squared;
E = intensity in volts per metre; and
120π = the resistance of free space.
The above formulas are for theoretical signal strengths between isotropic
sources in free space. However, there
are other external influences that may
times 20dB is 100 times. Thus,
the formula to include gain
arrays is:
HIGH SIGNAL AREA
Pr = 1.64Pt/4πr2
ANY POLARISATION
Antennas have a performance
factor known as “antenna aper
ture” and it determines how
60dB PATH
LOSS
much of that potential signal the
PASSIVE
antenna extracts from free space.
RE-BROADCAST
LOW SIGNAL AREA
The larger the receiving area,
SYSTEM
the more power is intercepted.
Aperture is determined by the
following equation:
A = λ/4π
For a gain array with a gain
of “G” times over isotropic, the
equation is:
Fig.1: this diagram shows the general concept of passive rebroadcasting as outlined
in the article. The hilltop antenna picks up a strong signal which is re-radiated
A = Gλ/4π
downhill by another antenna to the receiving antenna at the bottom of
where
the hill.
λ = wavelength of the signal in
metres;
G = gain of the antenna (not in
VERTICAL POLARISATION
+30dB
dB format) over isotropic; and
+30dB
A = Aperture, as a decimal
HORIZONTAL POLARISATION
fraction.
Remember that an isotropic
antenna has a gain of unity and
60dB PATH
AMPLIFIED
LOSS
RE-BROADCAST
a dipole has a gain 1.64 times
LOW SIGNAL AREA
SYSTEM
more. Thus, the amount of power available is derived by:
ISOLATION: GEOGRAPHICAL
Pa = PiA
AND POLARISATION
where
Pi = power density in watts/
metre2;
Pa = power available; and
Fig.2: this is a variant of the passive rebroadcasting system with better isolation
A = Antenna aperture as a decbetween antennas and a masthead amplifier interposed between the hilltop
imal fraction
antennas.
By combining the above equations, one arrives at an equation
have a bearing on the outcome and of a halfwave dipole, broadside to the that can determine the received power
signal strengths can be assumed to dipole, is:
in an antenna of known gain:
be slightly less than those calculated.
Pr = 1.64Pt/4πr
Pr = Pt.Gt.Gr.λ2/(4πr)2
An isotropic radiator is not exactly a or
The situation of passive rebroad
useful concept in the real world, alE = √(49.2 x Pt)/r
casting (receiving signals on one
though it is a base on which to place where
antenna and feeding them down to
firm theory.
Pr = power density in w/m2;
another for rebroadcast) can be shown
There are different correction factors Pt = power transmitted in watts;
to be something of a hopeless case and
that are added to the equations to take r = distance in metres; and
will only work if the received signal
account of antenna performance and E = field intensity in volts/metre.
strength is exceptionally strong and
other configurations. For a halfwave
The above equations give the pow- the rebroadcast distance is relatively
dipole oriented for maximum radia er density at a point “r” metres from short; ie, a couple of hundred metres.
tion, there is a correction factor of 1.64. the source. If you have a transmitting
By using the above formulas, the
This factor when converted to dB gives antenna with a gain of 10dBd (over received power level at the hilltop
the apparent gain difference between a dipole), then this factor must be receiving site can be approximated if
antennas referenced to a dipole and incorporated into the equation. 10dB you know several important factors:
those to the isotropic source. When is a power increase of 10 times, so the the radiated power of the transmitter,
looking at manufacturers’ antenna gain input power in watts must be multi- the frequency of the signal, the gain
figures, check to see if they are refer- plied by the apparent increase over the of your receive antenna, and the disenced to isotropic (dBi) or to a dipole original antenna (with its compensa- tance between the transmitter and the
(dBd). Those referenced to isotropic tion factor present if required).
receiving antenna.
appear to have 2.15dB more gain but
This multiplication factor is its
Let us put a few figures into the
their real gains are the same.
power gain not in dB form but linear equation and see how our theoretical
The formula for the field intensity form; eg, 6dB is 4 times, 10dB is 10 system is going to perform. To get a
VERTICAL POLARISATION
May 1994 15
antenna is 6.16nW. Let’s assume the
transmit antenna has a gain of 10dBi
and that the receive antenna has a
gain of 10dBi.
The power received by the home
TV antenna is found by utilising the
same equation and a transmit power
of 6.16nW (the original received
signal). This results in a signal level
of 5µV/m, a totally useless signal for
any TV.
75mm
600mm
BLACK
POLYTHENE
SPREADER
Calculating the path loss
8-12 GAUGE
FEEDLINE
SPACER
TAPERED MATCHING SECTION
APPROX. 2m LONG
10mm
SUPPORT
ROPE
CHOCOLATE
BOX
CONNECTORS
PVC STRAINER BLOCK
300 RI BB ON
Fig.3: this is the author’s open line feeder system which gives very low signal
loss over a long path. The open line is matched to 300Ω ribbon with a 2-metre
long tapering section and terminated as shown.
good quality signal at the TV set, you
need a minimum of 250µV (assuming
a modern sensitive TV set). For the
purposes of this exercise, we’ll assume
the following:
• 100 watts of transmitter radiated
power (Pt x Gt);
• UHF channel 42; 640MHz approximately; wavelength = 0.468 metres;
• Distance from transmitter to receiver
= 30km;
• Antenna receive gain = 6dBi (4 times
relative to isotropic antenna).
Pr = Pt.Gt.Gr.λ2/(4πr)2
= 1000 x 4(0.468)2/(4 x π x 30,000)2
16 Silicon Chip
= 876.096/(1.42 x 1011)
= 6.16 nanowatts
This is a respectable received signal
strength and can be converted into
volts/metre by the following formula:
E = √(Pr.R)
where R is the impedance of the antenna in ohms.
The result is a signal of 679µV into
a 75Ω antenna, a good signal indeed.
In our setup, the receive antenna is
connected via a short length of low
loss coax to the “transmit” antenna as
shown in the diagram of Fig.1.
The power delivered to the transmit
In order to produce the required
signal level at the home TV, a level of
amplification equal to the path loss
between the rebroadcasting antenna
and home receive antenna has to be
insert
ed at the re-transmitting site.
This is easily calculated. It is the difference between the re-transmitted
power level of 6.16nW and the home
television received signal:
6.16 x 10-9 - 3.4 x 10-15 = 60dB
This is about 60dB of path loss and
therefore the gain required is 60dB.
This amplification should be provided
between the hilltop receiving antenna
and the rebroadcasting antenna.
While it is relatively easy to provide 60dB of gain into the rebroad
casting system connecting coax, one
must maintain adequate RF isolation
between the receive and transmit
antennas. This is to prevent feedback
and thus stop the system becoming
an RF oscillator at the frequency of
maximum feedback. The two antennas must not “see” each other. One
antenna could be placed on one side
of the hill and the other placed on
the other side, “hidden” from view
of its mate.
Even more isolation can be obtained
by having one antenna with vertical
and the other with horizontal polarisation. This can amount to as much
as 20dB. One also has to make sure
that the coax between them is well
and truly decoupled to prevent RF
coupling along the outside of the coax.
The other factor that helps in antenna isolation is the front-to-back
ratio. An antenna with a very good
front-to-back ratio will have little
problem ignoring signals coming to it
from behind, again improving antenna
isolation. This setup is shown in Fig.2.
The foregoing should give the reader
an insight into antenna concepts and
propagation. While it is possible for
passive rebroadcast systems to work,
the received signals must be very
CAPACITOR
75
75
300
300
GND
GND
CAPACITOR HERE OR HERE
C
300
OR
C
75
Fig.4: this diagram shows the modifications needed to a
standard 4:1 balun to enable DC to be sent up the ribbon to
the masthead amplifier. Two such baluns will be required.
strong, the antenna gains high and the
rebroadcast distances short.
Masthead antenna
The other comment in the letter
relates to using a masthead amplifier
to drive a long feedline to the home
TV below a hill in a weak signal area.
My experience is that this setup can
work extremely well, contrary to the
comments from the magazine. I once
built such a system for my parents
who lived in the country and whose
TV reception left a lot to be desired.
It used a standard TV antenna on
a hilltop and a homebuilt masthead
preamplifier (BFY90) with a gain of
about 15dB. This preamplifier fed
signals down about 1km of balanced
open wire feeder. Power was fed to
the preamplifier via the open wire
feeder. This feeder was made from
single-strand copper wire spaced at
about 75mm and used spreaders made
from 12mm black polythene tubing.
Matching into and out of the open
wire feedline was by a 2-metre long
tapering section that brought the
open wire feeder down to the spacing of 300Ω ribbon. The 75Ω coax
was matched to a short piece of 300Ω
ribbon by the usual 4:1 ferrite balun,
modified slightly to enable it to pass
DC into the open-wire feedline from
the 75Ω coax. Fig.3 shows the details
of the polythene spreaders and the
tapering match and termination to the
300Ω ribbon.
Open wire feedline can also be made
from single strand galvanised fencing
wire. At UHF, open wire feeder can
have a loss of less than 1.5dB/100
metres. Even good quality coax has
a much greater loss than this and is
much more expensive. That means
that you could run a 15dB preamp
lified signal down 1km of open wire
feeder and still have the same signal
level present that was available at the
receiving antenna terminals ahead of
the masthead preamp.
On the other hand, open wire feeder
is more “messy” to use than coax as it
has to be supported on poles and must
not come too close to metal objects; ie,
no closer than 200mm.
Matching to 75Ω is somewhat involved and you must use modified
baluns to pass DC and RF simultaneously.
Power to the masthead amplifier
is best fed as AC as this will reduce
electrolytic corrosion at connections
but you can use DC if you want to. To
get DC through the 300Ω-to-75Ω balun requires it to be modified slightly.
For this, you need a small low-value
(eg, 470pF) ceramic capacitor. Look
very carefully at the way the balun
is wound. The windings you want to
investigate are those that appear to
crisscross. The capacitor is placed in
series with one of those wires.
Fig.4 shows how the balun is wired.
You will have to disconnect each wire,
leaving the others connected, and test
for a loss of continuity between the
inner and outer of the 75Ω side. When
this is achieved, test for continuity
from the 300Ω side to the 75Ω side
without any shorts between either side
of the respective feedpoints.
If all is well, solder the capacitor
in series between the 300Ω terminal
and the “disconnected” end of the
winding. It goes without saying that
you need to put this assembly into a
water-tight container.
Two of these baluns are required,
one for each end of the open wire
feeder. A good way of connecting
the 300Ω ribbon to the thin end of
the taper is to use the insides from a
“chocolate block connector” (ie, the
internal metal sections from plastic
barrier terminal blocks), as shown
in Fig.3.
References
(1). Hewlett Packard. Spectrum Analy
zer series Application Note 150-10,
1979.
(2). I.T.T Radio Reference Manual,
4th Edition
(3). Introductory Topics in Electronics
and Communications, Antennas, by F.
R. Connor, 2nd edition. ISBN 0-71313680-4.
(4). Radio Communication in Tunnels,
by K. F. Treen, Wireless World, March
SC
1979.
CALLING ALL HOBBYISTS
We provide the challenge and money for you to design and build as many
simple, useful, economical and original kit sets as possible.
We will only consider kits using lots of ICs and transistors.
If you need assistance in getting samples and technical specifications while
building your kits, let us know.
YUGA ENTERPRISE
705 SIMS DRIVE #03-09
SHUN LI INDUSTRIAL COMPLEX
SINGAPORE 1438
TEL: 65 741 0300 Fax: 65 749 1048
May 1994 17
Charge your nicad cells in rapid
time with this ...
By DARREN YATES
FAST CHARGER FOR
NICAD BATTERIES
Tired of waiting for the 16 hours it takes to
charge your nicad cells? This low-cost project
uses a single Philips IC & will charge four
“AA” cells in 50 minutes. It runs from
a 12V 1A plugpack supply or from a car
battery.
Nicad batteries are now one of
life’s necessary evils. They can make
running battery-operated gear much
cheaper than using ordinary dry cells
but they do have one big disadvantage
– when the batteries go flat, it usually
takes about 16 hours to recharge them.
Another disadvantage is their lower
output voltage compared to standard
dry cells (1.2V vs 1.5V).
18 Silicon Chip
We can’t do much about the voltage
difference between the two types of
batteries but we can do something
about the time it takes to recharge
nicads. The answer is to build this Fast
Nicad Charger. It can charge either two
or four “AA”, “C” or “D” cells in rapid
time – 50 minutes for “AA” 600mAh
cells and 100 minutes for “C” and “D”
1.2Ah cells.
The circuit is based on a new Philips
chip – the TEA1100. This is a dedicated nicad charger IC with inbuilt
switching controllers. This switching
technique provides much higher efficiency than the more conventional
linear techniques.
We’ve used the switching controller feature and several other
features of the chip to make one of
the simplest yet most comprehensive
nicad chargers currently available. It
provides automatic cutout when the
batteries are fully charged, a timer
override and two charging modes –
fast and trickle.
Preventing overcharging
Standard nicad chargers use circuitry which applies a constant current
Voltage sensing & timing
The Fast Nicad Charger uses both
current and voltage sensing to ensure
correct charging, as well as an RC
clock/timer which shuts down the
circuit after a preset time if the sensing
circuit fails to detect the full-charge
condition.
The charging current is sensed simply by using a low-value resistor in
series with the battery but the voltage
sensing is somewhat more complicated. Instead of checking the battery vol
tage for an absolute value, the circuit
V
CHARGE CURRENT
Fig.1: typical charging
curve for a nicad cell.
Note how the voltage
falls slightly at the end
of the charging cycle.
This is detected by the
circuit & used to switch
the charging current to
a low level to keep the
battery topped up.
BATTERY VOLTAGE
to the battery over a preset period
of time – usually about 16 hours for
ordinary nicads and five hours for the
fast-recharge types. The big disadvantage of this technique is that it doesn’t
take into account the current charge
state of the battery and this can lead
to overcharging and possible damage
to the battery pack.
By contrast, the Fast Nicad Charger
does take the current charge state of
the battery into consideration and
sets its charging current accordingly.
This prevents overcharging and greatly
increases battery life.
Another problem with nicad batteries is the so-called “memory effect”.
Often, batteries are placed into a charger with
out having been completely
discharged beforehand. In the short
term, this doesn’t cause too much of
a problem but problems do occur after
repeated charge/discharge cycles.
What happens is that the battery
develops a memory for the point to
which it is continuously discharged
and this ends up becoming the end
point for future use. In other words,
the bat
tery will only partially discharge before appearing to go “flat”.
This can reduce the effective capacity
of the battery by more than half in
some cases.
The only way to prevent this unwanted memory effect from occurring
is to deep-cycle the battery. In practical terms, this means discharging the
battery to its recommended end-point
voltage before placing it in the charger.
An automatic discharge circuit is
not a feature of this project, however.
If you want to correctly discharge
nicad batteries, we recommend that
you build either the Nicad Discharger
described in the July 1992 issue of
SILICON CHIP or the Automatic Nicad
Discharger described in the November
1992 issue.
TIME
looks for a relative change of 1% from
the maximum voltage – see Fig.1.
Unlike SLA batteries, once nicads
reach their full charge capacity, their
output voltage drops. Because it is
virtually impossible to predict the
absolute maximum voltage, Philips
has used an alternative method called
“-dV sensing”. By looking for a 1%
drop in the relative battery voltage,
the new TEA1100 can accurately
determine when a nicad pack is fully
charged. This ensures that the battery
is never overcharged, regardless of its
initial capacity.
The RC clock/timer utilises a counter block within the TEA1100 to set a
maximum timeout period. Its job is to
automatically switch off the charger if
the battery voltage hasn’t dropped the
required 1% during the set time period, or if the -dV sensing circuit misses
the slight drop in output voltage when
the cells are fully charged.
Essentially, the timing circuit is
included as cheap insurance against
the circuit not shutting down, as can
occur if the cells are faulty or if the
sensing circuit fails to detect the full
charge condition. Some cells have only
a very shallow voltage drop at the end
of their charging cycle and this can
sometimes be missed by the sensing
circuitry. In most cases though, by the
timer the timer operates, the circuit
will have already shut down.
Circuit diagram
Fig.2 shows the complete circuit
details of the Fast Nicad Charger.
Power is derived from a 12V DC 1A
source and applied to the circuit via
on/off switch S1 and reverse-polarity
protection diode D1. Since the TEA
1100 requires a supply of between
5.5V and 11V, ZD1, Q3 and their
associated components form an 8.5V
regulator which feeds pin 12 of IC1.
The output from the regulator also
drives charging indicator LED 1 via
pin 15.
The charging current flows to the
batteries from D1 via transistor Q2,
a TIP32C 3-amp PNP power device.
Main Features
•
•
•
•
Two charging modes – fast and trickle.
•
Timer override to ensure charger cuts off if cells are faulty or fully charged
condition not detected.
•
•
Can be powered from a 12V 1A plugpack supply or from a car battery.
Charges two or four cells (600mAh or 1.2Ah capacity) at once.
Charges “AA” cells in 50 minutes & “C” & “D” cells in 100 minutes.
Automatically cuts off when cells are fully charged & switches to trickle
charge mode.
Has reverse polarity protection for power supply & is fully protected
against short-circuit or open circuit nicad batteries
May 1994 19
C
Q3
BC337
S1
12V
INPUT
L1 : 60T,0.5mm DIA ENCU ON
ALTRONICS L-5120 TOROID
10
16VW
ZD1
9.1V
400mW
Q2
TIP32C
C
E
470
16VW
470
B
3.3k
D1
1N4004
E
LED1
CHARGE
L1
10k
D2
FR104
B
100
Q1
BC337
C
12
2.2k
B
E
100pF
K
A
15
S2
IC1
TEA1100
5
4
13
16 3
27k
B CE
0.1
5W
S3
470
16VW
600mAH
1.2AH
.0018
10
680pF
E
C
VIEWED FROM
BELOW
4
CELLS
7
1
2.2k
B
100k
2
CELLS
2 OR 4
CELL
BATTERY
Fig.2: the circuit
is based on IC1. It
samples the cell
voltage via its pin
7 input & provides
a pulse width
modulated (PWM)
output at pin 1.
This PWM output
drives Q1 and this
in turn drives power
transistor Q2 which
switches current
pulses through to the
cells.
100k
.0039
47k
FAST NICAD/NIMH BATTERY CHARGER
Along with fast-recovery diode D2 and
inductor L1, these components form a
step-down DC-DC converter which is
pulse width modulated (PWM) con
trolled by IC1.
The pulse-width modulated waveform appears at pin 1 of IC1 and is
inverted by transistor Q1. This in
turn switches power transistor Q2 to
control the current fed to the batteries.
Voltage monitoring is achieved by
applying a proportion of the output
voltage to the Voltage Accumulator
input (pin 7). This is done by using S2
to select between one of two voltage
divider circuits which connect across
the battery. The valid input range for
pin 7 is between 0.385V and 3.85V.
The maximum charging time is
set by switch S3 and its two associ-
ated timing capacitors: 0.0018µF for
600mAH batteries and 0.0039µF for
1.2AH batteries. The two capacitors
determine the frequency of the timing
oscillator; the higher the capacitor
value, the lower the frequency and the
longer the charging time.
The .0018µF capacitor sets the
timeout period to 50 minutes, while
the .0039µF capacitor sets the period
to 100 minutes.
Charge LED
The TEA1100 uses only a single
LED to indicate one of two charging states. When the charger is first
switched on, the charge LED is on
continuously, indicating that the
circuit has gone into the main “fastcharge” mode.
Once the circuit has decided that
the batteries are charged, the LED
flashes. This not only indicates “endof-charge” but also the rate at which
the current pulses are being fed to the
battery to maintain a “trickle” charge.
This trickle charge will maintain the
batteries in top condition after the
main charging cycle has been completed.
The charging current is regulated by
the IC and the 2.2kΩ resistor between
pin 5 and ground. This, along with the
0.1Ω 5W current sensing resistor on
pin 16, sets the main charging current
to just on 960mA. The main internal
reference current is determined by the
27kΩ resistor connected to pin 10 and
is set to approximately 45µA.
In order to main maintain loop sta-
RESISTOR COLOUR CODES
❏
❏
❏
❏
❏
❏
❏
❏
❏
❏
No.
2
1
1
1
1
2
1
1
1
20 Silicon Chip
Value
100kΩ
47kΩ
27kΩ
10kΩ
3.3kΩ
2.2kΩ
470Ω
100Ω
0.1Ω
4-Band Code (1%)
brown black yellow brown
yellow violet orange brown
red violet orange brown
brown black orange brown
orange orange red brown
red red red brown
yellow violet brown brown
brown black brown brown
not applicable
5-Band Code (1%)
brown black black orange brown
yellow violet black red brown
red violet black red brown
brown black black red brown
orange orange black brown brown
red red black brown brown
yellow violet black black brown
brown black black black brown
not applicable
S3
PARTS LIST
S2
5
2
3
4
A
1
6
LED1
K
470uF
Q3
.0039
.0018
47k
2.2k
27k
0.1
5W
Q2
1
2
LED1
A
K
100
470
3
IC1
TEA1100
L1
4 5 6
1
680pF
100pF
D2
2.2k
10k
100k
ZD1
12V
Q1
10uF
100k
D1
3.3k
S1
470uF
OUTPUT
Fig.3: install the parts on the PC board as shown on this wiring diagram,
making sure that all polarised parts are correctly oriented. L1 consists of
60 turns of 0.5mm-diameter copper wire on a Neosid toroidal core.
Fig.4: check your PC board against this full-size artwork before
installing any of the parts.
bility, an RC network consisting of a
47kΩ resistor and a 680pF capacitor is
connected between pin 4 and ground.
This ensures that no oscillation or
“motor-boating” occurs by reducing
the bandwidth of the circuit while still
maintaining an adequate level of error
voltage feedback information.
Construction
All the parts for the Fast Nicad
Charger, except for the three switches
and LED 1, are installed on a PC board
coded 11102941. Fig.3 shows the assembly details.
Before installing any of the parts,
it’s a good idea to check the board
carefully for any shorts or breaks in
the tracks by comparing it with the
published pattern (Fig.4). If you do
find any, use a small artwork knife or
a dash of solder to fix the problem as
appropriate.
Begin the assembly by installing PC
stakes at the external wiring points,
then install the wire link, the resistors
and diodes. Be sure to use the correct
diode type number at each location
and make sure that they are all correctly oriented. After that, you can install
the MKT capacitors, the electrolytics
and the 0.1Ω 5W resistor.
Next, install the three transistors
and the IC, again taking care with
the polarity. Once these parts are in,
a small finned heatsink should be attached to transistor Q2 using a 3mm
machine screw and nut.
The last component to go on the
board is inductor L1. This is wound on
1 PC board, code 11102941,
102 x 56mm
3 SPDT toggle switches
1 plastic case, 137 x 60 x 42mm
1 micro-U heatsink
1 large black crocodile clip
1 large red crocodile clip
1 small black crocodile clip
1 small red crocodile clip
4 PC stakes
1 5mm LED bezel
1 front panel label
1 33mm OD toroidal core
1 2-metre length of 0.5mm
diameter enamelled copper
wire
Semiconductors
1 TEA1100 battery monitor for
nicad chargers (IC1)
2 BC337 NPN transistors
(Q1,Q3)
1 TIP32C PNP power transistor
(Q2)
1 1N4004 silicon diode (D1)
1 FR104 fast-recovery diode
(D2)
1 9.1V 400mW zener diode
(ZD1)
1 5mm green LED (LED1)
Capacitors
1 470µF 16VW electrolytic
1 100µF 16VW electrolytic
1 10µF 16VW electrolytic
1 .0039µF 63VW MKT polyester
1 .0018µF 63VW MKT polyester
1 680pF 63VW MKT polyester
1 100pF 63VW MKT polyester
Resistors (0.25W, 1%)
2 100kΩ
2 2.2kΩ
1 47kΩ
1 470Ω
1 27kΩ
1 100Ω
1 10kΩ
1 0.1Ω 5W
1 3.3kΩ
Miscellaneous
Screws, nuts, washers, hook-up
wire.
a Neosid toroidal core (Altronics Cat.
L-5120) using two metres of 0.5mm
diameter enamelled copper wire. Feed
about one half of the wire through the
middle on the toroid, then wind on
about 30 turns, keeping the windings
tight and close together. The other
half of the wire can then be used to
complete the winding.
May 1994 21
screws and nuts, with an additional
nut under each corner to serve as a
spacer. This done, complete the wiring to the front panel items as shown
in Fig.3.
Make sure that switches S2 and
S3 are oriented with respect to the
LED exactly as shown (ie, the switch
terminals connecting to points 1 &
6 on the PC board must be nearest
the LED).
You will also have to connect the
power supply and output leads. These
can be fitted with crocodile clips or
terminated in some other suitable
manner, depending on your power
supply and the terminals on your
nicads or their holder.
Testing
Once everything is in position,
connect your multimeter (set to the 2A
Plastic cable ties are used to secure the wiring to the two switches & to anchor
range) in series with the power supply
the large toroidal inductor to the PC board. Take care to ensure that switches
and switch on. You should find that
S2 & S3 are correctly oriented on the front panel – see text & Fig.3.
the quiescent current measures about
5-10mA and that the LED is off.
The exact number of turns is not for the two switches and the indicator
If this checks out, set S2 and S3 to
critical but you should find that you LED. It’s best to use a 3mm drill to match your nicad battery pack and
get about 60 turns on in total.
begin with and then slowly ream the check that the output voltage is close
Finally, trim off the excess lead holes to the correct size with a tapered to the mark – for two cells, it should be
lengths, clean the wire ends and sol- reamer.
somewhere around 2.4V and for four
der the inductor into position on the
The power switch (S1) is mounted cells it should be about 4.8V.
board. The inductor can be anchored on one end of the case and an addiAssuming that the open-circuit
using a plastic cable tie which feeds tional hole is drilled adjacent to this output voltage is correct, connect
through a hole in the PC board – see to provide access for the power leads. the nicad pack to the output. You
photo.
A hole drilled in the opposite end of should find that the current drain
the case is used for the battery output is now either about 600mA or 1.2A,
Final assembly
leads. In addition, you will have to depending on the setting of S3, and
The board and its associated com- drill four mounting holes in the base that the LED is lit.
ponents are installed in a small zippy of the case for the PC board.
Depending on how much charge is
The various items of hardware can in the battery and the setting of S3,
box measuring 137 x 60 x 42mm. First,
attach the adhesive label to the lid of now be mounted in position and the the LED should stay on for some time
the case, then drill out mounting holes PC board secured using 3mm machine (it could be as long as 50 minutes for
“AA” cells” or 100 minutes for
“C” or “D” cells) and then begin
to flash. When this flashing
begins, the current should drop
CHARGE
to about 10mA between flashes
and rise sharply each time the
LED lights.
If the LED fails to light,
check that it has been oriented
2
600
correctly.
Now you can attack that
FAST NICAD
drawer full of nicad cells and
CHARGER
charge them up in quick time!
Don’t forget though – if you
1200
4
want maximum performance
mAH
CELLS
from your nicad cells, you
should also build a discharger
to discharge the battery pack
to its correct end-point voltage
Fig.5: this full-size artwork can be used as a drilling template for the lid of the case.
SC
before charging.
Drill small pilot holes first, then carefully ream these to size.
22 Silicon Chip
Simple drivers for
radio control servos
Build one of these simple servo drivers & you
can run the devil out of your servos. You can
use them for testing servos or for direct control
applications where a radio link is not required.
The circuit parts are cheap and readily
available.
By NENAD STOJADINOVIC
As anyone who has been reading
Bob Young’s excellent radio control
column in this magazine will know,
servos are the muscle behind any
radio control system. These devices
are a minor electronic miracle: small,
powerful and cheap, but until now
have always been lumbered with a
radio control system to drive them.
Think of how useful they would be if
you could drive them directly from a
simple pot or pair of pots controlled
by a joystick.
These were my thoughts, one dark
and stormy night, as I was casting
about for a good way of remotely
controlling a pair of mirrors to be used
in a laser light show. A quick perusal
of some modelling magazines and
the current circuit was born. After
fashioning some suitable metalwork I
24 Silicon Chip
2.1ms
30ms
soon had laser beams flying about the
lab with gay abandon.
Lately, I’ve been using servos in
place of mechanical linkages in my
car and at around $20 per servo there
is little in
centive to fiddle around
with cables, rods and so on. What’s
more, running controls into areas of
very high or low pressure is made
easy by the availability of watertight
bulkhead electrical connectors from
your friendly local marine chandler.
Anyway, whatever our field of
endeavour, that old worn-out cliche
about the applications are only limited by your imagination must surely
apply. So without further ado, on with
the circuit.
How it works
The standard servo has three input
This photograph shows the author’s prototype of the
circuit featured in Fig.2. Note that the final version differs
from this prototype in terms of board layout.
0.7ms
Fig.1: the control signal for a servo
consists of a continuous fixedfrequency pulse stream. The pulse
width controls the servo position.
pins and these are +5V (power), 0V
(GND) and control. The control signal
is a continuous pulse stream which is
shown in Fig.1. It is important to note
that the frequency of these pulses does
not intentionally vary (it is not critical)
and a period of between 20 and 50ms
will do the job with most servos.
The movement information is
contained in the width of the pulses, which is why this sort of control
system is referred to as Pulse Width
Modulation (PWM). A pulse width
of 0.7ms will usually give fully coun
terclockwise movement and 2.1ms
will give fully clockwise rotation.
This alternative version is based on the circuit shown in
Fig.5. Once again, the final version differs in layout from
this prototype – see Fig.6.
82k
11
180k
2
4
14
IC1a
NE556
6
5
3
7
VR1
10k
LIN
Q1 100k
VN10KM
D
0.1
.01
G
S
2.7k
+5V
PARTS LIST
VR3
100k
Circuit One (Fig.2)
VR2
5k
100
.01
.01
10
13
0.1
.01
9
IC1b
12
DG S
VIEWED FROM
BELOW
1 PC board, code 09105942
1 556 dual timer (IC1)
1 VN10KM Mosfet (Q1)
1 10kΩ linear potentiometer
(VR1)
1 5kΩ trimpot (VR2)
1 100kΩ trimpot (VR3)
OUTPUT
11
8
.01
.01
0.22
Fig.2: the pulse frequency for the servo driver is derived using astable oscillator
IC1a. Its output at pin 5 is differentiated & then used to trigger monostable IC1b
via buffer stage Q1. VR1 varies the pulse width produced by IC1b.
The duration of this output pulse is
set by potentiometer VR1 which is
calculated to give the required 0.72.1ms range.
Taming the duty cycle
As presented, the free-running
oscillator has a duty cycle of about
60%, meaning that its positive output
pulses will be about 18ms long. This
is much longer than can be used to
trigger the 556 monostable (IC1b), so
some means had to be used to obtain
short negative pulses.
My solution was to differentiate the
oscillator output and this produces a
series of positive and negative spikes
about zero volts at every transition.
These spikes don’t have much energy
and so are buffered by a Mosfet (Q1)
which has a very high input impedance. Being an N-channel device, it
only conducts on the positive pulses
and so produces negative-going pulses
at its drain (D).
These pulses are coupled to pin 8
to trigger the monostable. It produces
100k
VR2
1
+5V
1 PC board, code 09105941
1 4011 or 4001 quad gate
package (IC1)
1 1N914 signal diode (D1)
1 0.1µF MKT capacitor
1 10kΩ linear potentiometer
(VR1)
1 10kΩ trimpot (VR2)
Resistors (0.25W, 1%)
1 1.8MΩ
1 1kΩ
1 150kΩ
short positive pulses which can be set
to vary between 0.7 and 2.1ms long.
Building the circuit
A small PC board was designed to
accommodate the components and
this is shown in Fig.4. With only a
handful of components, construction
is very simple. You could use a small
piece of Veroboard as an alternative
to a PC board.
OUTPUT
0.1
GND
180k
.01
VR1
Circuit two (Fig.5)
Q1
0.1
2.7k
IC1
556
82k
VR3
Resistors (0.25W, 1%)
1 180kΩ
1 82kΩ
1 100kΩ
1 2.7kΩ
0.22
.01
100
The circuit to achieve this uses
a free-running oscilla
t or coupled
to a monostable or “one shot”, as
shown in Fig.2. It is based on a 556
dual timer which can be regarded as
two 555 timers in the one package.
The free-running oscillator has its
frequency determining components
connected to pins 1, 2 and 6 and these
give a frequency of around 34Hz,
corresponding to a period of about 30
milliseconds. The oscillator output
is taken from pin 5 and it is used to
trigger the monostable section of the
circuit.
The monostable or “one shot” is the
second half of the 556 and its pulse
length is determined by the components connected to pins 12 and 13; ie,
trimpots VR2 & VR3, control pot VR1
and the 0.22µF capacitor. The output
pulse stream appears at pin 9.
A monostable produces an output
pulse of programmable duration each
time it is triggered, the only proviso
being that the trigger pulse must be of
shorter duration than the output pulse.
Capacitors
1 0.22µF MKT capacitor
2 0.1µF MKT capacitor
2 .01µF MKT capacitor
GND
Fig.3: install the parts on the PC board as shown
in this diagram, taking care to ensure that the IC
is oriented correctly.
Fig.4: the full-size etching pattern
for the PC board. It is coded
09105942 & measures 51 x 40mm.
May 1994 25
SATELLITE
SUPPLIES
Aussat systems
from under $850
+5V
1
4001
IC1a
2
1.8M
1.8M
ON
CONTROL
VR2 10k
FEEDHORNS C.BAND FROM .........$95
150k
150k
4
IC1b
8
9
IC1c
10 12
13
14
IC1d
11
1k
OUTPUT
7
0.1
.01
D1
1N914
LNB’s Ku FROM ..............................$229
FEEDHORNS Ku BAND FROM ......$45
6
VR1
10k
SATELLITE RECEIVERS FROM .$280
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5
3
Fig.5: this alternative circuit from Bob Young was originally featured
in the April 1993 issue. IC1a & IC1b form an astable oscillator, with
pulse width set by VR1, VR2 and the 0.1µF capacitor.
DISHES 60m to 3.7m FROM ...........$130
0V
+5V
1k
1
OUTPUT
0.1
IC1
4001
150k
1.8M
VR2
D1
VR1
Fig.6 (left): the circuit of Fig.5 is assembled as shown in this diagram. Note
that the output frequency also varies with this unit but not enough to affect
servo operation. Fig.7 at right shows the full-size etching pattern for the PC
board.
LOTS OF OTHER ITEMS
FROM COAXIAL CABLE,
DECODERS, ANGLE
METERS, IN-LINE COAX
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FOR JAPANESE, NTSC TO
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DECODERS, PLUS MANY
MORE
For a free catalogue, fill in & mail
or fax this coupon.
✍
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on your satellite systems.
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L&M Satellite Supplies
33-35 Wickham Rd, Moorabin 3189
Ph (03) 553 1763; Fax (03) 532 2957
26 Silicon Chip
The lead for your particular servo
can usually be obtained from any good
hobby shop. If not, just ask who repairs
that particular brand and call them.
While you’re at it, find out how the
servo pins are arranged; the manual
might have the information.
If not, it’s simply a matter of checking the output voltages from the receiver with a multimeter. Ground and
+5V should be fairly obvious and the
lead with some small voltage will be
the control output.
Adjustment
The servo travel limits are adjusted
by VR2 and VR3. VR2 should be the
anticlockwise limit and this is set by
moving VR1 fully anticlockwise and
then adjusting VR2 so that the servo is
not stalled. It is important not to stall
servos because they will draw high
currents and get very hot, ultimately
burning out the motor.
The clockwise limit is then set in
the same way using VR3.
Second circuit
Having designed the above circuit, I
then came across a small circuit from
Bob Young that does the same job as
mine! It was featured in the April 1993
issue of SILICON CHIP. The obvious
solution, of course, was to present his
circuit as well, complete with a PC
board and the addition of the suggested
trimpot, VR2.
Bob’s version is shown in Fig.5
while the PC component wiring diagram is shown in Fig.6. Take care
to ensure that the IC and diode are
correctly oriented during the PC board
assembly.
This workings of this circuit are less
apparent than the circuit shown in
Fig.2 but essentially IC1a and IC1b are
connected as a free-running oscillator
with an uneven duty cycle. The pulse
duration is mainly a function of VR1,
VR2 and the 0.1µF capacitor.
There is also an essential difference
in its operation in that when you
change the settings of VR1 to set the
pulse output, the frequency changes
too, although not markedly. However,
this does not affect the servo operation
at all and so the circuit is quite valid
SC
for test purposes.
SILICON
CHIP
If you are seeing a blank page here, it is
more than likely that it contained advertising
which is now out of date and the advertiser
has requested that the page be removed to
prevent misunderstandings.
Rod Irving Electronics Pty Ltd
SILICON
CHIP
If you are seeing a blank page here, it is
more than likely that it contained advertising
which is now out of date and the advertiser
has requested that the page be removed to
prevent misunderstandings.
Rod Irving Electronics Pty Ltd
SILICON
CHIP
If you are seeing a blank page here, it is
more than likely that it contained advertising
which is now out of date and the advertiser
has requested that the page be removed to
prevent misunderstandings.
Rod Irving Electronics Pty Ltd
SILICON
CHIP
If you are seeing a blank page here, it is
more than likely that it contained advertising
which is now out of date and the advertiser
has requested that the page be removed to
prevent misunderstandings.
Rod Irving Electronics Pty Ltd
SILICON
CHIP
If you are seeing a blank page here, it is
more than likely that it contained advertising
which is now out of date and the advertiser
has requested that the page be removed to
prevent misunderstandings.
Rod Irving Electronics Pty Ltd
CIRCUIT NOTEBOOK
Interesting circuit ideas which we have checked but not built and tested. Contributions from
readers are welcome and will be paid for at standard rates.
Battery voltage
indicator for cars
Prevention is always better than
cure and less expensive. This simple
battery voltage indicator was devised
after the alternator in my car failed
during a long trip and the alternator
warning light did not light.
The circuit uses six LEDs (one yellow, three green and one red). Each
LED is wired in series with a zener
diode and a 680Ω current limiting
resistor, and connected across the
supply line. In addition, each zener
diode has a slightly higher voltage
than the preceding zener diode. Thus,
the LEDs progressively turn on as the
battery voltage increases from about
9.6V up to 15V.
The circuit can be powered via the
ignition switch. Table 1 shows how to
interpret the display.
When building the circuit, arrange
the LEDs in a straight line – yellow on
Light meter adapter
for a DMM
This light meter adapter may appear
primitive but it works very well. If
you already own a multimeter, its cost
would be insignificant compared to
that of a dedicated instrument. It can
measure from 1 lux to 200,000 lux,
which is comparable in range to the
light from a candle at one metre to
the light from the midday sun at the
equator.
As shown on the circuit, a BPW21
silicon blue photocell is used as the
sensing element. This has a logarithmic open circuit voltage response but
a very linear current response for short
circuit current versus light intensity.
Its internal impedance varies from
20MΩ at 1 lux to a few megohms at
100,000 lux.
By using a load resistor which is
small with respect to the internal
impedance, the cell acts as a current
generator over a limited range and we
accept a tolerance of a few percent.
32 Silicon Chip
+12V FROM
IGNITION
SWITCH
ZD1
7.5V
LED1
YELLOW
ZD2
10V
ZD3
11VV
LED2
GREEN
680
680
LED3
GREEN
680
ZD4
12V
LED4
GREEN
680
ZD5
13V
LED5
RED
680
TO
CHASSIS
TABLE 1
Yel
Grn
Grn
Grn
Red
o
o
o
o
o
o
o
o
o
o
o
o
o
o
Volt.
Battery Condition
9.6V
Low (engine off); normal when cranking
12V
Normal if engine off; undercharge if engine running
13V
Undercharge if engine running
14V
Normal (engine running)
15V
Overcharge
o
the left, greens in the middle and red
on the right. That way, you can tell the
state of the battery at a glance. Best
of all, there are no transistors, ICs or
x1000
BPW21
R
x100
10R
10R
capacitors to fail, so reliability should
not be a problem.
B. Paynter,
Narrogin, WA. ($20)
S1
x1
x10
100R
100R
1000R
(SEE
TEXT)
TO DIGITAL
MULTIMETER
ON 200mV
RANGE
The digital multimeter must be set
to the 200mV range. If the reading is in
excess of 200mV, the next load resistor
is selected and a multiplier used, in
this case a factor of 10.
The multimeter used must also have
an input impedance of 10MΩ, so as to
simplify load resistor selection, especially on the lowest range.
The resistor value R is chosen by
using the Sun for calibration. To do
this, wire a 200Ω variable resistor
across the cell, then select a clear sky
between 11am and 2pm and direct the
cell towards the Sun. Now measure the
voltage across the resistor and adjust
the resistor value until the reading is
100mV in winter, or 120mV in spring
and autumn, or 140mV in summer
(Melbourne latitude).
This simple light meter
adapter plugs directly into
a DMM to give a reading
directly in lux on the
200mV range.
This done, remove the resistor from
the circuit and measure its value. This
becomes the x1000 multiplier load.
The other loads are now arrived at
by multiplying this value by 10 (for
100R), 100 (for 10R) and 1000 (for R).
Select series-parallel combinations
to give values that are within 1% of
the calculated values and adjust the
1000R value to take account of the
meter impedance.
The cell gives a nominal current
output of 7nA per lux, is sealed, has
a response to colour that’s similar to
the eye and is very stable. The current
has a temperature coefficient of -0.05%
per degree C, which is negligible in
this application.
Victor Erdstein,
Highett, Vic. ($20)
RLY1
12V REED
+12V
TO
COMPUTER
POWER
SUPPLY
47
16VW
14
1
2
10
10k
10k
DELAY
TIME
VR1
500k
C1
10
16VW
IC1d
10k
RESET TIME
VR2 500k
C2
4
3
IC1a
74C14
RESET
LED1
13
IC1b
1
14
RESET OUT
(TO RESET ON
MOTHER BOARD)
12
IC1e
11
2
1
16VW
2.2k
5
9
6
10
IC1f
RESET IN
(FROM COMPUTER
RESET SWITCH)
6
8
7
8
7
IC1c
Delayed reset for
PCs & compatibles
For various reasons, some computers do not boot up correctly when
power is first applied. The error
message on the screen usually does
not help since it is often unrelated
to the fault.
Often the fault is only a minor one
related to a reset malfunction on the
VGA board. This can be cured simply
by pressing the reset switch just after
power is applied, after which the
computer behaves faultlessly.
This circuit was developed to provide a reset signal to the computer
soon after power is first turned on. This
provides the desired effect of a hard
reset without having to reset manually.
The extra time taken for the computer
to boot up is minimal, since the delay
between power on and resetting can
be adjusted to a minimum of about
one second.
The circuit is powered by the +12V
supply rail inside the computer. The
reset lines from the circuit then con-
nect in parallel with the lines to the
reset switch on the computer’s front
panel.
A 10Ω resistor and 47µF capacitor
isolate and decouple the +12V supply
from the computer. Initially, capacitor C1 is discharged and the output
of Schmitt trigger IC1a is high. The
input of IC1b is also high and so its
output is low. The paralleled inverters, IC1d-IC1f, have high outputs and
the relay is off. The normally open
relay contacts of RLY1 are connected
in parallel with the reset line to the
computer.
When capacitor C1 charges up to the
threshold voltage of IC1a, via VR1 and
the 10kΩ resistor, the output of IC1a
goes low. This pulls pin 1 of IC1b low
via capacitor C2 and pin 2 goes high.
The low outputs of IC1d-IC1f drive
the coil of relay RLY1 and its contacts
now close to provide a reset signal to
the reset line. IC1c drives LED 1 to
indicate the reset.
Capacitor C2 now charges up to the
positive supply via VR2 and the 10kΩ
resistor, thus sending the output of
Six-way decision
maker uses two ICs
This circuit will give a decision
on just about anything. When S1 is
pressed, its associated 4.7µF capacitor is charged to the positive supply
rail and 555 timer IC1 starts. This
in turn clocks IC2, a 4017 decade
counter, so that, initially, the LEDs
are rapidly cycled on and off.
The 4.7µF capacitor now slowly
discharges via its associated 560kΩ
resistor and pin 7 of IC1. As it
does so, the 555 timer frequency
decreases until eventually it stops
and no further clock pulses are
applied to IC2. This means that
the LEDs gradu
ally slow down
Schmitt trigger IC1b low. RLY1 and
LED 1 now switch off. Note that the
relay is a reed type which only draws
12mA of coil current. Because the coil
is internally clamped with a diode, the
voltage polarity applied to the coil is
important.
Trimpots VR1 and VR2 set the delay time and reset time respectively.
The delay time is adjusted so that the
computer is reset a certain time after
power is applied. This time must be
long enough to ensure that the computer boots up successfully.
The delay time is adjusted to be
about 100ms or longer which should
be sufficient time to reset the computer. Resetting times can be seen by
observing LED 1.
Note that if your computer does not
have a spare power cable to obtain
+12V for the circuit, you can buy a
power splitter cable from Dick Smith
Electronics (Cat. X-2064). The relay is
available from Jaycar Electronics (Cat.
SY-4032).
John Clarke,
SILICON CHIP.
+9V
100
S1
4.7
4.7M
560k
7
33k
4
8
IC1
555
6
2
6xLED
16
3
2
3
14
5
1
.047
.01
7
10
15
5
1
8
until only one remains lit, to give
a decision.
The LEDs can be marked in any
way; eg, yes, no, maybe, perhaps, go
4
IC2
4017
13
1k
and stop. Alternatively, the circuit
could serve as an electronic die.
S. Tsilomanis,
Reservoir, Vic. ($15)
May 1994 33
Build an induction
balance metal locator
res
Main Featuerate.
ild & op
Easy to bu
wet or
r use over
Suitable fo c lu d in g b e a c h
d , in
d ry gro u n
.
sand
ground
to exclude
• Adjustment
effects.
control.
• Sensitivity
head
ication via
• Audible inlodudspeaker output
phone or
l detected.
when meta
uency
ases in freq rch
ea
s
• Sound incre
r
e
d
oves un
as metal m
head.
le for
nced hand
• Counterba. la
ease of use
•
•
34 Silicon Chip
Most do-it-yourself metal locators are
difficult to build & operate but not this one.
This unit is a cinch to put together & is just
the shot for finding coins, rings, watches &
other valuable metallic items.
By JOHN CLARKE
Of course, as well as finding those
more mundane items, a metal locator
can also be used to locate the metal
of our dreams – GOLD! But let’s be
realistic; not many of us are ever going to strike it rich on the goldfields,
although metal locators have detected
large nuggets for a few lucky prospectors.
No, a metal locator is more likely to
be used for fun and any profits made
from finding coins or jewellery are
likely to be quite modest. Then again,
you never know what might be hidden
under the next few square metres of
beach sand.
The big advantage of a metal locator
is that it saves lots of digging. One only
has to dig in locations where the metal
locator indicates the presence of metal.
Of course, not all finds will be of any
value except maybe for the recyclers
of cans and scrap aluminium.
To overcome this problem, some
metal locators incorporate controls
which discriminate against various
types of metals (eg, ferrous metals)
which are likely to be of little value.
Taken to the extreme, the ultimate
metal locator would find only things
of value. As expected, metal locators
which can discriminate against unwanted metals are usually expensive
and can be extremely complicated to
use. They are best left for experienced
prospectors.
The SILICON CHIP Induction Balance
Metal Locator is not a discriminating
type and is very easy to use. In fact,
there are just three control knobs: Volume, Ground and Sensitivity.
The first control sets the volume
of the output from the loudspeaker
or headphones. The second control
(Ground) is the most frequently
used – it adjusts the sound from the
loudspeaker so that it produces a low
frequency growl when the search head
is positioned over the ground. The
frequency will then increase sharply
when metal is detected.
The final control adjusts the sensitivity of the unit and sets the maximum depth at which an object will
be detected.
VR3
80kHz
OSCILLATOR
Q1
TRANSMIT
COIL
3V
BATTERY
SUPPLY
IC1b
DC LEVEL
(GROUND SET)
RECEIVE
COIL
Q2
AMPLIFIER
FILTER
RECTIFIER
VOLTAGE
STEPUP
IC3
+8.8V
SUPPLY
GAIN
VR2
IC1a
AMPLIFIER
VCO
IC2
AMPLFIER
IC1d Q3,Q4
HEADPHONE
OR
LOUDSPEAKER
Fig.1: this block diagram shows the main circuit elements of the Induction
Balance Metal Locator. The output from the receive coil assembly is rectified,
filtered & amplified by IC1a. IC1a in turn controls the output frequency from
voltage controlled oscillator (VCO) IC2. IC1b & VR3 set the DC bias on IC1a to
null out ground effects.
The handle assembly for the prototype was made
from 20mm-diameter electrical conduit, while the
search coil assembly is fitted to a baseboard which
is attached to a plastic dinner plate.
Operating principle
Most simple metal locators operate
on the principle of beat frequency oscillation (BFO). In this type of design,
the search coil is used as the inductive
component of an oscillator. When a
metallic object is brought near the
coil, the frequency of the oscillator
changes slightly due to the resulting change in the coil’s inductance.
This frequency change is detected
by mixing the oscillator frequency
with a fixed frequency to produce an
audible beat.
It is often claimed that BFO metal locators are able to detect the difference
between ferrous and non-ferrous metals. This is because the inductance of
the search coil increases with ferrous
metals and decreases with non-ferrous
metals, corresponding to decreasing
and increasing beat frequencies respectively.
In practice, however, the audible
beat can also increase for ferrous metals since eddy current flow in the iron
often masks out the effect of increasing
Typical Detection Distances
$2 coin
170mm
10¢ coin
200mm
Tin can
400mm
Wedding ring
150mm
May 1994 35
+8.8V
L3
TP1 GND
TP1
7
6
5
10
IC1c
IC1a
A
B
22k
.001
RECEIVE
COIL
L2
.0039
+7V
33k
.015
22k
B
1k
E
.0056
C
Q1
BC547
100k
L1, L2 : 50T, 0.6mm ENCU, 115mm DIAMETER
L3 : 33T, 0.4mm ENCU ON NEOSID 17-732-22 TOROID
1k
.022
B
GROUND
RANGE
VR1 1k
Q2
BC548
0.1
100
0.1
.01
D1
1N4148
12
GROUND
VR3
10k
LIN
100k
0.1
TRANSMIT
COIL
L1
36 Silicon Chip
E
C
VIEWED FROM
BELOW
330k
D2
1N4148
IC1b
LM324
13
4
14
0.1
K
390
9
SENSITIVITY
VR2
100k
LIN
+7V
1
11
33k
8
9
VCO IN
3
5
IC2
4046
8
11
7
10k
.068
6
VCO OUT
15
14
16
+7V
ZENER
4
100
16VW
VOLUME
VR4
10k
LOG
3V
INDUCTION BALANCE METAL LOCATOR
220
16VW
POWER
S1
3
2
100
IC1d
1
330
16VW
100
2
6
7
IC3
TL496C
5
Q4
BC328
B
B
Q3
BC338
8
POWER
LED1
C
E
E
C
0.1
47
16VW
2.7k
A
K
8W
SPEAKER
+8.8V
HEADPHONES
▲
Fig.2: the final circuit is built around
just three ICs. The transmit coil forms
a tuned collector load for oscillator
stage IC1a & its output is coupled into
receive coil L2 which is positioned
for minimum pickup in the absence
of metal. L2’s output is amplified
by common emitter stage Q2 &
rectified by D1 & D2 before being fed
to amplifier stage IC1a which then
drives the VCO. The output of the
VCO appears at pin 4 & drives audio
amplifier stage IC1d, Q3 & Q4.
inductance. It is therefore impossible
to discriminate between the two different types of metal.
By far the biggest disadvantage of
the BFO technique is that the search
coil must be shielded with a metal
screen to prevent reaction with the
ground. This significantly reduces the
sensitivity of the BFO type metal locator, which means that small objects
buried in a few centimetres of soil can
easily be missed.
To eliminate this problem, the
SILICON CHIP metal locator uses a
completely different operating principle. Unlike the BFO type, it uses
two coils in the search head, with
one coil driven by an oscillator. The
second coil is used to pick up signal
from the first.
During construction, the two coils
are positioned in an overlapping
fashion so that the second coil has
minimum pick-up. When metal is
introduced, however, the signal level
in the second coil increases. This
increased level is detected and the
resulting signal used to drive circuitry
to provide an audible indication that
metal is present.
This principle of operation is called
“Induction Balance” (also known as
“Transmit Receive) and it provides a
far more sensitive metal detector than
the BFO type. Its only disadvantage
is that the two coils must be carefully
aligned during construction.
The depth to which the metal locator can detect metals under given
conditions is set by the search head
coil diameter. The larger the diameter,
the deeper it will detect. However,
large search coils suffer from lack of
pinpoint accuracy in finding metals.
We opted for a medium-sized search
head which provides a good compromise between accuracy and depth.
Of course, there’s nothing to stop
you from experimenting with larger
search heads if depth is important.
Block diagram
Fig.1 shows the block diagram of
the Induction Balance Metal Locator. An oscillator operating at about
80kHz drives the transmit coil and
signal from this is picked up by the
receive coil. Amplifier stage Q2 boosts
the signal output from the re
ceive
coil and the signal is then rectified
and filtered to produce a smooth DC
voltage.
IC1a amplifies the DC voltage from
the filter. Its output is offset by a DC
voltage provided by IC1b and this, in
turn, is set by potentiometer VR3 (the
Ground control). In operation, VR3 is
set so that the DC output from IC1b
is equal to the DC voltage from the
filter, so that IC1a’s output normally
sits close to 0V (this is done to cancel
out ground effects).
When the search coils are brought
near metal, the signal level in the
receive coil increases. This results in
a higher DC voltage at the output of
the filter and this is then amplified by
IC1a to produce a control voltage for
the following VCO (voltage controlled
oscillator stage).
When IC1a’s output is at 0V (ie, no
metal is present), the VCO is off and
no signal is produced. Conversely, as
the search coils are moved closer to
metal, IC1a’s output rises and the VCO
increases its output frequency from
0Hz to about 4kHz. This signal is fed
to an amplifier stage (IC1d, Q3 & Q4)
and the resulting output then fed to a
loudspeaker or a pair of headphones.
Circuit details
Refer now to Fig.2 for the circuit
details.
Q1 and its associated components
form the transmit oscillator. This stage
oscillates by virtue of the tuned collector load provided by coil L1 and the
.0056µF positive feedback capacitor
between collector and emitter. The
1kΩ emitter degeneration resistor provides a small amount of DC negative
feedback to reduce sinewave distortion and provide a stable bias point.
The signal in L1 is coupled to receive coil L2. This latter coil is aligned
with L1 so that the induced signal is
normally at a minimum. The .0039µF
capacitor across L2 forms a resonant
circuit to ensure maximum pickup
sensitivity.
PARTS LIST
1 PC board, code 04305941,
159 x 83mm
1 front panel label, 90 x 180mm
1 plastic case, 190 x 100 x
40mm
1 2-metre length of 20mm-dia.
electrical conduit
3 90-degree 20mm conduit
elbows
3 20mm conduit U-clamps
1 20mm conduit joiner
1 50mm-long spring toggle bolt
1 180mm diameter plastic dinner
plate (eg, Decor #459)
1 180mm diameter x 3mm
Masonite sheet (or equivalent
material)
1 37-metre length of 0.6mm
enamelled copper wire
1 660mm length of 0.4mm
enamelled copper wire
1 100mm length of 0.8mm tinned
copper wire
1 1.5-metre length of dual
shielded cable
1 miniature SPDT toggle switch
(S1)
1 1kΩ miniature horizontal
trimpot (VR1)
1 100kΩ linear pot (VR2)
1 10kΩ linear pot (VR3)
1 10kΩ log pot (VR4)
1 Neosid iron powder toroidal
core 17-732-22
2 C-cell holders
2 1.5V C cells
1 6.5mm mono headphone
panel socket with switch
1 27mm mini 8Ω Mylar
loudspeaker
1 3mm red LED (LED1)
16 PC stakes
4 4BA x 25mm Nylon screws,
nuts & washers
The resulting signal from L2 is
AC-coupled to the base of Q2 which
is configured as a common emitter
amplifier. Its DC bias is set by the
33kΩ and 22kΩ base resistors. The
output from this stage is taken from
the wiper of VR1 which allows the
signal level to be adjusted from maximum (at the collector of Q2) down to
full attenuation (ie, when the wiper
is at the +7V rail).
Following VR1, the level-adjusted
5 6BA x 25mm Nylon screws,
nuts & washers
4 3mm x 5mm screws
8 2mm x 10mm screws & nuts
2 self-tapping screws
1 12mm OD rubber grommet
3 20mm OD knobs
1 75-gram tube of neutral cure
silicone sealant (eg. Selleys
Roof and Gutter Sealant)
1 container of conduit glue
Semiconductors
1 LM324 quad op amp (IC1)
1 4046 phase lock loop (IC2)
1 TL496C 1.5V-9V converter
(IC3)
2 BC548 NPN transistors
(Q1,Q2)
1 BC338 NPN transistor (Q3)
1 BC328 PNP transistor (Q4)
2 1N4148, 1N914 diodes (D1,D2)
Capacitors
1 330µF 16VW PC electrolytic
1 220µF 16VW PC electrolytic
1 100µF 16VW PC electrolytic
1 47µF 16VW PC electrolytic
1 1µF 16VW PC electrolytic
5 0.1µF MKT polyester
1 .068µF MKT polyester
1 .022µF MKT polyester
1 .015µF MKT polyester
1 .01µF MKT polyester
1 .0056µF MKT polyester
1 .0039µF MKT polyester
1 .001µF MKT polyester
Resistors (0.25W, 1%)
1 330kΩ
1 2.7kΩ
2 100kΩ
2 1kΩ
2 33kΩ
1 390Ω
2 22kΩ
3 100Ω
1 10kΩ
signal is AC-coupled to the rectifier
stage (diodes D1 and D2). The resulting DC output voltage from this stage
is then filtered by the 0.1µF capacitor
and applied to the non-inverting
inputs of IC1c and IC1a (pins 5 &
10 respectively). The 330kΩ resistor
provides a discharge path for the
capacitor.
IC1c functions as a unity gain buffer.
Its output at pin 7 provides a convenient test point (TP1) for measuring
May 1994 37
Fig.3: the PC board assembly is
straightforward but make sure that all
polarised parts are correctly oriented.
Inductor L3 is made by winding 33
turns of 0.4mm enamelled copper wire
on a small iron-powdered toroid.
VR2
VR3
3
2
1
8
7
S1
VR4
Q3
330uF
100
2.7k
0.1
22k
100k
1
100uF
1k
TP
GND
0.1
100
D1
0.1
22k
VR1
.022
8
.01
.001
33k
7
Q2
390
33k
330k
1k
D2
0.1
A
K
LED1
10k
.015
.0039
6
IC2
4046
1uF
TO
L2
38 Silicon Chip
.068
IC1
LM324
.0056
the output of the rectifier during the
setting-up procedure.
IC1a is wired as a non-inverting
amplifier with DC gain adjustable from
85 to about 340 using Sensitivity control VR2. The 1µF feedback capacitor
between pins 8 & 9 rolls off the AC
gain for frequencies above 5Hz at the
low gain setting of VR2, and above
1Hz for the high gain setting. This
roll-off reduces noise at the output of
the amplifier.
IC1b functions as a buffer stage for
the DC voltage set by VR3 at its wiper. This pot sets the DC voltage offset
for IC1a and functions as the Ground
control. Note that its voltage range has
been restricted by connecting a 100kΩ
resistor in series with it, to make the
setting less critical.
The output from IC1a appears at
5
4
1
TP1
Q1
Q4
100
220uF
1.5V CELL
47uF
L3
IC3
TL496
1.5V CELL
SPEAKER
0.1
1
TO
L1
6
5
4
100k
pin 8 and drives the VCO input of
IC2, a 4046 phase lock loop IC. In this
circuit, we are only using the VCO
section of the phase lock loop. The
oscillator output appears at pin 4 and
varies in frequency from 0Hz when
pin 9 is at 0V to about 4kHz when
pin 9 is at 7V. This upper frequency
is set by the 10kΩ resistor at pin 11
and the 0.068µF capacitor between
the pins 6 & 7.
The output signal from the VCO is
fed to Volume control VR4 and thence
to buffer stage IC1d. IC1d in turn drives
complementary transistor pair Q3 and
Q4, which act as high current drivers
for the headphones or loudspeaker.
Power for the circuit is derived from
two 1.5V “C” cells connected in series
to provide a 3V rail. This 3V rail is
boosted to 8.8V using IC3, a TL496
1
2
3
HEADPHONE
SOCKET
low-voltage switchmode IC. LED 1
provides power on/off indication.
IC2 has an internal 7V zener diode
at pin 15 and this regulates the supply
to 7V for the majority of the circuit.
The audio amplifier output stage (Q1
& Q2) is powered directly from the
8.8V rail, however. Note that the 8.8V
supply from IC3 is maintained until
the battery output drops below 2V.
Construction
A PC board coded 04305941 is used
to accommodate most of the parts,
including holders for the two 1.5V
“C” cells. This board fits neatly into a
plastic instrument case measuring 190
x 100 x 40mm and this is attached to
the top of a long carrying handle. The
coil assembly mounts at the other end
of the handle – see photos.
Fig.3 shows the board assembly
details. The order of assembly is not
critical but make sure that all polarised
parts are correctly oriented. These
parts include the ICs, transistors, diodes, LED and electrolytic capacitors.
Note particularly that three different
transistor types are used on the board,
so be careful not to get them mixed
up. LED 1 is mounted with its leads
left untrimmed so that it can later be
pushed into its mounting hole in the
top end panel.
Table 1 shows the resistor colour
codes but it’s also a good idea to measure the resistor values on your DMM
since some colours can be difficult to
decipher. Once these parts are in, fit
PC stakes to all external wiring points
on the board.
Coil L3 is made by winding 33 turns
of 0.4mm enamelled copper wire onto
a small iron-powdered toroid. Wind
each turn adjacent to the previous turn
and secure the completed toroid to the
PC board using a Nylon screw, washer
and nut through the centre hole. This
done trim the leads to length and tin
them with solder before connecting
them to the board.
Note: the wire is self-fluxing and
requires heat from your soldering iron
to melt back the enamel.
The two “C” cell holders are secured to the PC board using 2mm
screws and nuts at each corner. Use
the battery holders as templates to
mark out the holes on the PC board,
then drill the holes and mount the
holders in position. Make sure that
the holders are oriented with the
correct polarity and note that they
face in opposite directions to each
other – see Fig.3.
The terminal ends of each holder
are connected to the PC board using
short lengths of 0.8mm tinned copper
wire.
The PC board can now be installed
in the base of the case and secured
using 3mm screws which tap into the
integral corner standoffs in the case.
This done, attach the label to the lid
of the case and drill out the holes for
the control pots and power switch.
These parts can now be mounted in
position and firmly secured using their
lock nuts.
The top end piece of the case must
be drilled to accept the headphone
socket and LED, and to make a speaker
grill. This grill consists of a nine 3mm
holes directly in front of the speaker
COIL BASE-BOARD
180mm DIA. x 3mm THICK
MASONITE OR SIMILAR
RECEIVE COIL L2
TRANSMIT COIL L1
155mm DIA.
SHIELDED LEADS
Fig.4: this diagram shows how the two coils in the search head are mounted on
the baseboard. Adjust L2 for a signal null in the absence of metal by following
the procedure described in the test.
This view shows the search head assembly after the two coils have been secured
to the baseboard using neutral cure silicone sealant.
May 1994 39
TOGGLE SCREW
SPRING LOADED
TOGGLE NUT
JOINER END
(SLIDE OVER
TOGGLE WHEN
SCREW IS
STARTED)
11
MASONITE COIL
CARRIER
185mm PLASTIC
PLATE
ANGLE BRACKETS, CONDUIT
AND PLATE ASSEMBLED WITH
4BA NYLON SCREWS, NUTS
AND WASHERS
COMPRESS END OF
CONDUIT TO 10mm
ANGLE BRACKET
FASHOINED FROM
'U' CLAMP
1280
10mm DIA. HOLE
THROUGH CONDUIT
°
90ø ELBOW
Fig.5: follow these mechanical details when making up the handle &
search coil assemblies. Note that no metal parts can be used near the
search coils (use plastic brackets & nylon screws & nuts instead).
JOINER END
'U' CLAMPS
CASE
DIMENSIONS IN MILLIMETRES
19mm PLASTIC CONDUIT
Search head
415
10
40 Silicon Chip
cone. Deburr the holes using an oversize drill, then smear silicone sealant
around the edge of the speaker and
attach it to the panel.
The hole for the LED should also be
drilled to 3mm, so that the LED is a
tight fit. The bottom end piece of the
case is drilled with a single centre hole.
This hole is fitted with a small rubber
grommet and accepts the shielded
cable that runs between the PC board
and the two search coils.
Use light-duty hookup wire when
wiring up the potentiometers, head
phone socket, loudspeaker and on/
off switch – see Fig.3. The figure-8
shielded cable that runs to L1 and L2
can also be connected to the PC board
at this stage.
It’s now time to do a couple of quick
operational tests on the assembly so
far. To do this, install the two “C” cells
and switch on the power. Check that
the LED lights (if it doesn’t, it’s probably wired incorrectly) and that pin
8 of IC3 measures 8.8V with respect
to the TP GND pin. Check also that
the voltage at pin 15 of IC2 measures
about 7V.
If these voltages are not within 10%
of the nominated values, check the
circuit for faults and clear the problem
before proceeding further.
The search head, which consists of
coils L1 and L2, is the critical part
of the construction. As indicated
previously, these two coils must be
carefully aligned in order to ensure
that the metal locator functions
correctly.
Fig.4 shows the mounting details for
L1 and L2. Each coil is wound using
50 turns of 0.6mm enamelled copper
wire on a 115mm diameter former.
After winding, wrap each coil tightly
with two layers of insulation tape
(note: the wire ends should exit from
the same position).
The two coils are mounted on a sheet
of Masonite which is cut to form a disc
180mm in diameter. Before mounting
the coils, draw a 115mm-diameter
circle on one side of the mounting
sheet, then drill a hole in the centre
to take a 4BA screw. The two coils can
now be bent to shape and positioned
as shown in Fig.4.
The two coils must now be carefully
aligned to ensure mini
mum signal
pickup in L2. This is done as follows:
(1). Temporarily connect the shield
The battery holders are each secured to the PC board using four small machine
screws & nuts. Twist the leads to the front panel controls as shown & bind them
with a cable tie to minimise the chances of a lead coming adrift.
ed cable to the coils and make sure
that the assembly is well away from
any metal items.
(2). Connect a voltmeter between
TP1 and TP GND on the PC board and
apply power. Rotate VR1 (Ground)
fully clockwise and check for a
high-frequency tone from the speaker
if the volume control is wound up. If
no tone is present, rotate the Ground
and Sensitivity controls fully clockwise and adjust L1 and L2 until there
is a tone. If no tone can be obtained,
check the PC board for wiring faults.
(3). Turn down the volume and
adjust L2 relative to L1 for a minimum reading on the voltmeter. This
should be somewhere between 0.8V
and 1.2V. You will need to bend the
coils at the L1 and L2 intersection in
order to obtain the lowest DC voltage
at TP1. Note that the coils should not
go outside the 155mm diameter limit.
(4). Check that the voltage at TP1
increases if a piece of metal is now
brought close to where the coils intersect. If the voltage falls, move the coils
together until the voltage rises when
the metal object is introduced.
(5). Turn up the Volume and adjust
the Ground control for a low-frequency
growl when no metal is near the coils.
Now check that the tone frequency
increases when metal is brought near
the coils.
Once you are satisfied with the coil
locations, they can be secured in position with silicone sealant. This process
will take time, so do not rush the job.
First, unsolder the shielded cable
and secure the transmit coil (L1) in position flat on the mounting plate. The
receive coil (L2) can then be secured
as well, but only around the 115mm
diameter perimeter section. Do not
apply any sealant to the overlapping
May 1994 41
The case containing
the electronic circuitry
is mounted near the
top of the handle as
shown here. Note the
holes drilled in the
end panel to allow the
sound to escape from
the loudspeaker.
section of L2 at this stage so that you
can make fine adjustments later on
when the rest of the sealant has dried.
This means leaving the assembly for
at least 24 hours.
Mechanical details
Fig.5 shows the general mechanical
details of the entire metal locator assembly. It uses 20mm-dia. electrical
conduit and 90° elbow sections for
the handle assembly, while the search
coil assembly baseplate is attached to
a plastic dinner plate.
Two plastic right-angle brackets are
used to secure the plastic plate to the
handle. These two brackets are made
by cutting the curved section out of
a U-clamp and then drilling holes
in the brackets to accept 4BA Nylon
screws. Note: metal parts must not be
used anywhere near the search coil
assembly.
The next step is to compress the
end of a 1280mm length of conduit
in a vyce until it is 10mm thick. Once
this has been done, the right angle
brackets can be attached to the conduit
using a 25mm-long Nylon screw and
the brackets then used to mark out
their mounting holes on the plastic
plate – see Fig.5.
Drill these holes to size, along with
a further hole exactly in the centre of
the plastic plate. You will also have
to drill a couple of holes in the side
of the plate (in line with the handle)
to accept the leads from the shielded
cable.
The plastic plate can now be fastened to the right angle brackets using
4BA Nylon screws and nuts. Cut off
Fig.6: this is the full-size etching pattern for the PC board. Check the board for defects before installing any of the parts.
42 Silicon Chip
any excess screw lengths using a sharp
knife or sidecutters.
The other sections of conduit can
now be cut to size and assembled as
shown in Fig.5.
Note that the bottom end of the top
handle section is secured to the main
section using a toggle screw (see detail). Shape the end with a round file
so that it mates neatly with the main
section, then drill the holes to accept
the toggle screw and its spring-loaded nut. This done, cut a sleeve from
one end of an elbow piece and slide
this over the shaped end of the top
handle section so that it clears the
10mm holes.
The toggle screw can now be installed and the sleeve slid down over
the 10mm holes after the nut is started. When the screw is tightened, the
ends of the toggle should catch on the
bottom edges of the 10mm holes to
provide a secure assembly.
Once the basic handle assembly is
completed, the instrument case can
be attached to it using two plastic
U-clamps. Note that the bottom clamp
goes over a sleeve which is cut from
the other end of the elbow piece mentioned above. The top clamp goes over
the sleeve on the end of the adjacent
90° elbow piece.
Use the U-clamps to mark out the
holes on the bottom of the case, then
remove the PC board and drill the
holes to accept 6BA Nylon screws.
This done, mount the case in position,
remove the excess screw lengths and
remount the PC board. The U-clamps
are secured to the handle using
self-tapping screws.
The next step is to drill a hole in
the handle just below the instrument
case and another in the bottom of the
handle adjacent to the search head.
The bottom end of the handle is compressed to about 10mm thick by squeezing
it in a vyce. It is then attached to the cover plate using two plastic right-angle
brackets & Nylon screws & nuts.
This photograph shows how the case assembly is secured to the handle using
two U-clamps. The sleeve under the bottom U-clamp is obtained by cutting it
from one end of a 90° elbow piece.
RESISTOR COLOUR CODES
❏
❏
❏
❏
❏
❏
❏
❏
❏
❏
No.
1
2
2
2
1
1
2
1
3
Value
330kΩ
100kΩ
33kΩ
22kΩ
10kΩ
2.7kΩ
1kΩ
390Ω
100Ω
4-Band Code (1%)
orange orange yellow brown
brown black yellow brown
orange orange orange brown
red red orange brown
brown black orange brown
red violet red brown
brown black red brown
orange white brown brown
brown black brown brown
5-Band Code (1%)
orange orange black orange brown
brown black black orange brown
orange orange black red brown
red red black red brown
brown black black red brown
red violet black brown brown
brown black black brown brown
orange white black black brown
brown black black black brown
May 1994 43
and adjust the Ground control for a
low-frequency growl when no metal
is near the coils.
(2). Adjust the receive coil (L2)
by bending it over the transmit coil
(L1) until the voltage at TP1 is at a
minimum (this gives the correct null
point).
(3). Disconnect the shielded cable
again and fully secure L2 by applying
additional silicone sealant. Wait until
this sealant dries, then reconnect the
shielded cable leads and cover the
connections with insulation tape. Use
a final coating of silicone sealant to
secure the leads.
(4). When the sealant has fully
dried, attach the search coil assembly
to the plastic cover plate lid using a
4BA Nylon screw and nut. Finally,
run some silicone sealant around the
edge of the plate to produce a watertight assembly.
INDUCTION BALANCE
METAL LOCATOR
POWER
SENSITIVITY
Using the metal locator
ON
.
.
VOLUME
.
.
.
.
.
+
.
.
.
.
.
.
.
.
POWER
.
.
+
.
.
.
.
.
.
+
.
.
.
.
.
HEADPHONES
.
.
GROUND
.
.
.
+
OFF
SPEAKER
Fig.7: this full-size artwork can be used as a drilling template
for the front panel or used to make your own label.
The shielded cable can now be fed
down the inside of the conduit and
out through the bottom hole, at which
point it is separated and the leads
connected to the coils.
Make sure that each lead goes to its
designated coil. If you get the leads
transposed, the performance will be
compromised.
Finally, the conduit fittings can be
44 Silicon Chip
glued with PVC adhesive and allowed
to dry.
Assuming that the silicone sealant
on the search coils is dry, you are now
ready for the final alignment procedure. The step-by step procedure is
as follows:
(1). Connect a voltmeter between
TP1 and TPGND on the PC board and
apply power. Turn up the Volume
Once the sealant has fully cured,
the metal locator is ready for use.
You can hold the metal locator with
one hand near the lower section of
the handle, at the balanced position,
and the other hand near the top end
of the handle. The search head should
be swivelled so that it is parallel to
the ground.
Adjust the Ground control so that
the sound is just a low frequency growl
and sweep the search head across the
ground. When metal is located, the
frequency will increase.
Normally, the sensitivity control
will be set at its maximum. However,
in some cases, the sensitivity may
need to be reduced if, for example, the
ground is mineralised or if you only
want to find larger objects.
VR1 is normally set to maximum
(ie, fully clockwise). It should only be
adjusted if the Ground control needs
to be set almost fully anticlockwise to
obtain a low-frequency tone (it’s just a
case of adjusting VR1 to provide a reasonable range for the Ground control).
Finally, note that the Ground control
will have to be readjusted for changes
in ground composition (eg, if you go
from dry sand to wet sand), or if the
distance between the search head
and ground changes. For this reason,
it’s best to keep the search head at a
consistent height. That said, the unit
is extremely easy to use and you’ll
soon get the hang of it by practising
SC
on a few metal coins.
SILICON
CHIP
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has requested that the page be removed to
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Please feel free to visit the advertiser’s website:
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CHIP
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has requested that the page be removed to
prevent misunderstandings.
Please feel free to visit the advertiser’s website:
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CHIP
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more than likely that it contained advertising
which is now out of date and the advertiser
has requested that the page be removed to
prevent misunderstandings.
Please feel free to visit the advertiser’s website:
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CHIP
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more than likely that it contained advertising
which is now out of date and the advertiser
has requested that the page be removed to
prevent misunderstandings.
Please feel free to visit the advertiser’s website:
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CHIP
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more than likely that it contained advertising
which is now out of date and the advertiser
has requested that the page be removed to
prevent misunderstandings.
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May 1994 53
If you’re always losing the Monopoly
dice, then this could save you several
hours of guests climbing the walls!
It uses just four CMOS ICs, has auto
power-off & even imitates the dice face!
Build this
Dual Electronic Dice
By DARREN YATES
There’s no doubt about it! Whenever
you go looking for your favourite board
game, the odds are that the dice have
been pinched for use somewhere else
or are just plain missing.
There are few more ugly scenes in
life than a room full of guests, a Monopoly board and NO dice!
So before your guests start looking
for a likely piece of rope, a roof beam
and a chair, you can either somehow
produce two dice or pull out your
newly-built piece of electronics! Not
only will you save your skin but you’ll
be able to wow them with your skill
and expertise.
This electronic dice uses just four
CMOS ICs, 14 LEDs and a handful of
other components. It runs from a 9V
battery and au
tomatically switches
itself off 30 seconds after use.
You simply press the button and
the dice start “rolling”. Once you let
the button go, the dice then begin to
slow down and finally come to rest
on one of six “faces”. Both dice are
independent of each other so there’s
no chance of ending up with “doubles” all night.
Circuit diagram
Let’s take a look at the circuit dia-
The button in the middle of the circuit board controls the roll of the dice. You
can mount the LEDs on the circuit board as shown here, or mount them on the
lid of a case & connect them to the PC board via flying leads.
54 Silicon Chip
gram – see Fig.1. The four ICs are two
CMOS 4015 dual 4-bit shift registers
and two CMOS 4093 quad 2-input
Schmitt-triggered NAND gates. If you
look carefully, you’ll see that there
are two identical halves to the circuit, both controlled by pushbutton
switch S1.
Starting off, when the ROLL button
S1 is pressed, the 33µF capacitor is
shorted while the 47µF capacitor is
shorted via diode D3. Once S1 is released, both capacitors begin to charge
via their associated resistors to the 0V
rail. However, they do so independently. Because the time constant of the
33µF capacitor and its 68kΩ resistor
is less than the 47µF capacitor and its
1MΩ resistor, the voltage at the anode
of diode D3 will always be lower than
that on its cathode. This is important,
as we’ll explain later.
Pressing switch S1 also allows the
.01µF capacitors con
nected to the
inputs of IC1a and IC3a to be charged
via their associated 1MΩ resistors.
Looking at just IC1a for the moment,
these components along with the
10kΩ resistor and diode D1 make
up a Schmitt trigger oscillator with a
difference.
As the 33µF capacitor charges, it
also supplies current through the 1MΩ
resistor to charge the .01µF capacitor.
This happens quite rapidly and once
the capacitor voltage rises above IC1a’s
threshold, its output at pin 4 goes
low. Diode D1 now becomes forwardbiased and discharges the capacitor
through the 10kΩ resistor. Once the
D1
1N914
10k
1M
5
6
.01
.01
ROLL
S1
33
14
7
470
16VW
4
9
IC1a
4093
7
IC2a
C 4015
R
10k
8 6
47
1k
14
LED4
IC1c
13
1k
A
11
.01
.01
D3
1N914
68k
5
Q0
D
LED5
12
A
LED6
LED7
K
IC1b
3
K
YELLOW
10
1M
9V
+9V
15 16
D
13
Q0
1
12
C IC2b
Q1
11
Q2
R
IC1d
1
2
9
8
1.5k
1.5k
1k
A
LED1
YELLOW
A
K
LED2
YELLOW
LED3
YELLOW
K
+9V
D2
1N914
10k
10k
1M
1
2
.01
.01
14
7
3
9
IC3a
4093
7
IC4a
C 4015
5
Q0
D
15 16
D
13
Q0
1
12
C IC4b
Q1
11
Q2
R
R
10k
8 6
1k
14
4
.01
.01
IC3c
5
LED12
RED
6
K
10
11
IC3b
9
1.5k
1.5k
K
LED13
RED
LED14
RED
K
8
1k
A
LED8
RED
A
K
LED9
RED
LED10
LED10
RED
DUAL LED DICE
K
Fig.1: the circuit uses two identical sections. IC1a & IC1b form free running
oscillators & these clock 4-bit shift registers IC2a & IC2b respectively. These then
clock IC2b & IC4b (via IC1b & IC3b) to drive the LEDs (LEDs 1-7 & LEDs 8-14).
capacitor voltage falls below the lower
threshold of the gate, its output swings
high again, forcing the diode off and
allowing the capacitor to once again
charge via the 1MΩ resistor.
While this all happens though,
A
IC3d
13
12
A
1k
A
LED11
LED11
RED
the voltage at the negative end of the
33µF capacitor is slowly dropping as
it charges up. This means that there is
less current flowing through the 1MΩ
resistor to charge the .01µF capacitor
so that it takes longer and longer to
charge up. The end result is that the
short negative-going pulses from the
output of IC1a take longer and longer
to appear so that its frequency gradually decreases until it eventually stops
altogether. This is how we generate
the “slowing down” effect of the dice
rolling.
At this point, some of you might be
May 1994 55
LED7
LED4
A
K
A
LED1
LED2
A
K
A
LED11
K
A
A
A
K
LED3
K
LED14
LED9
K
S1
A
K
LED10
A
K
A
K
K
LED8
LED6
A
LED13
K
A
K
A
LED12
A
K
K
LED5
470uF
9V
BATTERY
.01
1k
1k
1.5k
1k
1k
1.5k
1k
1k
10k
IC2
4015
IC4
4015
.01
10k
D2
1M
1M
1M
1
1
47uF
68k
.01
IC1
4093
D1
10k
33uF
10k
1
D3
IC3
4093
.01
1
Fig.2 (above): try to keep the LEDs at a consistent height when
installing them on the PCB. You can do this by cutting a length of
5mm-wide cardboard & then using this as an alignment tool. Fig.3
(below) shows the full-size etching pattern for the PC board.
wondering why we have chosen the same
components for the two oscillator sections
of IC1a and IC3a. Because of component
tolerances, no two components will ever
have exactly the same value so both oscillators will run at a different frequency. This
ensures that we don’t always get the same
number appearing on both dice repeatedly.
Note that this is still possible by chance,
of course.
From here on, we’ll just discuss that
part of the circuit which involves IC1 and
IC2. The other half of the circuit works in
exactly the same way.
The pulses from IC1a are used to clock
the rest of the circuit and simulate the roll
of a real dice, whereby the LEDs cycle very
rapidly at first and then slow down to a
complete stop to give a static display.
These clock pulses are fed to pin 9 of
IC2a, a 4-bit shift register which is connected up as a D-type flipflop. IC2a is made
to function as a flipflop by connecting its
Q0 output at pin 5 to the D-input at pin 7
via inverter IC1b. The Q0 output of IC2a
is also used to drive LED 1 which is on for
all odd-numbered displays; ie, “1”, “3”
and “5”.
The output of IC1b is also used to clock
the second 4-bit shift register, IC2b. The
D-input of IC2b is tied to the positive rail so
that on each clock pulse, a “high” is shifted
to each output from Q0 to Q1 to Q2 (pins
13, 12 & 11 respectively).
Pin 11 drives LEDs 2 & 3, pin 12 drives
LEDs 4 & 5 and pin 13 drives LEDs 6 &
7. These LEDs combine to produce the
even-numbered displays “2”, “4” & “6”.
When Q0 of IC2b goes high, LEDs 6 & 7
come on to produce displays “2” and “3”.
On the next clock pulse, Q1 also goes high
to produce the “4” and “5” displays, as
LEDs 4 and 5 are now also lit.
On the third clock pulse, Q2 goes high
as well, lighting LEDs 2 and 3 to produce
the “6” display.
Dice sequence
Let’s now follow the dice sequence.
When the first clock pulse from IC1a
arrives, Q0 of IC2a goes high, producing
the “1” display. The next pulse pulls it
low again which sends the output of IC1b
high. This clocks IC2b and sends its Q0
output high, turning on LEDs 6 and 7 to
produce a “2”.
The following pulse toggles IC2a again,
sending Q0 high and lighting LED 1 to
produce a “3”. The output of IC1b is a
falling edge this time so nothing happens
to IC2b.
The next clock pulse toggles IC2a again,
turning off LED 1 but clocking IC2b so that
56 Silicon Chip
Q1 of IC2b also comes on to produce
the “4” display. The clock pulse after
that toggles IC2a again, turning on LED
1 again to produce a “5”.
The next clock pulse toggles IC2a
off again and clocks IC2b so that the
last of the LEDs now light (via IC2b’s
Q2 output) to produce a “6”. This last
high also pulls one of the inputs to
IC1d high and when the next clock
pulse arrives, Q0 of IC2a goes high.
This pulls the output of IC1d low.
This low output is fed to pin 12
of IC1c. The other input to the gate
is controlled by the 47µF capacitor
we mentioned right back at the start.
While this continues to charge up, pin
13 is held at a logic high and so IC1c
acts as an inverter.
The low input that has just come
from IC1d thus forces the output of
IC1c high, which resets IC2b. Output
Q2 of IC2b now goes low again and
the reset condition is removed (ie,
the reset pulse is quite narrow). The
RC time constant on pin 6 of IC2a
prevents this register from also being
reset at this stage. This is because the
.01µF capacitor doesn’t have sufficient
time to charge.
IC2a now toggles again so that its
Q0 output goes high, lighting up LED
1 again, and so the cycle continues.
While this is happening, the 47µF
capacitor charges until the voltage at
pin 13 of IC1c drops to a logic low. At
this point, the output of IC1c is held
high regardless of the pin 12 input
level and thus both IC2a and IC2b
are reset.
All LEDs are now turned off and the
current consumption is down to only
a couple of microamps, allowing us to
do away with a power switch.
Once the ROLL button is pressed,
the circuit comes alive and the whole
process begins again.
Power is supplied by either a 6V
or 9V battery. The supply line is de
coupled via a 470µF capacitor which
also supplies the current surges re-
quired by the circuit when the LEDs
are being driven.
Construction
All of the components for the Dual
LED Dice are installed on a PC board
measuring 102 x 112mm and coded
08105941.
Before you begin any soldering,
check the board thoroughly for any
shorts or breaks in the copper tracks.
These should be repaired with a small
artwork knife or a touch of the soldering iron where appropriate.
Once the board appears to be OK,
you can begin by installing the wire
links. Make sure that you follow the
overlay wiring diagram so that they are
installed in the correct place.
Next up, continue on with the resistors and diodes, followed by the
capacitors and ICs. As most of the
components are polarised, be careful
to make sure that they are installed
correctly.
After that you can install the LEDs.
This should be relatively straightforward since all of the LEDs face the
same way.
Finally, install the switch and the
battery snap. You can use a 9V battery
or a battery holder with four 1.5V AA
cells (to give 6V).
PARTS LIST
1 PC board, code 08105941,
102 x 112mm
1 snap-action PCB switch (S1)
1 9V battery snap
1 6V or 9V battery (see text)
4 10mm x 3mm tapped spacers
Semiconductors
2 4093 Schmitt NAND gate ICs
(IC1,IC3)
2 4015 dual 4-bit shift registers
(IC2,IC4)
3 1N914 signal diodes
(D1,D2,D3)
7 5mm yellow LEDs (LEDs 1-7)
7 5mm red LEDs (LEDs 8-14)
Capacitors
1 470µF 16VW electrolytic
1 47µF 16VW electrolytic
1 33µF 16VW electrolytic
4 .01µF 63VW MKT polyester
Resistors (0.25W, 5%)
3 1MΩ
2 1.5kΩ
1 68kΩ
6 1kΩ
4 10kΩ
Miscellaneous
Machine screws, solder, tinned
copper wire.
Testing
Check your work carefully for any
components which are incorrectly
installed or for any solder splashes
causing shorts between the tracks.
Once everything looks good, connect up your battery and press the button. You should see the LEDs initially
flashing quite quickly and then slow
down to a complete stop. After about
30 seconds or so, the display should
then turn off.
You’ll need to do this a number of
times to make sure that all the displays
appear. If any LEDs fail to light up,
check that you have them installed
correctly. Note that for those LEDs
which are in series with each other,
you only need to have one installed
incorrectly for both not to work.
Cutting the board
If you prefer, you can install this
project in a plastic zippy box by cutting the board through the middle and
then soldering wire links between the
two boards to fold them over. This is
best done before you start construction and will make the assembly that
much smaller.
OK, you’ve had your fun. Now you
can get down to serious work with the
SC
board games.
RESISTOR COLOUR CODES
❏
❏
❏
❏
❏
❏
No.
3
1
4
2
6
Value
1MΩ
68kΩ
10kΩ
1.5kΩ
1kΩ
4-Band Code (1%)
brown black green brown
blue grey orange brown
brown black orange brown
brown green red brown
brown black red brown
5-Band Code (1%)
brown black black yellow brown
blue grey black red brown
brown black black red brown
brown green black brown brown
brown black black brown brown
May 1994 57
SERVICEMAN'S LOG
Always look on the grim side
That heading describes the pessimistic service
man. When he encounters a fault which looks
easy, he automatically assumes it’s going to be
hard. And when he encounters one that looks
hard, he is quite certain it’s going to be hard. Of
course, he’s often right – but not always.
My first story this month concerns
an HMV colour set, model B4803A,
the “48” signifying 48cm and the
“A” an Australian version. But more
exactly, the chassis is actually made
by JVC.
This model has been around for
about 15 years and I am fairly familiar
with it. So, when the lady owner rang
to say she had a problem, I assumed
that it would be something I could
handle without too much trouble. I
asked her in what way the set was
misbehaving and she replied that
while there was a watchable picture
on the screen, it was, in her words,
“very red”.
I pondered on this briefly, considered several possibili
ties without
reaching any conclusion, then simply
advised her to bring the set in. Even
then I didn’t anticipate anything
58 Silicon Chip
unduly difficult. But then, one never
does.
Anyway, the set was duly delivered and I put it up on the bench and
switched it on. The result was more or
less as the customer had described it;
the picture was complete and it was
only the colour that was wrong.
But it wasn’t red, as she had thought.
It was magenta, a colour which is often
mistaken for red, the difference being
rather subtle. But it is an important
difference, because it immediately
pinpointed the real nature of the fault
– loss of green, leaving red and blue
which mix to make magenta.
Well that seemed to simplify the
situation; all I had to do was find out
why there was no green. And, while
there could be several reasons, failures
of this kind are not normally difficult
to track down.
High voltage
My first check was the voltage on the
collector of the green drive transistor
Fig.1: this diagram shows the colour decoder IC (IC302) and the neck-board circuitry for the HMV B4803. The
picture tube driver transistors (X101-X103) are to the right, with the green driver transistor (X103) at the bottom.
Pin 10 of IC302 connects to pin 7 of IC301 (not shown) via two resistors.
(X103), which drives the picture tube
green cathode. This normally sits at
around 145V, with roughly similar
values on the red and blue drives.
However, this one measured around
180V which is the supply rail voltage, meaning that this transistor was
not drawing any current. As well as
suggesting a fault in the drive system
generally, this also cleared the picture
tube of suspicion.
Further checking revealed that the
voltage on the base of X103, normally
around 7.4V, was only a fraction of
this. And this in turn suggested two
possibilities, both of which I had
experi
enced previously: (1) a fault
in the drive transistor itself (they can
develop some very funny faults); or
(2) a more subtle fault around the colour matrix chip, IC302 (TA7622AP),
which provides the base voltages for
the three driver transistors.
It was toss up but the driver transistor is quite easy to change and I had
one on hand, so I tried that first. But
all that did was clear the transistor;
replacing it made no difference.
My next step was to take a look at
the circuitry around IC302. The three
pins involved are pin 2 (red), pin 4
(green) and pin 6 (blue). But there is
a nasty trap here for unsuspecting
players; not shown on the circuit is
a modification consisting of three
clamping diodes, one for each pin.
These are designated on the board as
D403, D404 and D405. In each case,
the anode goes to the pin and the
cathode to the 12V rail.
These diodes have a nasty habit of
going leaky. And when one does, it
can produce symptoms very similar to
these. Again it was a relatively simple
job to clarify the point. I pulled the
suspect diode out and, rather than
waste time testing it (such tests are not
always conclusive anyway), simply
fitted a new one.
But again, I drew a blank; the problem was still there. Which didn’t leave
much, except the IC. I went over the
circuit, seeking inspiration as to any
other likely cause but without success;
it just had to be the IC.
Good news & bad
Fortunately, I had this particular
IC in stock and, with only 16 pins
involved, it was a simple job to fit a
new one. And I confidently expected
that this would finally cure the fault.
How naive can one be?
All I had done was create a good
news/bad news situation. The good
news was that I had cured the original
fault. There was now normal voltage
on pin 4 of IC302 (and on the base of
transistor X103) and all signs of the
magenta cast had vanished.
The bad news was that I now had a
monochrome picture – there was no
colour. By very carefully adjusting
the fine tuning control, I eventually
brought up some colour but it was
still a long way from being right. There
were several things wrong with the
picture, some of them hard to describe.
For example, there were patches where
there was no colour, or where one particular colour was absent, to nominate
a couple of minor faults.
And I classified those faults as
minor because the major one was a
real beauty; the colour pattern was
displaced by about 30mm to the right
of the monochrome image to which
it belonged.
It produced a weird effect. The offair picture I was using happened to be
coverage of a one-day cricket match,
in which the fielding side was wearing bright yellow uniforms. Imagine,
if you can, a fieldsman, portrayed in
monochrome, chasing a ball across
the screen from right to left, with the
yellow of his uniform running several
steps behind in what looked like a
vain attempt to catch up. And then,
when he turned and ran the other way,
it looked as though he was trying to
catch the colour!
To the casual observer, it would
probably have looked outrageously
funny. To me, faced with the task of
May 1994 59
Fig.2: the power supply circuitry for the National TC-2658 colour TV set.
The mains power enters on the left (blue & brown), while the bridge rectifier
(D833-D836) is in the centre of the diagram. To the right of the bridge rectifier is
switching transformer T801, while IC801 is at extreme right. Test point TPE1 is
below IC801 & should normally measure 113V.
finding out what was causing it, the
humour of the display was somehow
lost. More to the point, I didn’t have
a clue as to where to even start looking for a fault like this. I had never
seen, or even heard of, anything like
it before.
To add to my confusion, there was
the question as to whether there had
been two faults in the set when it
came to me: (1) the obvious loss of
green; and (2) this “new” fault. It
was quite possible that the second
fault had originally been masked by
the obvious loss of green but, to be
truthful, I hadn’t taken all that much
notice of the picture’s finer points. I
had simply diagnosed loss of green
and gone on from there.
Alternatively, was there only one
fault originally, meaning that I had
created the second fault in curing
the first one? It was all very disconcerting.
Anyway, for want of any better
ideas, I went around IC302 with the
meter, checking the voltage on each
pin. Everything tallied very closely
with the circuit values until I came to
pin 10. This is shown on the circuit as
measuring a mere .08V but the meter
was reading somewhere around 5V
plus. I didn’t note it precisely; just
60 Silicon Chip
that it was grossly wrong.
Could the replacement for IC302
be faulty? It was hardly likely, seeing
it was a brand new unit. But stranger
things have happened and, as I had a
second one on hand, I decided to make
certain. So IC302 was changed for a
second time. Result – exactly the same
as before. That clinched it; it obviously
wasn’t IC302.
Next, I began tracing the circuit from
pin 10 and, after running up a couple
of blind alleys, I came to pin 7 of IC301,
the chroma IC. This is marked with a
similar value, in this case .09V, but
the actual voltage was grossly high
here too, being similar to that on pin
10 on IC302.
I checked the circuit carefully for
any other likely source of the spurious
voltage and the only other possibility
seemed to be diode D201, which might
be leaky. To make sure, I disconnected
it but that made no difference. So as
far as I could see, IC301 was about the
only possible place, apart from IC302
itself, from which the spurious voltage
could originate. And IC302 had been
replaced twice.
The next logical step was to change
IC301. The only snag was that I didn’t
have one in stock and so one had to be
ordered. I also ordered another IC302
while I was about it. In the back of my
mind was the thought that a fault in
IC301 might have damaged IC302, so
it was best to be on the safe side.
The two ICs arrived a couple of days
later and, full of confidence, I lost no
time in replacing IC301. It came as a
nasty shock when this had no effect;
the symptoms remained as weird as
ever and the same spurious voltage
was present.
When I’d regained my composure,
I did something which, in hindsight,
I realised I should have done much
earlier; I separated the two pins from
each other. And so, at long last the
truth was revealed; pin 7 of IC301
reverted to normal, while pin 10 of
IC302 retained the spurious 5V.
Initially, considering that IC302
had already been changed twice,
I was loath to accept that the fault
was actually in this IC. Instead, I
tried to think of some external error
which would cause it to produce this
voltage.
But I drew a mental blank; I could
think of nothing that would do this. So
there was only one thing left; change
IC302 for the third time. I couldn’t
believe that this was the answer but
I didn’t know what I would do if it
wasn’t.
But it was the answer; the new IC
cured the fault completely. And that,
from a practical point of view, was the
end of the story. The set was returned
to the owner and everyone was happy.
Well, I was happy the problems had
been solved but less happy and very
puzzled about the IC situation.
Statistically, ICs are very reliable
and I cannot recall the last time that a
new IC proved faulty. As for two new
ICs being faulty – well, that would
suggest lottery odds. But there was the
evidence on the workbench.
Granted, they had been in stock for
a couple of years but that is hardly
relevant. The only other point of note
is that they both carried the same batch
markings and, not surprisingly, these
differed from those on the one I had
just bought.
So, if it was a batch problem, how
many other unfortunate servicemen
had been driven half way up the wall,
as I had been?
Strange symptoms
My next story is not an especially
profound one but is of interest because
of an unusual fault in a particular
component. But the fault was not only
unusual; it also created some very
strange symptoms.
On the other hand, no great detective work was needed to track it down.
In fact, this was one of those rare occasions when a job which looked as
though it was going to be hard turned
out to quite simple, rather than the
other way round.
The set was a National colour TV
set, model TC-2658, which is fitted
with an M14 chassis. This chassis,
with minor variations, has been used
in a number of National models and
I have dealt with it several times in
the past.
The customer’s complaint was simply that the set had failed completely
and, when I put it up on the bench
and turned it on, this appeared to be
true enough, at least from his point
view; there was no picture and no
sound.
But there were some signs of life.
For starters, the power supply was
giving forth a high pitched squeal of
distress; the kind of sound usually
associated with a gross overload. And
this, initially, was what I suspected
was happening.
My first check was to measure the
HT rail voltage, which is most conveniently done at test point TPE1 in
the power supply section. The normal
value at this point is 113V but, in this
case, it was reading 163V. Apparently,
the power supply was underloaded
rather than overloaded and the sounds
of distress were, somehow, due to the
excessive voltage it was generating.
My first reaction to the excessive
voltage was to assume that some part
of the circuit – most probably the horizontal output stage – was not drawing
current. And, in turn, I suspected that
the horizontal output transistor, Q501,
might have gone open circuit. So this
was pulled out and checked.
No joy. It checked out perfectly and
there was certainly no sign of an open
circuit.
So what now? As I have pointed out
before when discussing this chassis, it
is fitted with an elaborate protection
circuit. This is designed to detect
over-current and over-voltage situa
tions in various parts of the circuit
and to shut the set down to avoid more
serious damage if a fault occurs. In this
case, it was obvious that the excessive
voltage had caused the protection circuit to shut the set down.
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May 1994 61
SERVICEMAN'S LOG – CTD
tant point was that the set was work
ing, with no obvious faults or signs
of distress.
This threw suspicion right back
to the power supply; the HT voltage
was not wrong because of any lack of
loading in the set, so it had to be the
power supply itself that was at fault.
The heart of the power supply is an
STR50113-M regulator chip (IC801).
These devices are no stranger to me;
while their failure rate is probably not
excessive, I’ve had enough trouble
with them to put me on alert. Except
that I had never seen a fault like this
before – usually, they develop an internal short to chassis, which takes out
a 4.7Ω safety resistor (R841).
Nevertheless, I could find nothing
else in the power supply circuit which
could possibly account for the excessive voltage. So out came IC801 – it has
only five pins – and in went a new one.
I switched the set on again – still
on the Variac – and found that the HT
voltage was now low. I then wound the
input up to 240V, still on the alert for
any signs of distress, but there were
none. More importantly, I now had a
HT rail that was spot on 113V and the
set was running perfectly.
One of the easy ones
From a practical point of view, the
existence of the pro
tection circuit
means that this has to be disabled in
order to track down the fault. Only
then will the set try to function normally and display the fault in its true
colours.
Disabling this circuit is simple
enough. Resistor R536 (100Ω) connects to the emitter of transistor Q503,
which forms part of the protection
circuit, and removing this is all that
is necessary.
Risk of damage
But there is more to it than that. If the
fault is a potentially destructive one,
disabling the protection circuit could
cause additional damage. And that
was exactly the situation here; with
the power supply generating 163V on
the HT rail, the risk of damage if the
set was allowed to function with this
voltage was quite high.
Fortunately, the solution is fairly
simple. In such circumstances, I feed
the set from a Variac. This is set initially at a suitable low voltage and
then gradually wound up while the
62 Silicon Chip
HT rail is monitored. There’s just one
catch here – in many cases, the set’s
kick start circuit will not function if
the voltage is wound up from zero; it
needs to switched on at a reasonable
input level.
I normally set the Variac to deliver
about 100V, with the set switched off,
then switch the set on. This is usually
high enough to provide the required
kick start but still low enough to avoid
trouble in the event of a destructive
fault.
So that was the setup. The set started
readily enough with an input of 100V
and I wound the voltage up gradually
until I had about 113V on the HT
rail (note: this occurred at something
considerably less than 240V input).
And all seemed well – there was no
smoke, flames, smells or other nasty
symptoms and, more importantly, the
set was functioning more or less normally, with a quite watchable picture
on the screen.
But I say “more or less” advisedly,
because the HT rail voltage was quite
unstable and the picture’s behaviour
was somewhat erratic. But the impor-
So, relatively speaking, this was one
of the easy ones. But I thought that it
was worth recounting for several of
reasons. My first reason was to restate
the protection circuit situation. One
must learn to recognise those sets
which incorporate these circuits and
know how to safely disable them without causing further damage.
My second reason was simply to
report the unusual fault in the regulator IC. It is a fault that I had not
encountered or heard of before.
And finally, I wanted to remind
readers of what I had to do to finish
the job – restore the protection circuit.
Unfortunately, I have encountered a
disturbing number of sets which have
had various protection circuits or safety features modified or disabled for one
reason or another and not restored to
original condition when the job was
finished.
It is important to always restore any
protection circuits when the job is
done, both from a safety aspect and to
prevent unnecessary damage to the set
if a fault occurs. After all, that’s what
the protection circuit is there for in
SC
the first place.
The receiver board at right
is capable of 16 channels
& you can build up to four
to give 64 channels. In
practice, one receiver board
would be built to control
each piece of equipment.
A smart remote control
with up to 64 channels
Have you ever wanted to control a
tuner, CD player, VCR or any other
device that does not have its own
remote control. If so, this project is for
you. It was developed to control a tuner
& a cassette deck but it could be made
to control almost anything using the
right interfaces.
By BRIAN ROBERTS
64 Silicon Chip
This project is extremely flexible
and uses a universal infrared remote
control. These “intelligent” or “learning” remote controls are readily available and can also replace the existing
remote controls for your TV, VCR and
other equipment.
For my application, I required 12
channels for the tuner and eight for
the tape deck. I did not want messy
wires connecting between a remote
control receiver and both of these units
so the unit was designed to be address
selectable which allows a receiver to
be fitted inside each unit. This means,
for example, that the tuner operates on
channels 1-8 and 33-40 and the tape
deck on say 9-16. If I needed to remote
PARTS LIST
Transmitter board
The transmitter board (above) is used
to teach codes to a learning remote
control unit. Up to 64 codes are
possible by changing the DIP switch
settings & a single link.
control another device, it would occupy addresses 17-24 and 49-56.
Because the receiver units were fitted internally in my installations, they
ran off the power rails in the controlled
device. The current drain is small, at
approximately 25mA. Alterna
tively,
you could have external receivers
which will require their own small
power supplies and a multi-way cable
to perform the control functions.
Each receiver board is capable of
handling 16 channels, so to provide a
total of 64 channels you would need
four separate receiver boards, each
of which is programmed via linking
options to decode its own 16 channels.
The receiver board has two channels
capable of either momentary or latched
operation for switching relays that turn
on and off high current loads. The two
outputs per board can be configured for
normally on or normally off operation
and are capable of sinking 75mA from
any rail up to and exceeding 16V. If this
feature is used, there is a maximum of
56 channels available (14 per board).
Circuit description
The circuit of the transmitter board
is shown in Fig.1. The transmitter is
built up only to provide a source of
codes which can be “learnt” by an
intelligent remote control. After this is
done, the transmitter board is not used.
IC1 is an MV500 remote control
1 PC board, code 15105942,
47 x 36mm
1 MV500 remote control (IC1)
1 2N2222 NPN transistor (Q1)
1 CQY89A infrared LED (L1)
1 8-way DIP switch
1 4-way DIP switch
1 2-pin header
1 jumper shunt
1 Murata CSB500E 500kHz
ceramic resonator (X1)
1 6V battery & snap connector
2 100pF ceramic capacitors
1 47kΩ 0.25W resistor
1 10kΩ 0.25W resistor
1 47Ω 0.25W resistor
Receiver PC board
(for 16 channels)
1 PC board, 80 x 86mm, code
15105941
8 4-way pin headers
1 8-way dual pin header
1 2-way dual pin header
4 jumper shunts
Semiconductors
1 MV601 infrared decoder (IC1)
1 SL486 infrared preamplifier
(IC2)
1 74HC138 3-to-8 line decoder
(IC3)
2 4028 BCD to decimal decoders
(IC4,5)
1 74HC74 dual D-type flipflop
(IC6)
1 4071 quad 2-input OR gate
(IC7)
4 4066 quad analog switches
(IC8,9,10,11)
transmitter IC. Pins 2-9 are the keypad row pins and pins 10-13 are the
column pins. The keyboard is scanned
in the conventional way and if a key
is pressed, the transmitter will deliver
a code relevant to that row/column
combination. In this circuit, no keypad
is used but DIP switches 1-8 and 9-12
provide all the combinations of a 32button keypad.
Pins 14 and 15 control the output
pulse frequency. SW13 is a link option which ties pin 14 high if inserted
while resistor R3 ties this pin low if
not. Therefore, two transmitting rates
are possible. With the link present, the
1 LM358 dual FET-input op amp
(IC12)
1 LM317T adjustable 3-terminal
regulator (REG1)
2 BC549 NPN transistors (Q1, Q2)
1 red LED (LED1)
1 BPW50 infrared photodiode
(IRD1)
1 1N914 diode (D1)
Capacitors
1 68µF 16VW tantalum
electrolytic
1 22µF 25VW electrolytic
1 10µF 16VW electrolytic
1 6.8µF 16VW tantalum
electrolytic
1 4.7µF 16VW electrolytic
1 0.47µF monolithic
1 0.15µF metallised polyester
(greencap)
3 0.1µF monolithic
1 .022µF metallised polyester
(greencap)
1 .015µF metallised polyester
(greencap)
2 .0047µF metallised polyester
(greencap)
2 100pF ceramic
Resistors (0.25W, 5%)
1 1MΩ
2 3.3kΩ
1 120kΩ
1 1kΩ
1 100kΩ
1 270Ω
1 27kΩ
1 240Ω
1 10kΩ
1 47Ω
1 4.7kΩ
Note: PC boards for this project will
be available from RCS Radio Pty
Ltd. Phone (02) 587 3491.
transmitted rate is 512 clock cycles
(fast rate); otherwise it is 2048 clock
cycles (slow rate).
Pins 16 and 17 connect to ceramic
resonator X1 and capacitors C1 and
C2 which form an oscillator circuit
of 500kHz from which all timing is
derived.
Q1 is the output driver which is
turned on and off by the current pulses from pin 1. L1 is the infrared LED
and resistor R1 limits the current to a
safe value.
Now let’s have a look at the circuit
of the receiver board – Fig.2.
The signal from the remote control is
May 1994 65
+3-6V
SW9-12
SW-DIP4
R2
10k
8
1
7
2
6
3
5
4
13
VDD
12 C1
11 C2
SW13
(LINK)
15
RA
RB 14
8
9
10
6
11
5
12
4
13
3
14
2
15
11
16
7 R2
6 R3
5 R4
4 R5
3 R6
2 R7
SW1-8
SW-DIP8
R1
47
R3
47k
10 C3
9 R0
8 R1
L1
CQY89A
K
B
OUTPUT 1
7
A
C
E
IC1
MV500
C2
100pF
OSC 17
OSC
Q1
2N2222
Fig.1: the circuit
of the transmitter.
IC1 generates a
serial pulse code
according to the
settings of the DIP
switches. 32 codes
are possible and the
total of 64 codes are
obtained by varying
the pulse rate low
or high.
X1
500kHz
16
C1
100pF
VSS
18
B
R
C
VIEWED FROM
BELOW
A
K
66 Silicon Chip
6 (ie, pulses are fast), the output at pin
7 will switch high and this toggles the
rate pin (pin 3) of IC1 so that it has the
correct rate selected. We’ll come back
to this factor in a moment.
IR pulse decoder
IC1, the MVA601 infrared pulse
decoder, is really the heart of the
circuit. Its timing is by the 500kHz
ceramic resonator at its oscillator pins
(6 & 7). IC1 decodes the pulses from
IC2 and the decoded result is presented on five data lines D0-D4 which gives
32 possible channels (ie, 25).
You will note that there is one extra
data bus line (D5) on the circuit which
comes from comparator IC12b. As the
decoder chip can only provide 32 independent codes and the design called
for 64 codes, we cheat by using the
rate of the pulses to give the extra 32
codes. If the rate of the pulses is fast,
then D5 is high. Conversely, if the rate
is slow then D5 is low. We now have
32 combinations when the pulse rate is
fast and 32 when the pulse rate is slow.
Pin 10 of IC1 is the Data Ready pin
and it goes low to light LED 1 when a
valid code has been received.
IC3, IC7, IC5 and IC4 convert the
binary data (D0-D5) from IC1 to 16
decoded outputs. IC3 is a 74HC138
3-to-8 line decoder. Dependent on the
data on its pins 1, 2 & 3, one of its eight
outputs will go low.
If the data was 00000 for D0-D5 and
the links on PL1 & PL2 are as shown
on the schematic, then the following
Construction
Let’s discuss construction of the
transmitter first. It is built on a PC
board measuring 47 x 36mm and coded
15105942 – see Fig.3 Mount all the
Fig.2 (right): the circuit of the receiver
board can decode up to 16 channels.
Four receivers are required to give a
total of 64 channels. IC1 is the heart
of the circuit & it decodes the serial
data from IC2 & presents it as parallel
data on lines D0-D5. This parallel
data is then decoded by IC3, IC4 & IC5
to drive the 4066 bilateral switches
(IC8-11).
▲
received by infrared photodiode IRD1
and then processed by IC2 which is
an SL486 infrared preamplifier chip
with AGC. This IC has a number of
features that ensure operation under
a wide range of operating conditions.
The chip has a differential input
stage to minimise noise, while capacitors C2 and C3 are part of the gyrator
circuitry to roll off the frequency response below 2kHz so that the attenua
tion at 100Hz is approximately 20dB.
C9 further reduces the gain below
2kHz in the first stage of the chip.
The output signal from pin 9 is coupled back into the stretch input (pin
10) via capacitor C10 to lengthen the
very narrow received pulses.
This is done to make the rate detector formed by IC12 operate with
wider margins. It also provides noise
immunity as the stretch input has
a threshold below which any noise
spikes are ignored.
The stretched pulses from pin 11 are
fed via op amp IC12a and then to pin 1
of IC1, the infrared pulse decoder. The
output of IC12a is also fed via diode
D1 to a circuit that detects whether the
pulse frequency is fast (output is high)
or slow (output is low). Resistors R7
and R4 and capacitor C11 form a filter
circuit for the rectified pulses from D1
and, depending on whether the pulse
frequency is high or low, the filter
voltage will be high or low.
Op amp IC12b is connected as a
comparator to monitor the filter voltage. If pin 5 is more positive than pin
conditions occur. Pin 15 of IC3 would
be low as a valid code (000) is being
received which means that pin 8 of
IC7c is also low. Pin 10 of IC1 (Data
Ready) would also be low, so pins 9
and 2 of IC7 would also be low. Pin 10
of IC7c would then go low to drive the
D input of IC4, a 4028 BCD-to-decimal
decoder. This then turns on bilateral
switch IC8 and channel 1 is enabled.
The purpose of the dual 8-pin headers
PL1 and PL2 is to allow link selection of
a block of any 16 channels from 64. This
enables us to have multiple decoders
which allow the flexibility talked about
in the introduction – see Table 1.
IC6a is a latch and channel 39 can
be selected for latched operation by
linking the pins of header SW1a, or for
momentary operation by linking across
SW1b. The same applies to IC6b and
channel 40 (link SW2a for momentary
operation and SW2b for latched).
The time constant consisting of R12
and C1 ensures that latch IC6 has its
pins 9 and 5 low at power up. The Q
outputs of IC6 turn on transistors Q1
and Q2 which can sink more current
than the bilateral switches. If the transistors are fitted, then IC11 is omitted
and vice versa. The solder straps indicated by the dotted lines on the circuit
diagram of Fig.2 allow the transistors
to be normally off or normally on by
selecting either the Q or Q-bar outputs
from IC6.
REG1 is an LM317 3-terminal adjustable regulator which is set to provide
an output of +6.3V. This is a compromise supply between IC1’s maximum
operating voltage of 7V and the desire
to obtain a low on-resistance in the
bilateral switches (IC8-11).
VCC
C7
.0047
R10
47
C6
.022 5
4
C2
6.8 2
C3
68 3
C5
10
IRD1
BPW41
C8
0.15 8
16
A
6
11
3
DEC4 OVCC
DEC2
IVCC
SOUT
C1
IC2
SL486
DECA
A
C
O/P
9 C10
.0047
DEC1
DEC1
1
IC12a
2 LM358
11
C2
R6
1M
8
D1
1N914
R3
4.7k
K
R5
10k
7
C9
15 .015
C11
0.47
IC12b
10
B
C
10
11
I/OA
6 CC
12
I/OA
CD
5
I/OB
CB
13
I/OB
CA IC8
4066
I/OC
I/OC
I/OD
3
Q0
14
Q1
2
Q2
IC4 Q3 15
4028
1
Q4
6
Q5
7
Q6
4
Q7
VCC
14
14
16
D
7
I/OD
8
I/OA
6 CC
12
I/OA
CD
5
I/OB
CB
13
I/OB
CA IC9
4066
I/OC
I/OC
I/OD
I/OD
VCC
16
1
10 A
13
B
12
C
IC7a
11
3
2
+9-16V
C4
22
IN
IN
REG1
REG1
LM317
LM317
ADJ
R8
1k
11 D0
12 D1
OB
13 D2
OC
A
RB
B
C
VCC
OD
OE
OUT
7
R1
1k
14 D3
11
6
16
15
14
13
12
Y0
A E3
2
Y1
B
3
Y2
C
IC3 Y3
74HC138
Y4
4
Y5
E1
5
Y6
E2
Y7
15 D4
D5
C13
100pF
OUT
R9
240
C12
4.7
CH1-8
CH9-16
1
2
3
1
2
3
CH17-24
CH25-32
CH33-40
4
11 5
6
7
D
4
5
CH41-48 6
CH49-56 7
8
8
CH57-64
PL1
PL2
1
2
3
4
E
F
1
2
3
4
PL4
8
9
10
1
2
3
11
4
CH4
14
D
1
2
3
4
8
9
10
11
1
2
3
4
PL6
1
2
3
4
Q7
8
R12
100k
C1
0.1
0.1
INTELLIGENT REMOTE CONTROL
1 PL7
2 CH36
6 CC
12
CD
5
IC10
CB 4066
8
13
I/OC
CA
9
I/OC
10
I/OD
11
I/OD
CH1
CH2
VCC
PL5
VCC
I/OA 1
2
I/OA
3
I/OB
4
I/OB
CH3
CH5
13 CA
12
CD
6
CC
5
CB
CH7
CH6
7
CH35
4
1 PL8
2 CH33
3
CH34
4
VCC
14
CH8
3
7
Q1, Q2, R13 AND R14
OPTIONAL. SEE TEXT
3
Q0
14
Q1
2
Q2
IC5
15
Q3
4028
1
Q4
6
Q5
Q6 7
VCC
VCC
PL3
7
14
E
F
10
8
10 A
13
B
12
C
9
K
VCC
A
D
PPM
C14
100pF
SIN
C15
100pF
IC7c
4071
8
IC1
MV601
8
VSS
9
0/E
OSC
6 X1
500kHz
7
4
R4
120k
VDD
DR
6
5
16
M/L
C16
0.1
OA
3
R7
27k
5
RA
RST
C17
0.1
11
GND
TP
IVSS 14
13
OVSS
12
REG
4
2
R11
270
A
LED1
RED
1 PL9
2 CH37
I/OA 1
2
I/OA
3
I/OB
4
I/OB
IC11
8
4066
I/OC
9
I/OC
10
I/OD
11
I/OD
3
CH40
4
1PL10
2
CH39
3
CH38
4
7
Q1
R14 BC549 C
3.3k B
E
R13
3.3k B
SW1b
SW2a MOMENTARY
4
VCC
10
PR
9
12
Q
CK
IC6b 8
11
D
Q
CLR
13
MOMENTARY
E
SW1a
LATCHED
SW2b
LATCHED
C
Q2
BC549
74HC74
VCC
14
2
3
5
Q
CK
IC6a 6
D
Q
CLR
1 7
A
K
A
K
B
E
C
VIEWED FROM
BELOW
ADJ
OUT
IN
May 1994 67
L1
3-6V
Q1
47
A
K
2x100pF
47k
10k
SW-DIP4
IC1 MV500
SW-DIP8
X1
1
SW13
Fig.3: the component overlay for the transmitter. Note that you could
substitute a 32-way keypad for the DIP switches if you wish. This would
make coding much easier. Fig.4 at right shows the full size artwork for
the receiver board.
TABLE 1
Sw 1-8
Sw 9-12
Sw13
PL1,2
Channel
Sw13
PL1,2
Channel
00000001
0001
out
Pos 1
Ch1
in
Pos 5
Ch33
00000001
0010
out
Pos 1
Ch2
in
Pos 5
Ch34
00000001
0100
out
Pos 1
Ch3
in
Pos 5
Ch35
00000001
1000
out
Pos 1
Ch4
in
Pos 5
Ch36
00000010
0001
out
Pos 1
Ch5
in
Pos 5
Ch37
00000010
0010
out
Pos 1
Ch6
in
Pos 5
Ch38
00000010
0100
out
Pos 1
Ch7
in
Pos 5
Ch39
00000010
1000
out
Pos 1
Ch8
in
Pos 5
Ch40
00000100
0001
out
Pos 2
Ch9
in
Pos 6
Ch41
00000100
0010
out
Pos 2
Ch10
in
Pos 6
Ch42
00000100
0100
out
Pos 2
Ch11
in
Pos 6
Ch43
00000100
1000
out
Pos 2
Ch12
in
Pos 6
Ch44
00001000
0001
out
Pos 2
Ch13
in
Pos 6
Ch45
00001000
0010
out
Pos 2
Ch14
in
Pos 6
Ch46
00001000
0100
out
Pos 2
Ch15
in
Pos 6
Ch47
00001000
1000
out
Pos 2
Ch16
in
Pos 6
Ch48
00010000
0001
out
Pos 3
Ch17
in
Pos 7
Ch49
00010000
0010
out
Pos 3
Ch18
in
Pos 7
Ch50
00010000
0100
out
Pos 3
Ch19
in
Pos 7
Ch51
00010000
1000
out
Pos 3
Ch20
in
Pos 7
Ch52
00100000
0001
out
Pos 3
Ch21
in
Pos 7
Ch53
00100000
0010
out
Pos 3
Ch22
in
Pos 7
Ch54
00100000
0100
out
Pos 3
Ch23
in
Pos 7
Ch55
00100000
1000
out
Pos 3
Ch24
in
Pos 7
Ch56
01000000
0001
out
Pos 4
Ch25
in
Pos 8
Ch57
01000000
0010
out
Pos 4
Ch26
in
Pos 8
Ch58
01000000
0100
out
Pos 4
Ch27
in
Pos 8
Ch59
01000000
1000
out
Pos 4
Ch28
in
Pos 8
Ch60
10000000
0001
out
Pos 4
Ch29
in
Pos 8
Ch61
10000000
0010
out
Pos 4
Ch30
in
Pos 8
Ch62
10000000
0100
out
Pos 4
Ch31
in
Pos 8
Ch63
10000000
1000
out
Pos 4
Ch32
in
Pos 8
Ch64
68 Silicon Chip
small components first, leaving the
MV500 IC till last. Watch the polarity
of the IC, the transistor and infrared
LED.
Next, assemble the receiver. This is
built on a board measuring 86 x 80mm
and coded 15105941. Before you begin
any soldering, check the board thoroughly for any shorts or breaks in the
copper tracks. These should be repaired
with a small artwork knife or a touch of
the soldering iron where appropriate.
If fitting the unit internally in a piece
of audio equipment, you will need to
look for a place to install the board
and the infrared LED. You will also
require a suitable relay which must
be installed inside the equipment
if you intend it to switch 240V AC.
Naturally, you must follow standard
wiring practice and take care with the
isolation of all 240V AC wiring.
You will need to make a number of
choices during construction and they
are as follows:
(1). Are you powering the receiver
circuit from a regulated voltage of between 5V and 6.8V? If so, you will not
need the LM317, R8 and R9.
(2). Do you need to operate relays?
If so, you are advised to delete IC11
and fit transistors Q1, Q2, R14 and
R13. This enables you to drive two
relays up to 16V and 75mA. Note that
a reverse-biased diode should be connected across each relay coil.
(3). If you are driving relays in the
latched mode, do you want the transistor normally on or normally off? Using
the solder links on the copper side of
the board, short pin 8 of IC6b to pin 2
of SW2a for normally on and pin 9 of
IC6b to pin 2 of SW2a for normally off
(Q1); and pin 6 of IC6b to pin 2 of SW1a
for normally on and pin 5 of IC6b to
pin 2 of SW1a for normally off (Q2).
Note: if you are using Q1 and Q2, it
is advisable to connect any load to the
unregulated positive voltage to avoid
the need for a heatsink to be fitted to
the LM317 regulator.
With these decisions made, it is
now a fairly straightfor
ward matter
of loading all the components onto
the board, starting with small passive
components and headers first and
leaving the integrated circuits and other semiconductors till last. Take care
with the polarity of semiconductors
and electrolytic capacitors.
Testing the transmitter
There is not much to testing the
10uF
.022
.0047
IC2 SL486
SW
2b
0.47
SW
1a
1
10k
1k
X1
2x100pF
4.7uF
+9-16V
REG1
LM317
1M
1
IC3 74HC138
PL1/2
PL3 1
IC4 4028
IC9 4066
1k
IC1 MV601
1
PL6
IC12
LM358
D1
1
1
IC6 74HC74
1
120k
4.7k
IC8 4066
SW
1b
0.1
PL5
.0047
1
22uF
.015
27k
SW2a
PL10
R13
Q2
M
L
IC5 4028
1Q1
R14
IC11
PL9
PL7
100pF
1
IRD1
1
0.15
GND
TP
IC10 4066
47
68uF 6.8uF
PL8
240
0.1
100k
transmitter until you have built the
receiver circuitry. One simple go/
no-go test is to see if your intelligent
remote control indicates that it has
learnt a code when the two units are
placed together. Another simple test
is to replace the infrared LED with a
visible LED and note if it is pulsing.
Alternatively, use a logic probe on the
collector of Q1.
To set up a code, the transmitter
must have one switch of SW1-8 on and
one switch of SW9-12 on (see Table 1).
The receiver must be powered up
and tested before it is installed in the
device to be controlled. You will also
need to set the two shorting links on
PL1 and PL2 to select the addresses so
that you can set the transmitter code
accordingly (again, see Table 1).
Power up the receiver board and
check that the current drain is around
30mA (with no relays operating). Select a code for a channel you would
like to test and bring the transmitter
close to the receiver’s infrared detector
(IRD1). The Data Ready LED should
light, until the transmitter is turned off.
With a multimeter set to “ohms”,
check the channel you have selected
with the transmitter. Ensure that the
transmitter is on and the Data Ready
LED is on while checking the resistance between the two pins for the
channel. When the channel is selected, the resistance should be less than
200Ω. If all is well, continue testing
all channels.
1
PL4
IC7 4071
A
270
IC11 NOT FITTED WHEN Q1,
Q2, R13 AND R14 ARE USED
LINK ON REG1 FITTED WHEN
OPERATING ON LESS THAN 6.5V
LED1
Fig.5: the component overlay for the 16 channel receiver
board. Take note of the settings in Table 1 when wiring up
the board & refer to the text to select the pin header options.
Troubleshooting
If you have followed the testing
procedure correctly and things are
not working, here are some checks
to make:
(1). If the Data Ready LED does not
light when the transmitter is sending
a valid code, check that the supply
voltage is correct for IC1 and IC2. Are
you testing under direct sunlight or
under very bright lights? Shade the
infrared detector (IRD1) or bring the
transmitter closer to the receiver.
(2). If the Data Ready LED lights but
the channels are not switching, try
sending three or four different codes
with the transmitter to see if it is an
isolated problem.
Check that PL1 and PL2 are set correctly; check the supply rails on ICs 3,
4 & 5; check the binary code from IC1
on pins 3, 11, 12, 13, 14 & 15; and check
that it is the code that you expected
the transmitter to send. Check that the
Fig.6: full size artwork for the transmitter board.
correct output for this code is enabled
on IC3 (pins 7-15, excluding pin 8).
Finally, check that the appropriate
output of IC4 or IC5 is high to select
its particular bilateral switch.
(3). If channels 39 or 40 don’t latch
or transistors Q1 or Q2 don’t turn on,
check the solder straps on the copper
side of the board associated with IC6.
Check that SW1 and SW2 have short
ing links in either the momentary or
latched positions, as appropriate. SC
May 1994 69
PRODUCT SHOWCASE
Tektronix launches a new style of
test instrument – the TekMeter
Tektronix Australia has announced
its TekTools product family which is
aimed at the electronic measurement
needs of the service professional.
The first of the TekTools family, the
TekMeter Series, is both an auto-ranging true RMS digital multimeter
(DMM) and an autoranging oscilloscope in a rugged, battery-powered
package. The TekMeter automates
common electronic measurements
in
cluding power quality and line
voltage monitoring, and variable AC
motor drive measurements. Tektronix claim that the TekMeter series is
half the price, size and weight of any
other similarly featured product on
the market.
The DMM features auto-ranging
DC and true RMS ranges from 400m
V to 600VAC/850VDC and Ohms
ranges from 400W to 40MW, as well
as diode and audible continuity tests.
The autoranging oscilloscope features
Tektronix' proprietary signal tracking
technology that automatically finds,
scales and displays signals continuously for hands-free operation.
DMM users will appreciate the
TekMeter's familiar user interface.
The TekMeter powers up in the DMM
mode and with a single press of a
button, it immediately displays the
signal for verification, characterisation
or analysis.
"We've designed the TekMeter Series with the non-oscilloscope user in
mind. The TekMeter takes advantage
of advanced Tektronix technology so
that users can have confidence that the
signal it displays is accurate," noted
Peter Roan, National Sales Manager.
"With both the auto-ranging DMM
and oscilloscope, users simply attach
the lead to the test point and the TekMeter does the rest. We've included
automatic measurements for power
calculation, Transformer Har
monic
Derating Factor (THDF), variable
70 Silicon Chip
speed AC motor control trigger
ing
and line aberration detection such as
spikes, brown-outs and blackouts. We
haven't compromised safety standards
either. The TekMeter is this industry's
first handheld DMM/oscilloscope to
receive UL and CSA safety certification"
TekMeter's 600V RMS, 6kV surge
rating provides ample protection
in high-voltage environments. The
TekMeter is compatible with commercially available DMM accessories
including temperature and pressure
transducers. Optional accessories for
the TekMeter include current probes, a
carrying case for hands-free operation,
a nicad battery pack with charger, and
an AC/DC adapter with RS232 communication for hard copy printouts and
remote communications.
Three models are available in the
Tekmeter series: the THM 550 with
single channel scope, the THM 560
with dual channel scope and the THM
565 deluxe model with advanced functions. The THM 565 can store up to 10
waveforms and instrument setups for
data comparison or archival and rou
tine measurements or calculations. A
backlight and real-time clock are also
available in the THM 565, allowing
low-light viewing and date stamping
of hardcopy printouts.
DMM accuracy is ±0.5% + 5 counts
on DC and ±2% + 5 counts on AC.
Vertical bandwidth in scope mode is
5MHz and the maximum sampling rate
is 25 megasamples/second/chan
nel.
Vertical resolution is eight bits and
vertical sensitivity ranges from 5mV
to 500V/division.
Pricing is as follows: Tekmeter THM
550, $1659; THM 560, $1903 and THM
565, $2380. These prices include sales
tax. All three units come with a 1-year
warranty.
For further information on the
Tekmeter series, cQntact Tektronix
Australia Pty Ltd on (02) 888 7066.
Low noise block converters
for satellite ground stations
L&M Satellite
Supplies have been
appointed sole Australian distributor of
Comtex microwave
equipment for the reception of satellites.
They have LNBs (low
noise block converters)
specifically manufactured for reception of
the following satellites
Aussat, Optus, Intelsat
and Gorizont.
Their model CX 101
is a dual polarity LNB
for use with Optus/
Aussat. It boasts a small size with exceptional electrical
characteristics and unique dish illumination properties,
being the only LNB that can be used with prime focus
and or offset dishes.
Some of its salient features are as follows: length
89mm, diameter 60mm, noise figure (total figure includ
ing inbuilt feedhorn) 1dB typical, offset or prime focus
reflector; inbuilt feedhorn, LO frequency 11.3 GHz for
Optus/Aussat; and F/D ratio match 0.35 to 0.65.
For further information, contact L&M Satellite Supplies, 33-35 Wickham Road, Moorabbin Vic 3199. Phone
(03) 553 1763.
Redback coaxial speakers
for PA work
These two loudspeakers are intended for wall or
ceiling installation in PA applications. They represent
a degree of refinement over the usual twincone speaker
used in ceiling installations and will have a much better
maintained upper frequency response.
The coaxial model has a single dome tweeter with
capacitor feed while the triaxial model has a cone
midrange and dome tweeter, with both drivers fed by
capacitors.
Both drivers are rated at 50 watts RMS with a
nominal impedance of 8W, a bass cone diameter of
200mm and a free-air resonance of 68Hz. Sensitivity
is quoted as 92dB/1W/1m (quite high compared to hifi
speakers) and both have a quoted frequency response
May 1994 71
to 20kHz. As you might expect,
the triaxial model has a somewhat
smooth
er frequency response than
the coaxial unit.
The triaxial unit is priced at $69.95
while the coaxial model is $59.95. See
them at Altronics in Perth or any of
their dealers.
VGA to VCR/TV
converter
Boston Technology Pty Ltd has an
nounced the release of the VID 701
Videoverter. The VID 701 Videoverter
comes in a compact (50 x 89 x 25mm)
box that fits in your pocket. Any PC
that has a VGA graphics adaptor card
can use the VID 701 Videoverter to
produce low-cost custom videos on
any standard video cassette recorder
or display on a large screen TV
The VID 701 Videoverter offers the
following features: LCD/TV display
toggling; TV auto blanking; display
size and position adjustment; AVRCA or S-VHS outputs (NTSC & PAL
versions available); interlaced/noninter
laced display; 11 VGA display
modes, up to 256 colours; compatible
with Microsoft Windows, Lotus 1-2-
3, Ani
mator, CAD and many more
application programs due to its software independence.
The VID 701 Videoverter works with
all major brands of VGA display cards
including Paradise, Cirrus, IBM, Oak,
ATI, Video 7 and Tseng Labs chip sets.
For more information, contact Boston Technology, PO Box 1750, North
Sydney 2059. Phone (02) 955 4765.
TDK's new 30 minute
videotape
TDK has introduced an E-30 HS30 minute tape to
complement its existing E-60, E- 120,
E-180 and E-240
minute tapes in the
popular HS formulation.
Camcorder users
favour a shorter tape time for dubbing,
rather than using E-120 and E-180
tapes. Until now, TDK had supplied
E-30 only in its HDX-Pro grade,
contending that the demand for this
playing time was mainly for mastering
and professional applications.
The HS E-30 has a recommended
retail price of $7.95 and is available at
selected TDK dealers and department
stores. For your nearest dealer, phone
TDK on (02) 437 5100.
HP introduces its
fastest 486-based PC
Hewlett-Packard has introduced its
fastest 486-based PC, the HP Vectra
VL2 4/100, which is based on the Intel
DX4 100MHz microprocessor. The
new PC delivers up to 50 percent more
performance than PC systems based
on previous Intel 486 technology at
a recommended retail price of $4451,
including sales tax.
With the addition of the 100MHz
Intel DX-4 based model, the HP Vectra
VL2 series now offers a range of keenly priced systems designed to meet
virtually any customer performance
need.
The HP Vectra VL2 series PCs are
said to deliver more features, including accelerated local bus video, power
management and plug-and-play features, than similarly priced mod
els
from other vendors.
The new 100MHz Intel DX4 pro-
Mini blow torch from Altronics
This little blow torch
has to be the nif
tiest
tool of its type that we
have ever seen.
All you do is slide
back the little red lock
and push the plunger to
ignite a hot little flame
that burns at 1300°C. It
burns for as long as you
hold down the plunger
When you take your
finger off, the flame
goes out.
The device is really easy to refuel too since it runs
off a standard disposable gas lighter – you just click
the case open, drop in the lighter and click the case
together and you're in business.
There are any number of soldering, brazing and
heating applications for it and you will wonder why
it wasn't on the market years ago. Called the Cadik
Micro-Jet, the mini blow torch has a piezoelectric
ignition system which is operated when you press the
plunger. Operating time with a standard disposable
lighter is about 20 minutes.
The Cadik Micro-Jet is priced at $29.95 and is
available from Altronics in Perth, or from their
dealers.
72 Silicon Chip
vides the highest performance of any 486 microprocessor
currently on the market. It has an iCOMP index rating
of 435, SPEC int92 of 51.38 and SPECfg of 26.59. In
addition to performance enhancements from the Intel
DX4 microprocessor, the HP Vectra VL2 4/100 offers
high performance through a Fast-IDE controller that
provides a 10-15% system performance increase over
PCs with standard IDE controllers. This system also
features a video subsystem capable of displaying up to
1280 x 1024 pixels.
A new power management feature, unavailable on
competitively priced models, also has been implemented
in the HP Vectra VL2 PC series. The HP power management system, which users can enable easily from the
PC setup menu, has a standby mode and a sleep mode
that reduce average power consumption to as low as 20
watts and 15 watts respectively.
For further information on HP products and services,
call 131347 (toll free Australia-wide).
Otari cassette
duplication system
Otari's new DP-4050F series of cassette duplicators
feature a 16-times duplication speed, enabling the
production on C60 cassettes in one pass in under two
minutes.
The DP-4050 series comprises four models: the DP4050F-C2 which provides simultaneous duplication
of two cassettes from one master; the Z3 cassette slave
expander which provides three additional slave transports; the OM open reel master, for ¼-inch tapes; and
the DP-4050E-Z buffer unit, a bias signal buffer unit for
driving up to six Z3 slave units in a large system.
Features of the DP-4050 series include switchable
8/16 times duplication speed, simultaneous stereo
copying of both sides of a cassette, automatic rewind
of master and slave transports at the program's end,
microprocesor controlled 3-motor transports, 4-channel
in-line ferrite heads, fixed/variable master pitch control,
independent and adjustable bias and level and EQ for
each channel.
For further information, contact Amber Technology
Pty Ltd, Unit B/5 Skyline Place, Frenchs Forest, NSW
SC
2086. Phone (02) 975 1211.
May 1994 73
COMPUTER BITS
BY DARREN YATES
What’s your free disc space?
This month, we begin a series of articles looking
at BIOS & DOS interrupts. In this article, we take
a look at a simple programming technique that
enables us to find out the free space on any drive
without having to use the DOS DIR command.
If you’re writing programs that use
up lots of disc space, particularly database files or any graphics programs,
the odds are that you’ll need to keep
track of how much space you have to
work with on a disc drive, whether it
be hard or floppy.
A program that crashes when the
disc drive is full is pretty useless but
most programming languages don’t
have a simple routine which returns
the bytes free in a variable.
An example of this related to
electronics is if you’re writing code
which allows the computer to sample
incoming analog voltages via an A/D
converter. At any time, and depending
on your sampling speed, it would be
quite easy for the system to run out of
disc space.
A crash at this point would be disastrous and would almost certainly
necessitate a repeat performance of the
sample. Thankfully, we can get access
to this information in the same way
the DIR command does using a simple
QuickBASIC routine.
CALL INTERRUPT()
In the past, we’ve used the CALL
ABSOLUTE() routine built into both
QBasic and QuickBASIC. This time,
let’s try an even simpler routine which
is built into QuickBASIC called CALL
INTERRUPT().
The original method consisted of
writing assembly code which has to be
74 Silicon Chip
stored into an array and then the base
and offset address found for the first
element of that array and so on. While
it worked well, it was by no means an
easy to remember process.
When QuickBASIC was launched,
the people at Microsoft realised the
usefulness of the inbuilt BIOS and
DOS routines and incorporated a simple interface function which allowed
easy access to them.
One of these routines happens to be
“Find Disc Space”. In the DOS routines, it is designated INT 21h,3600h.
When this routine is called, it returns
various pieces of useful information
and this can be seen in Table 1.
Upon calling INT 21H, the AX register must be loaded with 3600 hex.
As we mentioned a couple of months
ago, you can think of the interrupt as
TABLE 1
Get Disk Free Space
(interrupt 21h, service 36h)
Category: Disk services
Registers on Entry:
AH: 36h
DL: Drive code
Registers on Return:
AX: Sectors per cluster
BX: Available clusters
CX Bytes per sector
DX: clusters per drive
the street name and the AX register as
the house number.
When the routine is completed, all
four general purpose 16-bit registers
AX to DX are called into play and
return the sectors per cluster, number
of free clusters, bytes per sector and
clusters per drive, respectively.
From these registers, we can gather
the following about the drive:
• bytes per sector;
• number of sectors per cluster;
• number of free clusters;
• number of clusters per drive;
• amount of drive space used;
• drive space remaining; and
• total drive size.
In most normal programming cases,
only the last three items are of any
practical use.
Sample program
Right, let’s now take a look at
the sample program in Fig.1. If you
compare this to the other programs
published so far, you’ll notice that it
requires fewer lines of code.
To start off, we first have to define
a type variable which we’ll call REGTYPE. This consists of all the required
registers for CALL INTERRUPT(). The
initial values are not important at this
stage so we don’t have to worry about
clearing them.
Next, we define two arrays – INARY
and OUTARY – as copies of the type
REGTYPE.
After that, the AX field of INARY
is set to 3600 hex. The following line
takes advantage of QuickBASIC’s
COMMAND$ string metacommand.
When typing in the command
line at the DOS prompt to start the
program, you would normally type
BYTEFREE C: or whatever drive letter
you like. COMMAND$ then contains
everything after the program name.
Basic Listing For Disk Bytes Free Utility
‘Disk Bytes Free Utility
‘Written by DARREN YATES B.Sc.
‘Copyright 1994 Silicon Chip Publications Pty Ltd
TYPE regtype
AX AS INTEGER
BX AS INTEGER
CX AS INTEGER
DX AS INTEGER
BP AS INTEGER
SI AS INTEGER
DI AS INTEGER
FLAGS AS INTEGER
DS AS INTEGER
ES AS INTEGER
END TYPE
DIM inary AS regtype
DIM outary AS regtype
inary.AX = &H3600
drive$ = UCASE$(MID$(COMMAND$, 1, 1))
inary.DX = ASC(drive$) - 64
CALL interrupt(&H21, inary, outary)
bytespersector& = outary.CX
sectorspercluster& = outary.AX
freeclusters& = outary.BX
clustersperdrive& = ABS(outary.DX)
memfree& = bytespersector& * sectorspercluster& * freeclusters&
drivesize& = bytespersector& * sectorspercluster& * clustersperdrive&
PRINT : PRINT “Analysis of drive “; drive$ + “:”
PRINT : PRINT “Bytes free:”; memfree&; “bytes”, , “Bytes per sector :”;
bytespersector&
PRINT “Drive size:”; drivesize&; “bytes”, , “Sectors per cluster:”;
sectorspercluster&
PRINT “Bytes used:”; drivesize& - memfree&; “bytes”, , “Clusters per drive :”;
clustersperdrive&
program can be converted to work in
the same manner as BUTTON.BAS
published previously by just substituting the new INT number and adding
the appropriate bytes to the arguments
being passed to the machine code
program.
For those using QuickBASIC, make
sure that you load QB with the QB.QLB
quick library. This library holds the
CALL INTERRUPT and CALL ABSOLUTE routines. You can do this by
typing in the following line at the C:\
QB45 does prompt:
C:\QB45> QB/LQB.QLB
The /L option allows you to load
in an extra Quick library and automatically invokes QB.LIB when you
compile the program. The program
will also work with drives running
Microsoft Double
Space, recognising
both the real and host drives.
To run the EXE file, simply type:
BYTEFREE <drive>, where <drive>
is the drive letter.
As usual, we are making copies of
BYTEFREE.BAS/ OBJ/ EXE available
for $7 plus $3 postage. You can either
send your cheque to SILICON CHIP
or call (02) 979 5644 and quote your
SC
credit card details.
K
ALEX
The UV People
ETCH TANKS
● Bubble Etch ● Circulating
So in this case, it would contain “C:”.
Looking back at the program, this
line takes the first character in the
COMMAND$ string, converts it to
upper case and then stores it in the
DRIVE$ string.
The interrupt we’re going to use also
accepts a variable to allow us to select
the drive we wish to analyse. This
is stored in DX. However, the way it
recognises the drives is 0 for A:, 1 for
B:, 2 for C: and so on.
Using the ASCII code we can simply take the drive letter, convert it to
ASCII and then subtract 64 from it.
This gives us the correct number for
each drive.
The following line then makes the
call to the interrupt.
Upon return, all four registers AX
to DX contain our wanted informa-
tion. These are then stored in long
integers (four bytes wide), as denoted
by the “&” symbol. The reason for
using long integers is that it makes
the following multiplication much
easier to handle.
Now all we have to do is to multiply the bytes per sector by the sectors
per cluster and the number of free
clusters to get our resulting free disc
space.
The drive size is found by multiplying the bytes per sector by the sectors
per cluster and the number of clusters
per drive. The number of bytes used
is simply just the drive size minus the
free disc space.
The final four lines of code print this
information on the screen.
Now there are bound to be cries from
people who only have QBasic. This
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40 Wallis Ave, East Ivanhoe 3079.
Phone (03) 9497 3422, Fax (03) 9499 2381
May 1994 75
SILICON
CHIP
If you are seeing a blank page here, it is
more than likely that it contained advertising
which is now out of date and the advertiser
has requested that the page be removed to
prevent misunderstandings.
Please feel free to visit the advertiser’s website:
www.altronics.com.au
SILICON
CHIP
If you are seeing a blank page here, it is
more than likely that it contained advertising
which is now out of date and the advertiser
has requested that the page be removed to
prevent misunderstandings.
Please feel free to visit the advertiser’s website:
www.altronics.com.au
SILICON
CHIP
If you are seeing a blank page here, it is
more than likely that it contained advertising
which is now out of date and the advertiser
has requested that the page be removed to
prevent misunderstandings.
Please feel free to visit the advertiser’s website:
www.altronics.com.au
BOOKSHELF
QRP is alive & well!
QRP Classics, edited by Bob Schetgen. Published 1990 by the American
Radio Relay League, Newington, Connecticut, USA. 278 pages, soft covers,
276 x 211mm. ISBN 0 87259 316 9.
Price $24.00.
Over the last few years, it would
seem that the art of experimenting in
amateur radio was a dying one. The
number of ready built Japanese “appliances” around these days would
HF Antennas
For All Locations
HF Antennas For All Locations,
by Les Moxon, G6XN. 2nd edition,
published 1993 by the Radio Society of Great Britain. 322 pages,
soft covers, 245 x 186mm. ISBN 1
872309 15 1. Price $45.00.
Antenna theory has often been
regarded as a black art and something that only a learned few understand in any depth. This book
from respected British author and
amateur Les Moxon combines
much of the theory of HF antennas
into one handy volume. It is full of
diagrams, tables and examples of
practical antennas suitable for just
about all conditions and terrains.
The book is divided into two
parts. Chapters 1-9 explain the
theory behind how antennas work,
while chapters 10-20 put that the-
seem to suggest that Amateur Radio is
just an excuse to spend lots of money
on the most powerful receivers and
transmitters you can get.
So it was a breath of fresh air when
this book lobbed into the office and
gave this writer hope that Amateur
Radio isn’t dead yet. QRP Classics is a
compilation of low-power (QRP) lowcost projects from QST magazine and
the ARRL handbook. As you would
expect, it is chock-full of practical
circuits from oscillators to receivers,
transmitters and active audio filters.
The good thing about many of these
circuits is that they invite the reader to
pull out the trusty soldering iron and
start experimenting. What’s more, the
writers encourage readers to substitute
different components to see what happens – which is good to see!
There are nine chapters, starting
with an introduction to QRP ideas and
then following on with Construction
Practises, Receivers, Transmitters,
Transceivers, Antennas, Accessories,
Power Supplies and Design Hints.
ory into practice. Some readers
may find the theory a little heavy
going but the author has kept the
mathematics to a minimum and
used lots of diagrams to illustrate
the topics.
The first nine chapter headings
are: (1) Taking a New Look at HF
Antennas; (2) Waves and Fields;
(3) Gains and Losses; (4) Feeding
the Antenna; (5) Close-Spaced
Beams; (6) Arrays, Long Wires and
Ground Reflections; (7) Multiband
Antennas; (8) Bandwidth; and (9)
Antennas for Reception.
The remaining 10 chapters are as
follows: (10) The Antenna and Its
Environment; (11) Single Element
Antennas; (12) Horizontal Beams;
(13) Vertical Beams; (14) Large Arrays; (15) Invisible Antennas; (16)
Mobile and Portable Antennas; (17)
Small Antennas; (18) Making the
Antenna Work; (19) Antenna Con-
The circuits in this book use clever
design rather than brute force to get the
most out of a signal and help dispel
the myth that you need something the
size of the Snowy Mountains Scheme
to make big noises on the air.
There are also theory articles scattered throughout the book which give
the novice help on such topics as getting crystal oscillators going and how
to get the best out of your antenna.
The circuits range from a tiny 1-transistor CW oscillator/transmitter up to
a 3W PEP transceiver for six metres,
so there is something for both beginners and experienced construc
tors
alike. Many of the transistors used are
American 2N-series types but, for most
circuits, it should be easy to substitute
locally-available parts.
Overall, this book is a mine of information and ideas to get even the most
diehard appliance operator digging
around for that soldering iron.
Our review copy came from Daycom
Pty Ltd, 44 Stafford St, Huntingdale
Vic. Phone (03) 543 3733. (D.B.Y).
struction and Erection; (20) What
Kind of Antenna.
In summary, this text is one of the
best and most complete sources on
HF antennas available and deserves
a space on any amateur radio shelf.
Our copy came from Daycom Pty
Ltd and you can contact them on
(03) 543 3733. (D.B.Y).
May 1994 79
VINTAGE RADIO
By JOHN HILL
Trash or treasure – or how to
recognise the good stuff
Scrounging old radios & the parts to restore
them is all part of the vintage radio hobby. Much
of what one finds is junk but every so often, one
strikes it lucky.
A few years ago, I was a most enthusiastic collector of old radio receivers.
Countless hours were spent scrounging around secondhand shops, garage
sales and auctions, looking for those
elusive bargains. It was time-consuming work which located a lot of junk
and very few real treasures.
Those days have all but gone and
scrounging is now something I mainly
do when on holidays. My radio collecting has become so well known in
the district in which I live that I no
longer have to seek out old radios –
they seek me out instead. Well, their
owners do!
In the past week I have been fortunate enough to have been offered
a number of interesting items from
various sources, some of them being
of 1920s vintage. It is incredible that
such ancient equipment still survives
in any quantity.
The old Apex receiver
Perhaps the most interesting of these
recently acquired items is a 1929 Apex,
an 8-valve neutrodyne of American
manufacture. This particular set is a
mains-powered, steel-cased TRF receiver with a 3-gang tuning capacitor.
The receiver’s 91-year old owner had
This 1929 model 8-valve Apex is a TRF receiver of American manufacture. The
pressed steel radio cabinet has about the same aesthetic appeal as a sardine tin.
80 Silicon Chip
recently gone into a retirement village
and I found myself in the right place
at the right time, thus possibly saving
the old set from going to the tip.
While the receiver itself was in quite
reasonable condition for its age, the
same could not be said for the loudspeaker. Its open field coil and tattered
speaker cone left little doubt as to its
serviceability.
When I first saw the old Apex, I
thought that it would just have to be a
1929 model. Radios with pressed steel
cabinets came in around the 1928-29
period and didn’t last much longer.
The valve line-up also suggested a
similar date. The valves include: a
280 rectifier, five 227 triodes and
two 245s in the output. Whether the
output valves are in push-pull or are
parallel connected is not known at
this stage.
It is pleasing to note that Apex is
mentioned in “Radio Manufactures
of the 1920s”. The Apex chapter included an old advertisement for the
9-valve version of my particular set.
The advertisement was dated June
1929 – not a bad guess!
At this stage, I do not know whether
the Apex is a 110V or a 240V model.
The power transformer specification
plate carries blank spaces where the
vital information should have been
stamped. In such a case, it would be
prudent to plug the set into a 110V
transformer for a preliminary try out.
Because such a transformer is a permanent part of my workbench, that
does not present a problem.
Some of the better aspects of the old
Apex are: the cabinet is undented, it
still has its original knobs, the dial is
OK, the friction drive works quite well
and the on/off switch still functions.
No doubt, the Apex will require a
lot of work to restore it fully. There
will probably be open-circuit audio
transformers, crook paper capacitors
and other nasties underneath the
chassis, but such problems can usually be overcome one way or another.
A quick check revealed that all but
the output valves were in excellent
condition.
An unusual find
In the same shed that the Apex was
found there was also an old 5-valve
chassis which is interesting in an
unusual way.
The chassis originally used 4V European side contact valves, as witnessed
by the large valve socket holes and the
4V power transformer. Someone had
gone to a lot of trouble in the past and
removed the side contact valve sockets
and replaced them with smaller octal
sockets. Apparently, whoever did the
conversion had not given any thought
to the heater voltage of the replacement
octal valves, as there was no provision
made to supply 6.3V to the heaters. Instead, the octal replacements had been
wired up to the 4V heater winding on
the power transformer.
It would appear as though the
project was abandoned at that stage,
with the new octal valves still in
their sockets. Testing these valves in
a valve tester revealed that they were
indeed new for they all tested “GOOD”.
There’s nothing like a bit of luck now
and then!
There was still another interesting
item to come from that dusty shed and
With the lid removed, the old Apex receiver looks a little more interesting. The
pressed steel box at the right houses the power transformer & the large paper
capacitors used in the high tension filter.
These two ancient triode valves
(both Ediswan PV5DE) are still in
good working condition. One has the
American UX base, while the other
has the standard British 4-pin base.
This old electrodynamic loudspeaker from the Apex
receiver has not survived the past 60 plus years as well as
the receiver & a suitable substitute will have to be found.
This neutralising capacitor from the junkbox of parts is
far sturdier than the much more common screwdriver
adjusted variety.
May 1994 81
With a bit of cleaning & repair work, this trio of matching dials, tuning
capacitors & coils could be used to rebuild an early TRF receiver. This
equipment would be of about 1926-7 vintage.
This photo shows an old Igranic filament rheostat. It’s quite a sturdy & elaborate
device for a variable resistor.
that was a mid-1920s horn speaker.
Although sadly neglected and shabby looking, the Sterling “Baby” was
actually in working order and should
restore quite well.
The 1948 5-valve Healing hardly
warrants a mention at this stage but it
also came from the same shed. It was
a good shed, that one, and it wouldn’t
surprise me if something else old and
interesting comes to light in the near
future. There is still a lot of junk in
there yet!
A box of treasure
I recently met Domonic, a new col82 Silicon Chip
lector who has caught the valve radio
“bug” really bad. He is collecting radios as though there will be none left by
the end of the month. In the space of
just a few weeks, he managed to track
down about 20 old radios plus a box of
miscellaneous radio parts. It was these
odd bits and pieces that were offered
to me; not for money but in return for
a repair. It seemed like a good deal to
me so I accepted it.
Well, what was in the mystery box?
All 1920s parts; that’s what!
First, there were about eight old
triode valves. A quick examination
revealed that most had burnt-out
filaments but two of them were still
serviceable. And even though the others were no longer usable, they were
still very acceptable as show pieces.
A display of old valves only has to
look the part; they do not have to be
in working order.
There was also a quantity of board
mounted 4-pin valve sockets. These
included the American UX type, as
well as the British standard type.
Two of the valve sockets were of the
old porcelain variety which are fairly
rare today.
There are also five vernier dials
which could come in handy although
they would all require stripping,
cleaning and new dial glasses before
they could be considered usable. In
addition, there are a few ancient grid
leak capacitors of the type that have
clips fitted to them to hold a grid leak
resistor. And there were a couple of
resistors to go with them.
It is authentic old radio parts such
as these that are so valuable when
rebuilding an old 1920 receiver.
Apparently someone had stripped
an old 5 or 6-valve TRF at some stage
and the three inclined coils and matching tuning capacitors have been saved.
Three of the previously mentioned
vernier dials were possibly part of the
same receiver.
Unfortunately, only one of the five
audio transformers was still operative.
This is not surprising as these particular items have a very high mortality
rate. Most of them end up with open
circuit primary windings due to the
extremely fine wire used in their
manufacture.
Also included amongst the bits and
pieces were a number of swinging
coil sockets with their accompanying
plug-in coils. There are several 2-coil
models with a single swinging coil
and a 3-coil unit with two swinging
coils. Once again, these are fairly rare
items these days!
Bits & pieces
Naturally, there are a lot of other
incidentals: old mica capacitors, numbered dials, pieces of square section
wire, odd vintage style control knobs,
wire-wound rheostats, and a driver
from an old Amplion horn speaker.
The driver’s pole piece windings are
still intact, so that could be a handy
item.
The last items worth mentioning
from my treasure chest are several
variable grid leak resistors. There are
four of them and they are all in working order with resistances averaging
from about 0.5-10MΩ. It was the first
time I had ever seen variable grid leak
resistors; I had only read about them
previously.
Valuable items
No doubt some readers may consider that what I have described in the
last few paragraphs is little more than
junk. Well perhaps it is to some people
but not to me. As far as I’m concerned,
there are a few really valuable items
there although some may wonder what
would I possibly use them for.
I have quite a number of 1920s
receivers with missing and damaged parts – sets with broken dials,
open-circuit audio trans
f ormers,
missing knobs, burnt-out valves and
numerous other problems. The restoration of old and incomplete receivers is an impossible task without a
comprehensive supply of appropriate
spare parts.
In the January 1993 issue of SILICON
CHIP, the Vintage Radio story for that
month described the restoration of
a mid-1920s 3-valve receiver. That
particular restoration required the
following old-style spares: an on/
off switch, a radio frequency choke,
an audio transformer, a B605 valve,
a couple of terminals and possibly a
few other incidentals that have slipped
my mind. All these parts were readily
available from my own spare parts
supply.
Going back to the August 1989
issue, Vintage Radio gave details of
a complete rebuild of a mid-1920s
receiver. In this instance, what was
little more than an empty radio cabi
net was transformed into a working
3-valve receiver. This was done by
using carefully selected vintage spare
parts that were appropriate to that era.
The finished receiver may not have
been very original but it looked the
part and is a whole lot more interesting
than an empty cabinet.
So there it is - old junked parts from
valve radios of any age are useful to
collectors and restorers of vintage receivers. One cannot operate without
usable spares and one should not miss
out on any opportunity to obtain them.
No doubt many parts will never be
used but others will be the essentials
that restore an otherwise unrestorable
SC
receiver.
This simple 2-unit swinging coil socket assembly (with spare coils) is one of
several such coil assemblies found in the author’s “treasure chest”.
These old-style single-gang tuning capacitors always make a crystal set or
1-valve receiver a little more authentic looking.
These variable grid leak resistors are real relics from the past. The one on the
left has a carbon track & wiper arm, while the others are, presumably, carbon
granule compression types.
May 1994 83
Silicon Chip
March 1990: 6/12V Charger For Sealed Lead-Acid
Batteries; Delay Unit For Automatic Antennas;
Workout Timer For Aerobics Classes; 16-Channel
Mixing Desk, Pt.2; Using The UC3906 SLA Battery
Charger IC.
BACK ISSUES
September 1988: Hands-Free Speakerphone;
Electronic Fish Bite Detector; High Performance
AC Millivoltmeter, Pt.2; Build The Vader Voice;
Motorola MC34018 Speakerphone IC Data; What
Is Negative Feedback, Pt.4.
November 1988: 120W PA Amplifier Module
(Uses Mosfets); Poor Man’s Plasma Display;
Automotive Night Safety Light; Adding A Headset
To The Speakerphone; How To Quieten The Fan
In Your Computer.
April 1989: Auxiliary Brake Light Flasher; What
You Need to Know About Capacitors; Telephone
Bell Monitor/ Transmitter; 32-Band Graphic Equaliser, Pt.2; LED Message Board, Pt.2.
May 1989: Electronic Pools/Lotto Selector; Build
A Synthesised Tom-Tom; Biofeedback Monitor For
Your PC; Simple Stub Filter For Suppressing TV
Interference; LED Message Board, Pt.3; All About
Electrolytic Capacitors.
June 1989: Touch-Lamp Dimmer (uses Siemens
SLB0586); Passive Loop Antenna For AM Radios;
Universal Temperature Controller; Understanding
CRO Probes; LED Message Board, Pt.4.
July 1989: Exhaust Gas Monitor (Uses TGS812
Gas Sensor); Extension For The Touch-Lamp
Dimmer; Experimental Mains Hum Sniffers; Compact Ultrasonic Car Alarm; NSW 86 Class Electric
Locomotives.
September 1989: 2-Chip Portable AM Stereo
April 1990: Dual Tracking ±50V Power Supply;
VOX With Delayed Audio; Relative Field Strength
Meter; 16-Channel Mixing Desk, Pt.3; Active CW
Filter For Weak Signal Reception; How To Find
Vintage Radio Receivers From The 1920s.
Radio (Uses MC13024 and TX7376P) Pt.1;
Alarm-Triggered Telephone Dialler; High Or Low
Fluid Level Detector; Simple DTMF Encoder;
Studio Series 20-Band Stereo Equaliser, Pt.2;
Auto-Zero Module for Audio Amplifiers (Uses
LMC669).
October 1989: Introducing Remote Control; FM
Radio Intercom For Motorbikes Pt.1; GaAsFet
Preamplifier For Amateur TV; 1Mb Printer Buffer;
2-Chip Portable AM Stereo Radio, Pt.2; Installing
A Hard Disc In The PC.
November 1989: Radfax Decoder For Your PC
(Displays Fax, RTTY & Morse); FM Radio Intercom
For Motorbikes, Pt.2; 2-Chip Portable AM Stereo
Radio, Pt.3; Floppy Disc Drive Formats & Options;
The Pilbara Iron Ore Railways.
December 1989: Digital Voice Board (Records
Up To Four Separate Messages); UHF Remote
Switch; Balanced Input & Output Stages; Data For
The LM831 Low Voltage Amplifier IC; Installing A
Clock Card In Your Computer; Index to Volume 2.
January 1990: High Quality Sine/Square Oscillator; Service Tips For Your VCR; Speeding Up
Your PC; Phone Patch For Radio Amateurs; Active
Antenna Kit; Speed Controller For Ceiling Fans;
Designing UHF Transmitter Stages.
February 1990: 16-Channel Mixing Desk; High
Quality Audio Oscillator, Pt.2; The Incredible Hot
Canaries; Random Wire Antenna Tuner For 6
Metres; Phone Patch For Radio Amateurs, Pt.2.
June 1990: Multi-Sector Home Burglar Alarm;
Low-Noise Universal Stereo Preamplifier; Load
Protection Switch For Power Supplies; A Speed
Alarm For Your Car; Design Factors For Model
Aircraft; Fitting A Fax Card To A Computer.
July 1990: Digital Sine/Square Generator, Pt.1
(Covers 0-500kHz); Burglar Alarm Keypad & Combination Lock; Simple Electronic Die; Low-Cost
Dual Power Supply; Inside A Coal Burning Power
Station; Weather Fax Frequencies.
August 1990: High Stability UHF Remote Transmitter; Universal Safety Timer For Mains Appliances (9 Minutes); Horace The Electronic Cricket;
Digital Sine/Square Wave Generator, Pt.2.
September 1990: Music On Hold For Your Tele
phone; Remote Control Extender For VCRs; Power
Supply For Burglar Alarms; Low-Cost 3-Digit
Counter Module; Simple Shortwave Converter For
The 2-Metre Band.
October 1990: Low-Cost Siren For Burglar
Alarms; Dimming Controls For The Discolight;
Surfsound Simulator; DC Offset For DMMs; The
Dangers of Polychlorinated Biphenyls; Using The
NE602 In Home-Brew Converter Circuits.
November 1990: How To Connect Two TV Sets To
One VCR; A Really Snazzy Egg Timer; Low-Cost
Model Train Controller; Battery Powered Laser
Pointer; 1.5V To 9V DC Converter; Introduction
To Digital Electronics; Simple 6-Metre Amateur
Transmitter.
December 1990: DC-DC Converter For Car
ORDER FORM
Please send me a back issue for:
❏ May 1989
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❏ November 1989
❏ December 1989
❏ April 1990
❏ June 1990
❏ October 1990
❏ November 1990
❏ March 1991
❏ April 1991
❏ August 1991
❏ September 1991
❏ January 1992
❏ February 1992
❏ June 1992
❏ July 1992
❏ January 1993
❏ February 1993
❏ June 1993
❏ July 1993
❏ November 1993
❏ December 1993
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Card No.
Amplifiers; The Big Escape – A Game Of Skill;
Wiper Pulser For Rear Windows; Versatile 4-Digit
Combination Lock; 5W Power Amplifier For The
6-Metre Amateur Transmitter; Index To Volume 3.
50-Watt/Channel Stereo Power Amplifier; 12VDC/240VAC 40-Watt Inverter; Adjustable 0-45V 8A
Power Supply, Pt.2; Designing A Speed Controller
For Electric Models.
January 1991: Fast Charger For Nicad Batteries,
Pt.1; Have Fun With The Fruit Machine; Two-Tone
Alarm Module; Laser Power Supply; LCD Readout
For The Capacitance Meter; How Quartz Crystals
Work; The Dangers When Servicing Microwave
Ovens.
March 1992: TV Transmitter For VHF VCRs; Studio Twin Fifty Stereo Amplifier, Pt.1; Thermostatic
Switch For Car Radiator Fans; Telephone Call
Timer; Coping With Damaged Computer Direct
ories; Valve Substitution In Vintage Radios.
February 1991: Synthesised Stereo AM Tuner,
Pt.1; Three Inverters For Fluorescent Lights; LowCost Sinewave Oscillator; Fast Charger For Nicad
Batteries, Pt.2; How To Design Amplifier Output
Stages; Tasmania's Hydroelectric Power System.
March 1991: Remote Controller For Garage
Doors, Pt.1; Transistor Beta Tester Mk.2; Synthesised AM Stereo Tuner, Pt.2; Multi-Purpose I/O
Board For PC-Compatibles; Universal Wideband
RF Preamplifier For Amateurs & TV.
April 1991: Steam Sound Simulator For Model
Railroads; Remote Controller For Garage Doors,
Pt.2; Simple 12/24V Light Chaser; Synthesised
AM Stereo Tuner, Pt.3; A Practical Approach To
Amplifier Design, Pt.2.
May 1991: 13.5V 25A Power Supply For Transceivers; Stereo Audio Expander; Fluorescent
Light Simulator For Model Railways; How To Install
Multiple TV Outlets, Pt.1; Setting Screen Colours
On Your PC.
June 1991: A Corner Reflector Antenna For
UHF TV; 4-Channel Lighting Desk, Pt.1; 13.5V
25A Power Supply For Transceivers; Active Filter
For CW Reception; Electric Vehicle Transmission
Options; Tuning In To Satellite TV, Pt.1.
July 1991: Battery Discharge Pacer For Electric
Vehicles; Loudspeaker Protector For Stereo
Amplifiers; 4-Channel Lighting Desk, Pt.2; How
To Install Multiple TV Outlets, Pt.2; Tuning In
To Satellite TV, Pt.2; PEP Monitor For Amateur
Transceivers.
August 1991: Build A Digital Tachometer;
Masthead Amplifier For TV & FM; PC Voice Recorder; Tuning In To Satellite TV, Pt.3; Installing
Windows On Your PC; Step-By-Step Vintage
Radio Repairs.
September 1991: Studio 3-55L 3-Way Loudspeaker System; Digital Altimeter For Gliders
& Ultralights, Pt.1; Build A Fax/Modem For Your
Computer; The Basics Of A/D & D/A Conversion;
Windows 3 Swapfiles, Program Groups & Icons.
October 1991: Build A Talking Voltmeter For Your
PC, Pt.1; SteamSound Simulator Mk.II; Magnetic
Field Strength Meter; Digital Altimeter For Gliders
& Ultralights, Pt.2; Getting To Know The Windows
PIF Editor.
November 1991: Colour TV Pattern Generator,
Pt.1; Battery Charger For Solar Panels; Flashing
Alarm Light For Cars; Digital Altimeter For Gliders
& Ultralights, Pt.3; Build A Talking Voltmeter For
Your PC, Pt.2; Modifying The Windows INI Files.
December 1991: TV Transmitter For VCRs With
UHF Modulators; Infrared Light Beam Relay;
Solid-State Laser Pointer; Colour TV Pattern
Generator, Pt.2; Windows 3 & The Dreaded Un
recoverable Application Error; Index To Volume 4.
January 1992: 4-Channel Guitar Mixer; Adjustable
0-45V 8A Power Supply, Pt.1; Baby Room Monitor/FM Transmitter; Automatic Controller For Car
Headlights; Experiments For Your Games Card;
Restoring An AWA Radiolette Receiver.
February 1992: Compact Digital Voice Recorder;
April 1992: Infrared Remote Control For Model
Railroads; Differential Input Buffer For CROs;
Studio Twin Fifty Stereo Amplifier, Pt.2; Understanding Computer Memory; Aligning Vintage
Radio Receivers, Pt.1.
May 1992: Build A Telephone Intercom; LowCost Electronic Doorbell; Battery Eliminator For
Personal Players; Infrared Remote Control For
Model Railroads, Pt.2; Aligning Vintage Radio
Receivers, Pt.2.
June 1992: Multi-Station Headset Intercom, Pt.1;
Video Switcher For Camcorders & VCRs; Infrared
Remote Control For Model Railroads, Pt.3; 15-Watt
12-240V Inverter; What’s New In Oscilloscopes?;
A Look At Hard Disc Drives.
July 1992: Build A Nicad Battery Discharger;
8-Station Automatic Sprinkler Timer; Portable
12V SLA Battery Charger; Off-Hook Timer For
Telephones; Multi-Station Headset Intercom, Pt.2.
August 1992: Build An Automatic SLA Battery
Charger; Miniature 1.5V To 9V DC Converter;
Dummy Load Box For Large Audio Amplifiers;
Internal Combustion Engines For Model Aircraft;
Troubleshooting Vintage Radio Receivers.
September 1992: Multi-Sector Home Burglar
Alarm; Heavy-Duty 5A Drill speed Controller (see
errata Nov. 1992); General-Purpose 3½-Digit LCD
Panel Meter; Track Tester For Model Railroads;
Build A Relative Field Strength Meter.
October 1992: 2kW 24VDC To 240VAC Sinewave
Inverter; Multi-Sector Home Burglar Alarm, Pt.2;
Mini Amplifier For Personal Stereos; Electronically
Regulated Lead-Acid Battery Charger.
January 1993: Peerless PSK60/2 2-Way Hifi
Loudspeakers; Flea-Power AM Radio Transmitter;
High Intensity LED Flasher For Bicycles; 2kW
24VDC To 240VAC Sinewave Inverter, Pt.4; Speed
Controller For Electric Models, Pt.3.
February 1993: Three Simple Projects For Model
Railroads; A Low Fuel Indicator For Cars; Audio
Level/VU Meter With LED Readout; Build An Electronic Cockroach; MAL-4 Microcontroller Board,
Pt.3; 2kW 24VDC To 240VAC Sinewave Inverter,
Pt.5; Making File Backups With LHA & PKZIP.
March 1993: Build A Solar Charger For 12V
Batteries; An Alarm-Triggered Security Camera;
Low-Cost Audio Mixer for Camcorders; Test Yourself On The Reaction Trainer; A 24-Hour Sidereal
Clock For Astronomers.
April 1993: Solar-Powered Electric Fence; Build
An Audio Power Meter; Three-Function Home
Weather Station; 12VDC To 70VDC Step-Up Voltage Converter; Digital Clock With Battery Back-Up;
A Look At The Digital Compact Cassette.
May 1993: Nicad Cell Discharger; Build The
Woofer Stopper; Remote Volume Control For Hifi
Systems, Pt.1; Alphanumeric LCD Demonstration
Board; Low-Cost Mini Gas Laser; The Microsoft
Windows Sound System.
June 1993: Windows-Based Digital Logic
Analyser, Pt.1; Build An AM Radio Trainer, Pt.1;
Remote Control For The Woofer Stopper; A Digital
Voltmeter For Your Car; Remote Volume Control
For Hifi Systems, Pt.2; Double Your Disc Space
With DOS 6.
July 1993: Build a Single Chip Message Recorder;
Light Beam Relay Extender; AM Radio Trainer,
Pt.2; Windows Based Digital Logic Analyser;
Pt.2; Quiz Game Adjudicator; Programming The
Motorola 68HC705C8 Microcontroller – Lesson 1;
Antenna Tuners – Why They Are Useful.
August 1993: Low-Cost Colour Video Fader; 60LED Brake Light Array; A Microprocessor-Based
Sidereal Clock; The Southern Cross Z80-based
Computer; A Look At Satellites & Their Orbits;
Unmanned Aircraft – Israel Leads The Way; Ghost
Busting For TV Sets.
September 1993: Automatic Nicad Battery Charger/Discharger; Stereo Preamplifier With IR Remote
Control, Pt.1; In-Circuit Transistor Tester; A +5V to
±15V DC Converter; Remote-Controlled Electronic
Cockroach; Restoring An Old Valve Tester; Servicing An R/C Transmitter, Pt.1.
October 1993: Courtesy Light Switch-Off Timer
For Cars; FM Wireless Microphone For Musicians;
Stereo Preamplifier With IR Remote Control, Pt.2;
Electronic Engine Management, Pt.1; Mini Disc
Is Here; Programming The Motorola 68HC705C8
Micro
controller – Lesson 2; Servicing An R/C
Transmitter, Pt.2.
November 1993: Jumbo Digital Clock; High
Efficiency Inverter For Fluorescent Tubes; Stereo
Preamplifier, Pt.3; Build A Siren Sound Generator;
Electronic Engine Management, Pt.2; More Experiments For Your Games Card; Preventing Damage
To R/C Transmitters & Receivers.
December 1993: Remote Controller For Garage
Doors; Low-Voltage LED Stroboscope; Low-Cost
25W Amplifier Module; Peripherals For The
Southern Cross Computer; Build A 1-Chip Melody
Generator; Electronic Engine Management, Pt.3;
Index To Volume 6.
January 1994: 3A 40V Adjustable Power Supply;
Switching Regulator For Solar Panels; Printer
Status Indicator; Mini Drill Speed Controller;
Stepper Motor Controller; Active Filter Design For
Beginners; Electronic Engine Management, Pt.4;
Even More Experiments For Your Games Card.
February 1994: 90-Second Message Recorder;
Compact & Efficient 12-240VAC 200W Inverter;
Single Chip 0.5W Audio Amplifier; 3A 40V Adjustable Power Supply; Electronic Engine Management,
Pt.5; Airbags: More Than Just Bags Of Wind;
Building A Simple 1-Valve Radio Receiver.
March 1994: Intelligent IR Remote Controller;
Build A 50W Audio Amplifier Module; Level Crossing Detector For Model Railways; Voice Activated
Switch For FM Microphones; Simple LED Chaser;
Electronic Engine Management, Pt.6; Switching
Regulators Made Simple (Software Offer).
April 1994: Remote Control Extender For VCRs;
Sound & Lights For Model Railway Level Crossings; Discrete Dual Supply Voltage Regulator;
Low-Noise Universal Stereo Preamplifier; Build
A Digital Water Tank Gauge; Electronic Engine
Management, Pt.7; Spectrum Analysis Using An
Icom R7000 Communications Receiver.
PLEASE NOTE: all issues from November 1987
to August 1988, plus October 1988, December
1988, January, February, March & August 1989,
May 1990, and November and December 1992
are now sold out. All other issues are presently
in stock. For readers wanting articles from soldout issues, we can supply photostat copies (or
tearsheets) at $7.00 per article (incl. p&p). When
supplying photostat articles or back copies, we
automatically supply any relevant notes & errata
at no extra charge.
May 1994 85
AMATEUR RADIO
BY GARRY CRATT, VK2YBX
The Rhombic: a high gain
wire antenna for HF reception
Capable of providing significant performance
at HF, the Rhombic is often overlooked
because of space requirements. Where space
is no object, this antenna can give excellent
performance, particularly for HF point-to-point
communications, on any single amateur band.
Basically a variant of the long wire
antenna, the Rhombic antenna is simple to construct, both electrically and
mechanically. The antenna is used for
skywave communications and adopts
horizontal polarisation. When the
length of each leg exceeds five wavelengths at the frequency of operations,
the gain of a Rhombic compared with
a half-wave dipole can exceed 12dB.
There are two configurations of the
Rhombic antenna: resonant and nonresonant. The non-resonant antenna,
characterised by its resistive termination, has several advantages over the
resonant configuration.
A resonant Rhombic exhibits bidirectional characteristics, a disadvantage for maximum point to point
commu
nications. The non-resonant
Rhombic is unidirectional, and pres
ents a resistive match to the transmitter. Even though some energy is
dissipated in the terminating resistor,
that energy would have been radiated
in the opposite direction in the reso
l
"A"
"A"
DIRECTIVITY
"A"
R
"A"
l
Fig.1 (above): the layout of a typical Rhombic antenna. The diamond
shape has four “legs” of equal length & the opposite angles are equal.
The variation shown in Fig.2 at right uses several parallel elements.
This helps reduce the characteristic impedance of the antenna &
offers slightly improved gain.
86 Silicon Chip
nant Rhombic antenna, so the energy
dissipated does not equate to a loss of
directivity.
There is a theory amongst many HF
amateurs that a long wire performs
better than a Yagi of equivalent gain,
due to the length of the actual receiving elements being able to overcome
the diversity effects of ionospheric
propagation. The Rhombic antenna,
having multiple wavelength elements,
goes a long way towards capitalising
on this theory.
Layout
Fig.1 shows the layout of a typical
Rhombic antenna. The characteristic
diamond shape has four “legs” of equal
length and the opposite angles are
equal. Technically, the Rhombic is a
large travelling wave antenna, which
is terminated at the far end with a resistive load equal to the characteristic
impedance of the antenna.
Fig.3 (left): this diagram
shows the gain of a Rhombic
antenna compared to a dipole
for various leg lengths. The
optimum gain of a Rhombic
antenna is realised when the
side lengths, height & side
angles are selected to give
in-phase energy fields at the
chosen operating band.
14
12
10
GAIN IN dB
Ideally, the antenna should be fed
with a transmission line having an
impedance of 600-800Ω. However,
this may not always be practical. Often, Rhombic antennas are fed using
coaxial cable and a matching balun at
the feedpoint.
This termination suppresses reflections of the transmit power and the
antenna behaves almost exactly as a
matched transmission line, resulting
in an almost constant impedance over
a relatively wide bandwidth. As the
gain and beamwidth are significantly
affected by the operating frequency,
the practical bandwidth limitation of
the antenna is one octave (or about 2:1
in frequency terms).
8
6
4
2
0
1
2
3
4
LEG LENGTH IN WAVELENGTHS
5
75
Parallel elements
Optimising gain
A Rhombic antenna with sides equal
to two wavelengths or less has relatively low efficiency but if the length
of the sides is increased to seven or
eight wavelengths, the gain becomes
appreciable and the termination loss
is reduced to around 20% due to
improved radiation efficiency. Fig.3
shows the gain compared to a dipole
for various leg lengths.
Optimum gain of a Rhombic antenna is realised when the side lengths,
height and side angles are selected
to give in-phase energy fields at the
chosen operating band.
As is the case with all horizontal
antennas, optimum point-to-point
performance is achieved when the
antenna is aligned to the calculated
optimum wave angle. For amateur use,
70
OPTIMUM LENGTH
65
60
TILT ANGLE IN DEGREES
A variant of the Rhombic uses either two or three parallel elements,
similar in concept to the reflector and
director used in resonant antennas.
The use of multiple elements helps
reduce the characteristic impedance
of the antenna and offers slightly
improved gain.
The three wires should be separated
by one metre or so and wired as shown
in Fig.2. The terminating resistor
needs to be non-inductive and 800Ω
in value, rated at half the transmitter
power being used. It should be mounted as close as possible to the ends
of the three elements, in a suitable
weatherproof housing. This could be
remotely mounted at the bottom of the
mounting pole, via a length of 800Ω
matching cable, for convenience of
adjustment.
WAVE
ANGLE
o
0
o
5
o
10
o
15
o
20
o
25
o
30
55
50
45
40
35
30
1
1.5
2
2.5
3
3.5
4
LEG LENGTH IN WAVELENGTHS
4.5
5
5.5
6
Fig.4: this diagram allows the required “tilt angle” to be determined for
maximum radiation at the selected wave angle for a given leg length. The tilt
angle is simply 90° minus the angle of maximum radiation. This is the angle
formed between the two halves of an individual leg of the antenna.
where the distance between stations is
unpredictable, it is best to adjust the
antenna for the lowest angle of radiation and place the elements as high as
possible above the ground – normally
at least 6-10 metres.
Fig.4 allows the best “tilt angle” to
be found to give maximum radiation
at the selected wave angle, for a given
leg length. The tilt angle is simply 90°
minus the angle of maximum radia
tion. This is the angle formed between
the two halves of an individual leg
of the antenna (see Fig.1 – shown as
angle “A”).
Further reading
(1). Antenna Engineering Handbook,
2nd edition. Published 1961 & 1984
by McGraw Hill.
(2). Antennas, by John D. Kraus, 2nd
edition. Published by McGraw Hill.
ISBN 0-07-100482-3
(3). The ARRL Antenna Book. Published 1983. ISBN 0-87259-414-9.
SC
(4). ITT Designers Handbook.
May 1994 87
REMOTE CONTROL
BY BOB YOUNG
How to service servos & winches, Pt.2
Some servos must be regarded as throwaway
items not able to be serviced but even defunct
servos can be cannibalised to keep others going.
This month, we continue with this topic &
include an interesting if unusual description on
how these circuits work.
The development of the modern
integrated circuit servo goes back a
long way. To my knowledge, Orbit
Electronics in America commissioned
the first IC amplifier in about 1969.
I remember bringing back a bag full
of them from the World Aerobatic
Championships in 1971. They were
a stunning innovation at the time,
replacing an 11-transistor discrete
amplifier which chewed up lots of
space in the servo.
As a result of this chip, Orbit introduced the PS-4 servo which rocked
the R/C world at the time. We had
never dreamed of servos so small.
These days they still look small but
the new miniature servos are an or-
Fig.1: up until a few years ago, the Signetics NE544 was used in many
servos but it is no longer available.
88 Silicon Chip
der of magnitude down in size again
and make them look very ordinary.
However, in 1970 they were simply
amazing.
By modern standards the Orbit
amplifier was not very good and it
was prone to several shortcomings no
longer encountered in the modern IC
servo. They tended to dither around
neutral due to the dead band being
too small. This tended to raise servo
current and made the neutralising a
little less precise than it should have
been. They also exhibited temperature drift which we ultimately cured
with the addition of a diode in the
feedback path. They were also inclined to non linearity, a very serious
fault in a servo.
New ICs followed in quick succession as other manufacturers scrambled
onto the bandwagon in order to maintain their position in the R/C marketplace. Each learned from the preceding
and gradually the flaws disappeared.
With the arrival of the NE544 IC
(Fig.1), servo design came of age but
not however without a struggle! The
first two NE544 masks were duds. The
“B” mask in particular was prone to
latch up on the output bridge. This
resulted in a short circuit through the
bridge and the heat generated usually
blew the top off the IC.
With the arrival of the “C” mask, all
difficulties and defects were overcome
and I had a long and happy association
with this amplifier. Linear, accurate
and reliable, it was all we could ask
for in a servo amplifier.
Then they went and discontinued
it. Why do manufacturers do these
things? This is particularly upsetting
when they offer no direct replacement
and people with equipment designed
around these devices are left stranded
with no alternative.
The Japanese in the meantime were
pressing on with their own development and Futaba came up with a twochip solution, as shown in Fig.2. The
logic was in one chip and the bridge
in another. These were also prone to
blowing out the side of the chip. (They
were vertical mount).
Manufacturers do tend to skimp on
epoxy at times. They seem to forget
that electronic devices are driven by
smoke under pressure and that if the
case ruptures and the smoke escapes,
then the device will no longer function. (Editor’s note: we are indebted
to Bob Young for this illuminating
explanation of the workings of electronic components. Designing circuits
will now be so much easier!)
Futaba finally came up with a new
single chip solution (with thicker
epoxy?) and went on to produce some
very popular and reliable servos.
These days surface mount components
have reduced the servo amplifier to
a mere shadow of the old massive
shoulder-to-shoulder discrete servo
amplifiers. A couple of SM resistors
and capacitors and a teensy IC, and
that is it. Not like the good old days
at all.
From a servicing point of view,
there have been some nasty techniques
introduced by modern assembly methods which make servicing very tedious. Mounting the servo motor directly
on the PCB is probably the nastiest.
This means complete stripping of the
servo to get inside to the amplifier. The
completely sealed pot which has now
become a throwaway item is another
although the scales seem to have been
balanced by the improved reliability
of these pots.
All in all, there is little that can be
serviced in the modern servo and one
must be careful not to be drawn into
servicing something that is really a
throwaway item. All you can do with
cheap servos is to cannibalise them
for parts.
Fig.2: Futaba’s first integrated circuit servo
used two ICs, one for the logic & the other
for the motor drive bridge.
the servo for crash damage, etc (see
last issue) and then plug the opened
servo into the analyser. Servo neutral
and travel length are checked against
the manufacturer’s specs and a note
taken of the servo motor current con
sumption. Modern servo standards
usually call for 1-2ms at extremes with
a 1.5ms neutral. The old Futaba was
0.65-1.90ms and I have seen examples
of sets swinging around 1.2-2.5ms although this was rare. If in doubt, check
the manufacturer’s specifications – if
you can get them, that is.
with a lint free cloth and a smear of
Vaseline will help minimise wear on
the track. Check the wiper for tension
and cleanliness.
Servo motor current consumption is
a bit of a headache as motors of various
types draw widely differing current.
Your best bet is to note the current
on a new servo and use it as a guide.
What you are looking for is a marked
increase in motor current when the
motor is free running. Typically, a
new 11Ω permag motor will run free
(unloaded) at around 80-100mA. As
“All in all, there is little that can be serviced in
the modern servo and one must be careful not to
be drawn into servicing something that is really
a throwaway item. All you can do with cheap
servos is to cannibalise them for parts”.
Routine chores
That said, there are routine chores
which should be carried out regularly and there are some not so routine
techniques which may be helpful in
unusual circumstances.
At Silvertone, we use a servo analyser which consists of a pulse generator with variable rate auto-sweep, a
pulse width meter with LED display
and a current meter. We begin the
service with a visual inspection of
The servo is then checked for
smoothness over the entire arc of
travel. This will pick up any flaws in
the potentiometer track. If the servo
jumps or dithers around one spot
this usually indicates a hole in the
track or a dirty pot element. The pot
is replaced or cleaned as appropriate
and re-neutralised. Where it can be
done, pots are cleaned routinely as
part of a general service. Clean them
they age, the current will creep up,
sometimes to as high as 300mA. The
causes are many and varied and include dry sintered bronze bearings,
dirty commutator, bent shaft, broken
brushes and sometimes pinions which
have been pushed against the bearings.
Lubrication
Some motors can be stripped down
for inspection and repair or cleaning,
May 1994 89
REMOTE CONTROL – Servicing the servos
and some cannot. A simple way to
brighten up a tired motor is to start
the motor running and spray CRC-226
onto the bearings (front and rear). This
will soak into the bronze bushes and
some will work its way into the commutator, cleaning it as well.
Be sure to run the motor in both
directions for about five minutes. I
have seen motors respond well to this
treatment, with current consumption
falling from around 170mA to 100mA.
In a model with four servos, this
amounts to a significant reduction in
battery load.
Motor problems
Motor problems are still a worry
due to engine vibration pounding
away at delicate brushes. One rule to
remember in this regard is to never
connect the case of the servo motor
directly to ground. If the armature
insulation breaks down then you
have a dead short from motor drive
positive to ground. Scratch one servo
amplifier. The servo amplifier IC case
will rupture immediately, fill the
model with escaping smoke, blind
whilst monitoring the detector output
with an oscilloscope. Noisy servos
will show up as noise bursts in the
sync pause or even obliterated control pulses. If you lack a scope, then
remove the Tx antenna and do a range
check. With the model at the extreme
of controllable range, move each servo
in turn. A noisy servo will kill the
signal and control will be lost, whereas
good servos will function normally.
Once you are satisfied that all is
well electronically, reassemble the
servo and check for smooth operation
and that the servo neutral and current
draw have not changed. Sometimes
tightening the screws in the servo case
can distort the case or load the gears,
causing increased current drain.
Finally, before we close on the servo,
servicemen are often asked routine
questions or required to perform
non-standard modifications on servos
for special projects. Here are a few
hints on these problems.
Reversing servos
One common inquiry is how do you
reverse a servo. Virtually all transmit-
potentiometer element.
Do not touch the wiper wire. The
tricky bit comes about because the
wiper usually does not sit in the centre
of the pot element. Therefore, after
reversing, the wiper must be reset so
that the angle/resistance (whichever
is easier for you to measure) is the
same between the wiper and whichever of the two leads you used as a
reference. Once the wiring has been
swapped, reset the wiper so that the
angle/resistance between the wiper
and the reference end or colour is the
same as the original. If you get this
wrong, the servo will jam at one end
of the track, possibly damaging the
gears, amplifier or the motor. Plug the
servo in and switch the Tx and Rx on.
The servo should take up a position
roughly around neutral and work in
the reverse rotation. Reset neutral and
seal up the servo.
Stay alert during this procedure
and take the phone off the hook. If
you get interrupted, all hell can break
loose. I have seen people come into
my workshop with servos in pieces
and unable to get normal operation
in either direction. Usually they have
reversed one pair of wires and not the
other, forgotten to reset the wiper angle
or moved the wiper wire by accident.
Changing angle of rotation
“One rule to remember is to never connect
the case of the servo motor directly to ground.
If the armature insulation breaks down then you
have a dead short from motor drive positive to
ground”.
the pilot and almost certainly result
in a crash.
Checking for interference
Finally, one last note on servo
motors. One common cause of radio
interference is servo noise getting into
the receiver. This can be caused by a
dirty commutator but is more usually
caused by broken noise suppression
capacitors on the servo motor. These
sometimes get broken in a crash and
can cause problems to the less experienced or alert serviceman.
The best way to check for this is to
reduce the Tx signal level to a minimum and run each servo separately
90 Silicon Chip
ters these days are fitted with servo
reversing switches and these are a
good thing too. There are, however,
many old transmitters still in use
without this feature and the request
still comes at regular intervals. The
change is tricky at times and some
care is called for.
Firstly, write down or draw the location of the original wiring before you
disturb it. Next, before you touch the
pot wiring, measure the angle/resistance between the wiper and one end
of the pot element – this becomes your
reference end or colour. Now reverse
the two commutator leads on the motor
and the two wires at the ends of the
Another common request is for
the angle of rotation of the servo to
be changed. Some applications call
for very small or very large angles of
rotation. The request for 180° of travel
for flaps, undercarriage, etc is still a
common one. Again, modern transmitters can sometimes accommodate this
or servos can be purchased with 180°
of rotation as standard. If, however,
you live on a desert island and need
to doctor an existing standard servo,
the procedure is as follows.
Most servo ICs have external components to set such parameters as travel
length, minimum impulse and pulse
stretching, so check the specifications
for this information. Small variations
of rotation angle can be achieved by
changing the value of the one-shot
timing resistor.
Large variations are best done by
placing a resistor in series with the
pot element. Done very carefully,
rotation angles of up to 250° can be
achieved. Do not forget to remove
the output gear over-travel stops in
SC
the gearbox.
ASK SILICON CHIP
Got a technical problem? Can’t understand a piece of jargon or some technical principle? Drop us a line
and we’ll answer your question. Write to: Ask Silicon Chip, PO Box 139, Collaroy Beach, NSW 2097.
Binary confusion in
programming
I have read your Binary Clock article
in your March 1994 issue with interest. As I am at the moment attending
microproces
sor classes, I saw this
Binary Clock as a valuable practice
for my binary reading.
After typing the program into
DOS 6.2 Dosshell Editor and double
checking for any mistakes, I naturally
wanted to run it. As I know nothing
about PC programming, I saved the
Binary Clock as Binary.exe and tried
to run it through DOS. The computer
was rebooted. I then tried through
Windows and I got a message to the
effect “violation of system integrity,
reboot computer”.
Could you please advise me how
I could execute this program? (J. S.,
Portarlington, Vic).
• As explained in the article, the published program runs under QBASIC
and you have this if you are running
DOS 6.2. If you do not have QBASIC
set up to be accessed via the DOSSHELL, you can access it via your DOS
directory by typing “QBASIC” and
then “ENTER”.
If you want to run the Binary Clock
program as an executable file (ie, BINARY.EXE) you cannot save the listing
with an .EXE extension. It will cause
havoc as you have found. You can
UHF antennas
to build
Could you please inform me as
to whether any of the following
items have appeared as construction projects in your magazine: (1)
a UHF television antenna (channels
29-35), and (2) an infrared triggering device for 35mm SLR cameras,
working on reflected beam. (R. P.,
Deloraine, Tas).
• Two UHF antennas have been
described in SILICON CHIP. They are
the 4-Bay Bowtie Array described
purchase the BINARY.EXE form of the
program from SILICON CHIP for $7 plus
$3 for postage and packing.
Overloaded Discolight
blows Triacs
A while ago, I built two Discolight
kits (SILICON CHIP, July & August
1988 & October 1990) with dimmer
controls for a friend to be used as light
controllers in bands. Since then, we
have had occasional problems with
the 8A Triacs blowing up which was
not caused by overdriving them. As
a result, we upgraded to 16A Triacs
in the same package and they too are
occasionally blowing. The problem is
not just with the one channel or the
one kit and there is nothing wrong
with the lights we are using.
What we need is something that is
going to be 100% reliable and not give
up on us half-way through the gig.
We were thinking of using 40A TO-3
Triacs mounted with their heatsinks
in a separate metal box, with a cooling fan and a custom made PC board
that has the optocouplers, capacitors,
inductors and resistors mounted on it.
This way, there will be a low voltage
multicore cable between the main
controller and the new “output” box.
What I need to know is: (1) does the
value of the 0.1µF 250VAC capacitor
need to be changed?; (2) does the
in the January 1988 issue and the
UHF Corner Reflector described in
the June 1991 issue.
An infrared light beam relay
which might be applicable to your
camera application was published
in the December 1991 issue. We
also featured a PIR triggered motor driven camera in the March
1993 issue. The 1988 issue is now
unavailable but we can supply a
photostat copy of the article for $7
including postage. We can supply
the other issues for $7 each, including postage.
wattage of the 680Ω resistors need upgrading as two of these have burnt out
before?; and (3) as the physical size of
the inductor will need to be upgraded
to handle more current, what should
the wire size be, what are the number
of turns required and what size/part
number should now be used for the
toroid formers?
Each channel has to be rated at
15-20 amps continuous without anything getting too hot. We do need
the interference suppression as we
sometimes get RF switching noise
coming from the sound equipment.
We sometimes run these kits off a
3-phase outlet so as we can run more
lights than off GPOs without blowing
fuses (some nights we can run up to
12-14 kilowatts of lights.)
Are there any laws against using a
low power laser within a public bar as I
want to use the Oatley 2mW laser with
the deflection kit as a lighting back
drop when the band stops playing. (D.
Y., Edgewater, WA).
• It seems likely that you have had
Triac failure because you have been
using bigger lamp loads than we recommended. We published a 4-channel
dimmer using 40A Triacs in the June &
July 1991 issues but even for this we
would only recommend 2400 watts
maximum lamp load per channel.
Using higher lamp loads would be
inviting failure, even with 40A Triacs
because the surge currents at switchon are so high. In any case, normal
mains circuits should only be loaded
with 15 amps as a maximum.
The only way to handle higher lamp
loads is to have more channels (and
more 15A circuits) and to have some
Triacs slaved via the MOC3021 opto
couplers. We strongly caution against
using the Discolight or our 4-channel
dimmer in a 3-phase setup – it is just
too dangerous. We considered the
design of a 12-channel light dimmer
across 3-phase some years ago and
decided against it, partly because of
the difficulty of ensuring safety.
We suggest you use the same interference suppression net
work as
May 1994 91
Problem with
capacitance meter
I have had a problem with the
performance of the Digital Capacitance Meter Kit (May 1990). The
problem is that the readings are
slightly unstable; eg, a 22pF capacitor varies from 19-22pF on the pF
range, while a 2200pF capacitor
varies from 2189-2196.
It is also necessary to carry out
the calibration procedure each
time the instrument is used, as the
setting varies. I wonder if perhaps
you could offer a solution to my
problem. (R. D., NZ).
• The problem with drifting calibration can be caused by the master
oscillator comprising IC4, trimpot
VR2 and the 100pF styro capacitor. We suspect that one of these
used in our 4-channel lighting desk.
This used a 0.22µF/250VAC capacitor
and an inductor consisting of 0.8mm
enamelled copper wire on a much
larger toroid. You can upgrade the
680Ω resistors to 1W but they should
not burn out under normal use.
We should also point out that our
4-channel lighting desk also incorporated lamp preheat to reduce surge
currents and also had features such as
chaser and lamp flash. Back issues are
available at $7 each (includes p&p).
Some states do have laws controlling the use of lasers in public
places. You would be wise to consult
the Department of Labour and Industry
in your state.
Optical pickup for high
energy ignition
I am writing regarding adapting a
circuit published in SILICON CHIP in
June 1988 for a high energy electronic
ignition conversion. Could this circuit
be adapted to use an optical sensor
(switch) as my car is a 1978 Skyline
and does not suit the Hall Effect Siemens setup and the Sparkrite parts are
not now available?
I have an optical switch from a
Lumenition brand setup and the companion chopper for this unit. Three
wires go to the optical switch. (B. K.,
New Lambton, NSW).
• Based on the voltages you have
92 Silicon Chip
components is faulty. First, check
that the IC is labelled LMC555CN,
TLC555CN or ICM7555. If the IC
is labelled LM555
CN, then this
is only a standard 555 timer and
should be replaced with a CMOS
type. The 100pF capacitor or VR2
could also be faulty and you may
like to try substituting for these
components.
With regard to the display jitter,
check that regulator REG2 is correctly earthed to the mains supply earth as shown in the wiring
diagram. Similarly, check that the
transformer is earthed to the metal
plate at the rear of the case. Note
that the transformer body is usually
heavily covered in varnish so you
may need to scrape this away at the
mounting points to ensure a good
earth to the transformer case.
+12V
2.2k
LUMENITION
MODULE
OPTO
PICKUP
0.1
Q2
TO IC1
10k
10k
GND
given for when the optical switch is interrupted or not, it should be possible
to adapt it to our High Energy Ignition
quite simply. Just modify the circuit
published in June 1988 as follows:
remove the 820Ω resistor at the input
and change the 56kΩ resistor at the
base of Q2 to 10kΩ. The accompanying
circuit shows the details.
Controlling a motor
driven actuator
I have developed a project that I
have been working on part-time for
three years. This is a 12-volt nicad
powered electric motor driven actuator. This assembly is now developed
to a satisfactory stage, however I am
now stumped as I have an electronic
problem I can’t solve.
I wish to control my actuator remotely which isn’t the problem. My
problem is telling the motor to start
and then stop at a pre-selected and adjustable RPM, then pause momentarily
for the motor to come to rest, then
reverse to the same RPM. This is then
a completed cycle. I have sought and
received varied and widely conflicting
advice that all terminate in the “too
hard – can’t do” basket.
Is expensive computing power necessary as I have been told or is there a
low-cost circuit that will do the job?
(G. B., Carrajong Lower, Vic).
• There are a number of ways of
approaching your problem but they
don’t need to be complicated and they
certainly don’t require a computer or
a microprocessor, although that is a
possible solution. All you need to do
is to measure the motor RPM and then
when a certain figure is reached, let
the motor stop, reverse it and so on.
The simplest way to measure and
sense the RPM would be to use a
frequency to voltage converter and
use it to drive a comparator which
would switch the motor off when the
preselected speed was reached. After
that, you need some logic circuitry to
reverse the motor and go through the
cycle again. We can’t provide a complete design for you but can give you
a good start in the “Overspeed Alarm”
published in our June 1990 issue.
How to get ultra bass in
a small room
I was wondering if you could help
me with a problem to do with speakers
and room positioning. I have built an
88W per channel amplifier and I am
using a pair of homemade speakers
utilising one 12-inch 68W woofer, one
4-inch 48W midrange and two 3-inch
28W tweeters. This combination gives
me just the right level of power I am
looking for in my small room (loud,
and damn loud if I want to show off!).
There is only one discrepancy; ie, I
have problems getting enough bass. I
don’t mean normal bass. I mean headache inducing bass! I have always put
it down to my small room size but in
my experimentation, I found that if I
stand on my bed, right against the wall
opposite the speakers, I get more than
enough bass to satisfy my sub 200Hz
hungry ears!
Since my parents weren’t keen on
my idea of attaching a hanging chair to
my ceiling, I must turn to the experts
for more suggestions. I hope you don’t
tell me I need a bigger room because
I haven’t had much luck convincing
my parents to swap my room for the
lounge room!
One other thing – what is the maximum continuous temperature rating
SILICON CHIP FLOPPY INDEX
WITH FILE VIEWER
Now available: the complete index
to all SILICON CHIP articles since the
first issue in November 1987. Now
you can search through all the articles
ever published for the one you want.
Whether it is a feature article, a project,
a circuit notebook item, or a major
product review, it doesn’t matter; they
are all there for you to browse through.
The index comes as an ASCII file on a
3.5-inch or 5.25-inch floppy disc to suit PC-compatible computers and you
can use a word processor or our special file viewer to search for keywords.
Now with handy file viewer: the Silicon Chip Floppy Index now comes with
a file viewer which makes searching for that article or project so much easier.
You can look at the index line by line or page by page for quick browsing,
or you can make use of the search function.
Simply enter in a keyword(s) and the index will quickly find all the relevant
entries. All commands are listed on the screen, so you’ll always know what
to do next. Note: requires CGA, EGA or VGA graphics card, IBM-compatible
PC, MSDOS 3.3 and above.
Disc size: ❏ 3.5-inch disc ❏ 5.25-inch disc
❏
❏
❏
❏
❏
❏
❏
Floppy Index (incl. file viewer): $A7 + p&p
Notes & Errata (incl. file viewer): $A7 + p&p
Bytefree.bas /obj / exe (Computer Bits, May 1994): $A7 + p&p
Alphanumeric LCD Demo Board Software (May 1993): $A7 + p&p
Stepper Motor Controller Software (January 1994): $A7 + p&p
Printer Status Indicator Software (January 1994): $A7 + p&p
Switchers Made Simple – Design Software (March 1994): $A12 + p&p
Note: Aust, NZ & PNG please add $A3 (elsewhere $A5) for p&p with your order
Enclosed is my cheque/money order for $__________ or please debit my
❏ Bankcard ❏ Visa Card ❏ Master Card
Card No.
Signature_________________________ Card expiry date______/______
Name _____________________________________________________
PLEASE PRINT
Street _____________________________________________________
Suburb/town __________________________ Postcode______________
Send your order to: SILICON CHIP, PO Box 139, Collaroy, NSW 2097; or
fax your order to (02) 979 6503; or ring (02) 979 5644 and quote your credit
card number (Bankcard, Visacard or Mastercard).
✂
for a 2N3055 power transistor? I am
developing some really high power
13.8V power supplies and am using
3055s because I have obtained around
30 of them secondhand at low cost.
How many would you expect a 40amp supply to need? (J. P., Teralba,
NSW).
• The question you ask about getting
more bass could easily take a whole
magazine to answer in detail. You
don’t necessarily need a larger room
to get more bass and in fact you can
get huge amounts of bass inside a car
and that is much smaller than any
room. However, as you have found,
loudspeakers do set up standing waves
in any room at particular frequencies
and when you stand in the right place
you get copious amounts of bass. So
what to do?
Try changing the position of the
loudspeakers. In general, the closer
into the corners you place the speakers, the more bass you will get. You
will also get more muddy sound but
that may not matter depending on
what sort of music you are listening
to. You will probably find that there
is a good compromise between the
amount of bass and the overall clarity
of the sound.
Failing that, we have to ask about
the size and design of the loudspeaker
cabinets. This may not be suited to the
speakers you are using.
Your question about 2N3055s could
also take a lot of space to answer fully.
Briefly though, the 2N3055 is a rated
at 150 watts for a case temperature of
25°C and has a maximum junction
temperature of 200°C. Just how much
power a 2N3055 can actually dissipate
depends on its SOAR conditions (ie,
voltage and current within the “safe
operating area”), its junction temperature and the ability of the heatsink to
get rid of the heat.
Having said that, in a typical power
supply designed to deliver 13.8V DC
and producing around 22V unregulated, we would not like to see more
than 5 or 6A through each 2N3055 in a
parallel setup. So for 40A output, you
would probably need eight devices
and they would need to be mounted
on a vary hefty heatsink capable of
dissipating around 300W total. That
is a big ask indeed. By the way, you
would also need a transformer capable
of delivering around 900W and all the
other components would need ratings
SC
to match.
May 1994 93
MARKET CENTRE
Cash in your surplus gear. Advertise it here in Silicon Chip.
ANTIQUE RADIO
CLASSIFIED ADVERTISING RATES
Advertising rates for this page: Classified ads: $10.00 for up to 12 words plus 50
cents for each additional word. Display ads (casual rate): $20 per column centimetre (Max. 10cm). Closing date: five weeks prior to month of sale.
To run your classified ad, print it clearly in the space below or on a separate
sheet of paper, fill out the form & send it with your cheque or credit card details
to: Silicon Chip Classifieds, PO Box 139, Collaroy, NSW 2097. Or fax the details
to (02) 979 6503.
_____________ _____________ _____________ _____________ _____________
_____________ _____________ _____________ _____________ _____________
_____________ _____________ _____________ _____________ _____________
ANTIQUE RADIO RESTORATIONS:
specialist restoration service provided
for vintage radios, test equipment &
sales. Service includes chassis rewiring,
recon
densering, valve testing & mechanical refurbishment. Rejuvenation
of wooden, bakelite & metal cabinets.
Plenty of parts – require details for mail
order. About 1200 radios within 16,000
square feet. Two-year warranty on full
restoration. Open on Saturday 10am4.30pm; Sunday 12.30-4.30pm. 109
Cann St, Bass Hill, NSW 2197. Phone
(02) 645 3173 BH or (02) 726 1613 AH.
FOR SALE
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THE HOMEBUILT DYNAMO: (plans)
brushless, 1000 DC watt at 740 revs.
$A85 postpaid airmail from Al Forbes,
PO Box 3919 - SC, Auckland, NZ.
Phone Auckland (09) 818 8967 any
time. Rotor magnets (3700 gauss) kit
now available.
WEATHER FAX programs for IBM XT/
ATs *** “RADFAX2” $35 is a high resolution, shortwave weather fax, Morse &
RTTY receiving program. Suitable for
CGA, EGA, VGA and Hercules cards
(state which). Needs SSB HF radio &
Radfax decoder. *** “SATFAX” $45 is
a NOAA, Meteor & GMS weather satellite picture receiving program. Needs
EGA or VGA plus “WEATHER FAX”
PC card. *** “MAXISAT” $75 is similar
Enclosed is my cheque/money order for $__________ or please debit my
❏ Bankcard ❏ Visa Card ❏ Master Card
✂
Card No.
RCS RADIO PTY LTD
Signature__________________________ Card expiry date______/______
Name ______________________________________________________
Street ______________________________________________________
Suburb/town ___________________________ Postcode______________
94 Silicon Chip
RCS Radio Pty Ltd is the only company that manufactures and sells every
PC board and front panel published
in SILICON CHIP, ETI and EA.
RCS Radio Pty Ltd,
651 Forest Rd, Bexley 2207.
Phone (02) 587 3491
Radio and Electrical Books
1914 Catalog Electro Importing Co ............$18
1936 Radio Data Book ...............................$15
Hammarlund Short Wave Manual (1937)....$11
Henley’s 222 Radio Circuit Designs ......$26.50
Neon Signs (1935) ................................$28.50
How to Become a Radio Amateur (1930) .....$7
How to Build & Operate Short Wave
Receivers ...................................................$18
How to Build a Solar Cell ...........................$11
High Frequency Apparatus (1916) .............$29
Radio for Beginners ................................$6.50
Radio for the Millions .................................$20
Short Wave Radio Manual (1934) ..............$30
Television (1938) .........................................$7
Tesla Coil ....................................................$11
Tesla Coil Secrets .......................................$16
Tesla Said ...................................................$79
Construction of Large Induction Coils ........$23
The Wimshurst Machine How to Make .$19.50
The Wireless Man ......................................$27
Wireless Experimenter’s Manual 1920 .......$31
Electrical Goods & Radio Apparatus ..........$14
Electroplating (1911) ............................$17.75
Experimental Television How to Make ........$34
Meissner “How to Build” Instructions ........$22
How & Why of Radio Apparatus ...........$20.50
All prices include postage. Payment can be
made by cheque or money order made out
to Plough Book Sales, PO Box 14, Belmont,
Vic. 3216. Phone (052) 66 1262.
Silicon Supply and Manufacturing
4002B
4010B
4011B
4012B
4013B
4014B
40150
4017B
4019B
4023B
4025B
4027B
4040B
4048B
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4053B
4060B
4069B
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4075B
4082B
4094B
74HC11
74HC27
.86
.70
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.77
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1.53
1.55
1.88
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.67
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2.13
1.15
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1.39
1.71
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1.31
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74HC30
74HC76
74HC86
74LS11
74LS12
74LS13
74LS14
74LS20
74LS21
74LS27
74LS30
74LS33
74LS49
74LS73
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74LS83
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74LS90
74LS92
74LS109
74LS126
74LS138
74LS139
74LS147
74LS148
.50
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1.00
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2.85
1.35
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1.10
1.45
1.10
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2.85
1.25
74LS151
74HC138
74HC139
74HC154
74HC174
74HC373
74F00
74F02
74F08
74F10
74F11
74F20
74F30
74F32
74F36
74F38
74F151
74F163
74F169
74F175
74F241
74F244
74F257
74F258
74F353
.60
1.05
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3.80
.80
1.25
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1.10
.80
.65
.85
2.30
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1.15
1.10
.75
2.15
1.75
All prices include sales tax.
Phone (02) 554 3114; Fax (02) 554 9374. After
hours only bulletin board on (02) 554 3114
(Ringback). Let the modem ring twice, hangup, redial the BBS number, modem answers on
second call.
PO Box 92, Bexley North, NSW 2207.
TRANSFORMER REWINDS
ALL TYPES OF TRANSFORMER REWINDS
TRANSFORMER REWINDS
to SATFAX but needs 2Mb expanded
memory (EMS 3.6 or 4.0) and 1024
x 768 SVGA card. All programs are
on 5.25-inch or 3.5-inch disks (state
which) & include documentation. Add
$3 postage. Only from M. Delahunty,
42 Villiers St, New Farm, Qld 4005.
Phone (07) 358 2785.
INTELLIGENT INFRARED receiver:
(ref. SILICON CHIP, March 1994). Use
your TV or VCR infrared remote control
transmitter to control your TV or hifi
appliances with an intelligent infrared
receiver kit ($55). Also available infrared transmitters, preprogrammed
and learning models. For details call
Benetron Pty Ltd (018) 20 0108 or (02)
963 3868.
ELECTRONICS REPAIR BUSINESS:
Established 3 years, Finley, NSW. Authorised for major brands, contract with
local retail outlet, low rent premises on
highway, ideal first business for qualified
technician. Well equipped workshop and
office, extensive manual collection, good
parts stock. Price $45,000 neg. WIWO.
Phone owners (058) 83 1977 BH or
(058) 85 9254 AH.
Reply Paid No.7, PO Box 1058,
St Marys, NSW 2760.
Ph: (02) 833 1146. Fax: (02) 623 5559.
SECONTRONICS
COMPONENTS, COMPUTERS, ELECTRON TUBES
S/H TEST EQUIPMENT, COMPUTER REPAIRS
PC COMPATIBLE KEYBOARDS 101 AT:$39
I/O + IDE/FDD
$35
RECYCLED EPROMS
AT I/O CARDS
$22
2716
$1.50
2SD1169
$2.00
2732
$1.50
2N3440
$0.80
2764
$2.00
2N3439
$0.80
27128
$3.00
2SC3157
$4.00
27256
$3.50
27C41
$0.80
27512
$3.50
7406
$0.20
27C101
$4.00
8250 $5 8251 $2
8259 $2 6809 $8
MC8050 $2
MCT275 $1.20
MOC3032 $2
VALVES:
QQV07/50 $25
3D21 $8
12AU7 $6
6SG7 $8
6U8A $8
1S2 $3
1T4 $6
CV553 $3
2C39A $30
2C40A
$40
3A4 $8
5651 $6
5651A $6
6AK5 $6
6J6WA $7
6AM6 $5
6BA6 $4
SPECIAL: SURFACE MOUNT COMPONENT PACK – 180 RESISTORS, 40 ZENERS, 30 TRANSISTORS AND 2 ICs. $6.50 INC.
PACK & POST
PHONE OR MAIL ORDERS, CREDIT CARDS ACCEPTED FOR
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PHONE (07) 396 1859, FAX (07) 855 1014.
MEMORY PRICES
PRICES AT MARCH 21ST, 1994
SIMM
1Mb x 3
1Mb x 9
4Mb x 9
4Mb (72-pin)
8Mb (72-pin)
16Mb (72-pin)
70ns
70ns
70ns
70ns
70ns
70ns
$63
$65
$256
$250
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DRAM DIP
1 x 1Mb
256 x 4
70ns
70ns
$8.50
$9.00
IBM PS.2
55/65SXVP
L40/N33
90/95 PS1
4Mb
4Mb
4Mb
$250
$300
$265
MAC
4Mb 4Mb x 80 80ns
6Mb P’BOOK
$220
$420
CO-PROCESSORS
387S/DX to 40
$105
LASER PRINTER HP
with 4Mb
$260
COMPAQ
LTE 25C
8Mb $635
TOSHIBA
2000SX
8Mb $475
46/1900 3.3
4Mb $350
SUN
SPARC 10/20 16Mb $1140
PCMCIA
1Mb V2 BAT SRAM
$230
2Mb V2 BAT SRAM
$380
2Mb V2 FLSH SRAM $380
42Mb V2 HARD DRIVE $560
Sales tax 21%. Overnight delivery.
Credit cards welcome. 5-Year Warranty
Ring for Latest Prices
1st Floor, 100 Yarrara Rd, PO Box 382, Pennant Hills, 2120.
Tel: (02) 980 6988
Fax: (02) 980 6991
CONTROL RELAYS, Robots, Radios
or Railways from LPT1: of your XT
to 486 PC. 64 bits. Fully expandable.
Demo programs, flow charts, circuits,
drivers in M.L. & Basic. Main PCB
& software $35. Don McKenzie, 29
Ellesmere Crescent, Tullamarine 3043.
Phone (03) 338 6286.
SOUTHERN CROSS SBC, accessories
& EPROM emulator. See SC 8/93 &
12/93. Ideal for TAFE, schools & individual use. Alpine Technologies, tel/fax
(03) 751 1989.
ROMLoader EPROM EMULATOR (EA
Jan/Feb 92) - upgrade to handle 27128,
27256 EPROMs. Includes memory edit
facility. 8051 Proto-Boards (EA Feb 93)
PELHAM
also available. Send SAE for details.
Tantau Australia, PO Box 1232, Lane
Cove 2066. AH (02) 878 4715.
VALVE AMPLIFIERS: Australian made.
Mono, stereo, guitar using 2A3, 211, 6L6
or 807 valves. Williamson reproductions.
Parts available for DIY constructors.
Circuit diagrams and construction details for many types of valve amplifiers.
Valve equipment repairs. Lancroft Pty
Ltd, PO Box 439, Bexley 2207. Phone
(02) 567 5390.
UNUSUAL BOOKS: Electronic Devices, Fireworks, Locksmithing, Radar
Invisibility, Surveillance, Self-Protection,
Unusual Chem
istry and more. For a
complete catalog, send 95 cents in
May 1994 95
ICL 286 Board
Kits
All in one board with two serial,
printer, IBM keyboard, high
density floppy & IDE mono
video interface. Up to 4Mb
RAM, 80286-16cpu, MS-DOS
compatible, 130 page manual,
small size 170mm x 255mm.
Max I/O kit for PCs, 7 relays,
ADC, DAC, stepper driver, TTL
inputs, with software
$169
PC I/O card with 8255 chip 24
I/O lines programmable as inputs
or outputs
$69
1.5 watt AM broadcast transmitter XTAL locked
$49
2.5 watt FM broadcast transmitter 88-108MHz.
$49
Digi-125 audio power amp
(over 19,000 sold since 1987)
50 watt/8 $14 125 watt/4 $19
New 200 watt/2 version $29
Infrared relay kit
$9
Remote control tester
$4
$299
Ampo little PC
All in one NEC V40 CPU board,
MS-DOS compatible, high density floppy. SCSI hard disk, 2
serial, printer, solid state hard
disk, IBM keyboard interface,
(4W), CMOS single +5V rail,
up to 768Kb RAM, 384Kb
ROM, 145mm x 250mm, 98page manual.
$299
P.C. Computers
36 Regent St, Kensington,
SA. Phone (08) 332 6513.
stamps to Vector Press, Dept S, PO Box
434, Brighton, SA 5048.
BINARY CLOCK - OCTOBER 1993:
complete documentation supplied,
includes introduction to binary, how it
works, PLD source listings, conversion
tables. Kit with PCB and all components
$75 + $5 p&p. Optional Z frame stand
(includes spacers and chassis DC connector) $25 + $5 p&p. Prototype Electronics, 1/29 Stewart St, Parra
matta,
NSW 2124. Phone (02) 683 3510; Fax
(02) 630 3148. Pay by cheque, money
order, credit card.
SUBSTITUTE FOR A HANDFUL OF
ICs: Parallax “BASIC STAMP”. A general
purpose small circuit module, it is really
a 25 x 50mm board with a computer
chip (4MHz PIC 16C56), EEPROM, 8
I/O pins, board space includes prototyping area. Program it on a PC (only
CTOAN ELECTRONICS
4-channel piped music system for your
home. Hundreds of dollars cheaper than
commercial systems. Build it yourself and
save heaps. Ring for details.
PO Box 211, Jimboomba 4280.
Phone (07) 297 5421.
Advertising Index
Altronics ................................ 76-78
Antique Radio Restorations.........94
Av-Comm.......................................9
Ctoan Electronics........................96
David Reid Electronics ..............73
33 instructions) with development kit
which includes one “BASIC STAMP”
($249 plus S/T & post), extra modules
($66 plus S/T & post). Send 45c stamp
for more information. Parallax distributor and technical support in Australia:
MicroZed Computers, PO Box 634,
Armidale, NSW 2350. Facsimile (067)
72 8987.
Dick Smith Electronics........... 10-13
Electronic Fault Info.....................61
Harbuch Electronics....................73
Instant PCBs................................95
Jaycar ................................... 45-52
Kalex............................................75
PRINTED CIRCUIT BOARDS for the
hobbyist. For service & enquiries contact: T. A. Mowles (08) 326 5590.
L & M Video.................................26
MICASOFT Electronics and Computing
tutor program, written in UK, ideal for
TAFE, schools, or individual use. Now
available in Australia. Send $1.80 in
stamps for demo disk (tell us what size).
MicroZed Computers, PO Box 634,
Armidale 2350.
PC Computers........................63,96
WANTED
Secontronics................................95
HANDBOOK & SCHEMATICS for
Advance Instruments pulse generator model PG52. (Local agents were
Jacoby Mitchell.) Phone Steve Dolding
(02) 888 4883 B.H. or (02) 871 1073
A.H.
McLean Automation.....................72
Oatley Electronics........................23
Pelham........................................95
Plough Book Sales......................95
RCS Radio ..................................94
Rod Irving Electronics .......... 27-31
Silicon Chip Back Issues....... 84-85
Silicon Chip Projects Book......OBC
Silicon Chip Software.............93,96
Silicon Supply & Manufact...........95
Telecom Australia........................71
Transformer Rewinds...................95
SILICON CHIP FLOPPY INDEX
WITH FILE VIEWER
Now available: the complete index to all SILICON CHIP articles
since the first issue in November 1987. Now you can search
through all the articles ever published for the one you want.
The index comes as an ASCII file on a 3.5-inch or 5.25-inch floppy disc to suit
PC-compatible computers and you can use any word processor or our special
file viewer to search for keywords.
Now with handy file viewer: the Silicon Chip Floppy Index now comes with
a file viewer. You can look at the index line by line or page by page for quick
browsing, or you can make use of the search function.
Simply enter in a keyword(s) and the index will quickly find all the relevant
entries. All commands are listed on the screen, so you’ll always know what to
do next. Note: requires CGA, EGA or VGA graphics card, IBM-compatible PC,
MSDOS 3.3 and above.
Price $7.00 + $3 p&p. Send your order to: Silicon Chip Publications, PO Box
139, Collaroy 2097; or phone (02) 979 5644 & quote your credit card number;
or fax the details to (02) 979 6503. Please specify 3.5-inch or 5.25-inch disc.
96 Silicon Chip
Tektronix....................................IFC
West Tech Industries.................IBC
Yuga Enterprise...........................17
_________________________________
PC Boards
Printed circuit boards for SILICON
CHIP projects are made by:
• RCS Radio Pty Ltd, 651 Forest
Rd, Bexley, NSW 2207. Phone (02)
587 3491.
• Marday Services, PO Box 19-189,
Avondale, Auckland, NZ. Phone (09)
828 5730.
• H. T. Electronics, 35 Valley View
Crescent, Hackham West, SA 5163.
Phone (08) 326 5590.
WEST TECHTRONICS
WEST TECHTRONICS
UP TO 14-DAY MONEY BACK GUARANTEE
OTHER PRODUCTS AVAIL:
DEALERS REQUIRED IN ALL STATES.
PLEASE APPLY IN WRITING ONLY.
PLACE YOUR ORDER BY PHONE, FAX OR
POST. DEALER & TRADE PRICES AVAIL.
UP TO 1kg $4.50; UP TO 5kg $6.50.
O/NITE & OTHER FREIGHT PLEASE CALL.
SYSTEMS WITH 2YR WARRANTY
4M RAM, 210M HD, 1.44 OR 1.2 FDD, 1M
SVGA CARD, 14" SVGA MONITOR 0.28DP, 101
KEYBOARD, 2S/1P/1G, 200W P.S. & EPSON
PRINTER LX-400.
386DX-40 128K CACHE .............................$1750
486DX-33 258K CACHE & 3 VL/B S ...........$2260
488DX2-66 256K CACHE & 3 VL/B S .........$2570
PLEASE CALL FOR ANY CONFIGURATION AT
THE BEST PRICES
NOTEBOOK 386SX-33, 4M RAM, 120M HD,
VGA LCD-32 GREY SCALES, 1S/1P/1VGA/1KBD/1PS/1 SCANNER PORT, CARRY CASE,
BATTERY & CHARGER ..............................$2195
DOS 6.2 & WINDOWS 3.11 ..........................$169
MULTIMEDIA PERFORMANCE PACK .........$769
S/BLASTER 16 BIT WITH ASP .....................$439
COMPUTER ACCESSORIES
VGA
CARD
CABLES - MADE TO STANDARD; WE CAN
MANUFACTURE CABLES TO YOUR SPECS
IBM PARALLEL PRINTER CABLES:
2M $4.00 5M $9.00, 10M ...........................$18.00
2M RIGHT ANGLED PLL P CABLE ...........$10.00
25 CORE STRAIGHT THRU CABLES
D25M-D25M; 2M $5.50, 5M .........................$9.00
D25M-D25F; 2M $5.50, 5M ..........................$9.00
D9F-D25M MODEM 2M ...............................$5.50
D15 HIGH DENSITY M-M OR M-F ............$14.00
SCSI CBLE 1M; 50 CENT. M-M .................$28.00
MAINS TO MONITOR IEC 2M .....................$8.00
MONITOR TO PC IEC 2M ............................$8.00
FDD POWER SPLITTER CBLS; 3.5"-3.5", 3.5"5.25", 5.25"-5.25", 5.25" Ext. ........................$5.00
ETHERNET CABLES - 50 OHM COAX:
2M . . $8, 5M . . $15, 10M . . $25, 20M . . $37
TELEPHONE ACC. ARE TELECOM APPRVD
FAX/PHONE SWITCH ...................................$155
ANSWERING MACHINE AV130 ...................$130
MUSIC ON HOLD ...........................................$49
AUST. INLINE PLUG. $2, SCKT. ..................$2.00
AUST. WALL SCKT. $2, ...........DBLE ADPT $3.50
AUST. PLUG - UD MOD. SCKT. ...................$3.00
AUST. SCKT - US MOD. SCKT. ....................$3.00
TEL. CRIMP TERMINALS 20 pack ..............$1.00
AUST. TELEPHONE EXT. LEADS:
3M . . $6, 5M . . $8 10M . . $9 15M . . $10
AUST. TO US PLUG EXT. LEADS:
5M . . $6, 10M . . $7, 15m . .$8
US MODULAR EXTENSION LEADS:
5M . . $4, 10M . . $5, 15M . . $6
HANDSET CURLED CORD 4M ........................$5
TEL. CABLE: 4 CORE FLAT 100M ..................$35
MAINS POWER ACCESSORIES:
WITH ENERGY AUTHORITY APPROVAL
SURGE PROTECTION POWER BOARDS:
4 WAY OUTLET $28, 6 WAY OUTLET ............$33
10M MAINS EXTENSION LEAD .....................$11
MAINS FLASHING STROBE ..........................$35
DC POWER ADAPTORS/SUPPLIES:
PANTHER POWER SUPPLIES-REG.:
240VAC: <at> 2A CONT. $59, <at> 4A CONT. .......$79
240VAC/300MA <at> 3,4,5,6,7,5,9 12VDC .........$15
240VAC/500MA <at> 3,4,5,6,7,5,9 12VDC .........$19
12VDC/800MA <at> 3,4,5,6,7,5,9, 12VDC .........$15
WEST TECHTRONICS
PLUGS, SOCKETS & PLUG ADAPTORS
BNC PLUG/RCA SCKT. ...............................$2.50
PL259 PLUG/RCA SCKT. .............................$2.50
BNC SCKT./BNC SCKT. ...............................$3.00
BNC 3 SCKTS.-T PIECE ..............................$4.50
3.5MM PLUG/TV COAX SCKT. ....................$1.30
RCA PLUGS RD, BLCK, WHITE, YLW. ........$0.40
TV METAL COAX PLUG $1.30, SCKT. ........$1.30
TV COAX PLASTIC INLINE JOINER ...........$1.30
TV COAX MALE/MALE JOINER ..................$1.30
TV RIBBON 2 PIN PLUG - 3MM ..................$1.30
BNC CRIMP PLUG FOR RG58 ...................$2.50
TNC CRIMP PLUG FOR RG58 ....................$3.00
CB MIC 4 PIN PLUG, FEMALE ....................$3.00
CAR RADIO ANT. PLUG INLINE .................$1.30
AUDIO 6.5MM MONO PLUG, RED, BK. ......$0.90
AUDIO 3.5MM STEREO PLUG BLCK. ........$0.90
AUDIO 3.5MM STEREO SKT. & STRN. .......$1.10
HARDWARE, TRANSFORMERS & TOOLS
ALLIGATOR CLIPS 32MM RED, BLCK. .......$0.40
AUTO RELAY SPST 12VDC/30 A ................$5.50
GROMMETS: 9.7 x 6.0mm CBLE HOLE .....$0.17
..........................12.7 x 9.5mm CBLE HOLE $0.22
5A FUSES 3AG, M205 TYPES ....................$0.17
3AG FUSE HOLDER CHAS MNT. SRW ......$1.20
AC POWER TRANSFORMER 2155 ............$9.00
HOBBY KNIFE SET WITH 5 BLADES .........$3.00
COAXIAL STRIPPING TOOL-RG58,59 ..........$15
4-PCE JWLERS S/DRVR SET PHILPS ............$5
TELEVISION ACCESSORIES
INDOOR BALUN 300/75 TV SCKT. ..............$1.30
INDOOR BALUN 300/75 TV PLUG ..............$1.10
75-OHM BAND SEPARATOR UHF/VHF ......$4.00
2-WAY 75 OHM COAX SPLITTER BOX ......$3.50
4-WAY 75 OHM COAX SPLITTER BOX ......$4.50
KINGRAY MASTHEAD AMPLIFIERS:
MHU34T MSTHD. AMP. - UHF 34DB ..............$55
MHW34T MSTHD. A.-UHF/VHF 34DB ............$55
MH21 POWER SUPPLY ..................................$55
BATTERIES AND ACCESSORIES
NICAD CHRGR & T AAA.AA,C,D,9V ..............$23
BATTERY HLDRS: 2XAA, 4XAA ..................$0.50
SHARP V/CAM BATRY PK BT-75 ...................$79
MOTOROLA T/TALKER BAT. 12V/4A ..............$99
MOTOROLA FLIP PH FAST CHGR/CND .....$180
WEST TECHTRONICS
WEST TECHTRONICS
GENDER CHANGES & ADAPTORS:
D9: MALE-MALE, FEM.-FEM. ......................$4.00
D25: MALE-MALE, FEM.-FEM. ....................$6.50
D15 HIGH DENSITY M-M, F-F ....................$7.50
6 MINI DIN MALE - 5 DIN M OR F ...............$7.50
D9M-D15HD F, D9F-D15HD M ....................$6.50
D9M-D25M, D9M-D25F ...............................$5.00
D95-D25M, D9F-D25F .................................$5.00
HIGRADE DISKS; BX/10 3.5" DSHD ...........$9.50
MOUSE; 3 BUTTON MS COMP .................$19.50
IBM M/S MOUSE & PS2 CONVTR ...............$115
MATS: RED, BLUE OR GREY ......................$5.00
101 KEYBOARD .............................................$35
FAX MODEM; NETCOM ...............................$349
MONT; 14" SVGA 0.28DP 1024X768 ...........$490
PANASONIC FLOPPY DISK DRIVES:
1.44MB $70, MNT. KIT $9, 1.2MB ...................$86
HARD DRIVE IDE V/C 340M 13MS ..............$520
SIMM; 1M 9-70 $70 4M 9-70 .........................$290
M/BOARDS: 3 VL/B SLOTS & 256K CACHE;
488DX-33 $689; 486DX2-88 .........................$945
CARDS: GAMES CARD .............................$19.50
ETHERNET 16 BIT (NE2000 COMPAT.) .......$285
VL/B CIRRUS LOGIC SVGA 1M W/A ...........$160
IDE I/O CARD IDE HD/FDD/2S/1P/1G ...........$35
GAME CARD ..............................................$19.50
VGA CARDS; VLBUS VGA ACCEL. ..............$175
TRIDENT 3900 1MB SVGA CARD (ISA) ......$125
PRINTER CANON 10EX B/JET SQUIRT .....$495
ETHERNET
ADAPTER
SCSI DRIVES, CASES, NETWORKING, FIBRE OPTICS,
LAB POWER SUPPLIES, TEST
GEAR, EDUCATIONAL PANELS,
RADIO CONTROL DEVICES,
LASER ACCESS. ETC.
WEST TECHTRONICS
WEST TECHTRONICS
TEL: (02) 872 2847, FAX: (02) 872 5329. PO BOX 336, NORTH RYDE 2113.
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