This is only a preview of the September 2017 issue of Silicon Chip. You can view 59 of the 112 pages in the full issue, including the advertisments. For full access, purchase the issue for $10.00 or subscribe for access to the latest issues. Items relevant to "Fully adjustable, 3-way active loudspeaker crossover Pt.1":
Items relevant to "Dead simple radio IF alignment with DDS":
Items relevant to "LTspice Tutorial Part 3: Modelling an NTC Thermistor":
Articles in this series:
Items relevant to "Arduino Data Logger Part 2":
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Contents
Vol.30, No.9; September 2017
SILICON
CHIP
www.siliconchip.com.au
Features & Reviews
16 Commemorating Cassini’s demise and Sputnik’s birth
The Cassini spacecraft will be deliberately plunged into Saturn this month, to
certain destruction. It’s had a remarkably successful mission. We also look at
the world’s first man-made satellite, Sputnik, 60 years on – by Ross Tester
40 This month: Melbourne’s turn for Electronex Expo
Australia’s only dedicated electronics design and assembly industry expo and
conference returns to the Melbourne on September 6 and 7
61 The unclear future of radio broadcasting in Australia
Did you know the ABC turned off its shortwave transmitters in January, leaving
vast areas of Australia without a viable radio service? AM, FM and DAB+ don’t
stand a chance – so where do we go from here? – by Alan Hughes
63 Digital Radio Mondiale (DRM): what’s it all about?
Cassini is about to be crashed
into Saturn’s atmosphere,
sending back valuable data
until its last moments – Page 16
DRM could be the solution for continent-wide broadcasting and beyond –
with excellent quality and can even be in stereo. It’s a much better proposition
than anything else and its cost would be minimal – by Jim Rowe
78 LTspice Tutorial Part 3: Modelling an NTC Thermistor
We show how to simulate this tricky non-linear device – by Nicholas Vinen
Constructional Projects
24 Fully adjustable, 3-way active loudspeaker crossover
Want more than a boring passive crossover? Build this one! The crossover
points and levels for tweeter, midrange and woofer are fully adjustable with
separate level controls for each driver – by John Clarke
You may not have even heard of
DRM – Digital Radio Mondiale –
but it’s already in use in many
overseas countries. Why not
here in Australia? – Pages 61/63
66 Dead simple radio IF alignment with DDS
Gone are the days when aligning a superhet radio IF took lots of gear and time:
this Maximite-based DDS module makes short work of it. And it’s really simple!
A must for all our (many!) vintage radio enthusiasts – by Nicholas Vinen
86 An Arduino Data Logger with GPS, Part 2
Here’s the description of how the software works and how it all goes together
with a custom shield – by Nicholas Vinen
92 Arduino “ThingSpeak.com” ESP8266 data logger
It’s easy to log data to the cloud using an Arduino – by Bera Somnath
Repairing, restoring or even
building AM superhet radios? You
want this simple DDS IF Alignment
Unit – Page 66
94 El Cheapo modules Part 9: AD9850 DDS module
It can be programmed to produce sine and square waves from 0.0291Hz to over
62MHz in tiny increments – by Jim Rowe
Your Favourite Columns
36 Circuit Notebook
(1) Automatically rebooting NBN modem each night
(2) LIDAR rangefinder with Arduino
(3) Level shifting the output of the High-Temperature Digital Thermometer
73 Serviceman’s Log
Not just one but two Arduino data
logger projects this month,
including storing data in the
cloud – Pages 86/92
When a GPS loses its way – by Dave Thompson
100 Vintage Radio
The 3-transistor Philips MT4 Swingalong – by Ian Batty
Everything Else!
2 Editor’s Viewpoint
4 Mailbag – Your Feedback
siliconchip.com.au
104 SILICON CHIP Online Shop
106 Product Showcase
107
111
112
112
Ask SILICON CHIP
Market Centre
Advertising Index
Notes and Errata
Australia’s largest electronics expo
is on this month in Melbourne – and
you’re invited! Get your free entry at
www.electronex.com.au – Page 40
September 2017 1
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2 Silicon Chip
Editorial Viewpoint
A rapid shift to electric vehicles
could be disastrous
Norway and the Netherlands have announced that they
plan to ban the sale of vehicles powered by Internal Combustion Engines by 2025, Germany by 2030 and the UK
by 2040. China is forcing automobile manufacturers to
sell a percentage of vehicles as electric only and India is
talking about banning the operation of petrol and diesel
vehicles altogether in the future.
Leaving aside the question for now of whether it’s feasible to manufacture the
batteries required for all these vehicles in the time frames given, there are still
two significant hurdles which are likely to frustrate these plans.
Firstly, electricity generation and distribution would likely need to increase by
up to and 40% (depending on what assumptions you make) and most sources of
renewable energy would not be suitable without backup, due primarily to mismatches between availability and demand.
Natural gas is currently in short supply in Australia, nuclear fission is unpopular and coal is actively being discouraged. That doesn’t leave us a lot of options
for providing the extra energy needed to run a large fleet of electric vehicles.
But there’s potentially a more serious issue. Have any of the people behind
these plans stopped to consider what would happen in the event of a natural
disaster or a major disruption to the electricity grid? We all know from recent
experiences that neither of these scenarios is unlikely.
These days, blackouts of relatively short durations (ie, up to a few hours) are
frustrating but life can generally go on until the power comes back on. That may
not be so if transportation becomes utterly dependent on the electric grid.
Worse, imagine what would happen if the power goes out for a week or more,
due to a flood, cyclone, earthquake, major bushfire or similar event.
At the time of the disaster, some vehicles will have a fully charged battery that
may be good for several hundred kilometres of travel. Some will have a smaller
battery or be partially charged while others will be close to depleted.
How will people flee from the affected areas? How will food and medicine be
delivered? How will debris be cleared and people rescued? Even if emergency
vehicles were still liquid fuelled, they would have to bring their own re-fills.
Many are now saying that ICE-powered vehicles are obsolete but they do have
some distinct advantages. Even if you don’t keep your tank full, chances are you
could drive a significant distance now if you absolutely had to. If you rely on an
electric car, you’d better make sure to keep it charged in case you need it.
We tend to take for granted the huge, distributed network of petrol stations
that we have. This network stores a lot of energy, is widely distributed and always available. There are challenges pumping fuel in a blackout but it can be
done, while electric charging stations are utterly useless when the grid is down.
And petrol stations can be also replenished during a blackout, as long as road
access is still available. We haven’t even mentioned (and don’t really want to
think about) the potential effects of a coordinated terrorist attack on power supply infrastructure in a city with electricity-dependent transportation.
Plug-in hybrids are a much better compromise than pure electric vehicles, with
the possibility of dramatically reducing fuel consumption without being totally
dependent on a functioning grid. They also make good financial sense. But banning petrol-powered vehicles would eliminate this option.
Perhaps electric charging stations should have backup generators. Sure, they
would not be able to charge many vehicles at a time but at least transportation
would not grind to a complete halt if the grid goes down for some time.
We wonder whether the central planners who are trying to ban ICE vehicles
have thought of and solved all these problems, or if they’re just taking a “damn
the torpedoes” attitude for which many innocent people may suffer when the
inevitable “unexpected” disaster occurs.
Nicholas Vinen
siliconchip.com.au
MAILBAG – your feedback
Letters and emails should contain complete name, address and daytime phone number. Letters
to the Editor are submitted on the condition that Silicon Chip Publications Pty Ltd may edit and
has the right to reproduce in electronic form and communicate these letters. This also applies to
submissions to “Ask SILICON CHIP”, “Circuit Notebook” and “Serviceman”.
Why are the SPICE tutorials
based on the SoftStarter?
I have a resounding Bravo for Nicholas Vinen for his introduction of LTspice XVII in your recent issues! But
why the obsession with his passivelyrepresented SoftStarter circuit with
pages elaborating on a relay, with a
thermistor to follow (or am I just getting impatient)?
Interesting as these may be, the
SPICE acronym, with its deliberate
emphasis on ICs, begs for an introduction to designing and testing amplifiers, active filters, oscillators, precision
rectifiers etc, and delving into AC circuit analysis, Bode plots and the like.
Such an approach could help your
August correspondent Andrew Pullin,
with whom I sympathise. As to Andrew’s appeal for introductory topics
in your magazine, I remember being
helped and encouraged in my youthful
studies by Wireless World magazine,
now sadly missed.
Wireless World struck a happy balance between assumed basic knowledge (now copiously available on the
Web), step-by-step constructive design
and polished circuits with detailed
walkthroughs and constructional information. Silicon Chip does this rather well but to my mind could improve
on the former, more basic aspects.
Of course, we never cease learning,
especially with the tsunami of technological progress. So my question to
Nicholas asks if there is a convenient
way to correlate the various SPICEcoded ICs with conveniently available
retail items? It would greatly ease the
path from simulation to actual prototype construction.
John Gale,
Beecroft, NSW.
Nicholas replies: I started with the
SoftStarter circuit because I thought
it would provide a gentle introduction for beginners to SPICE, with its
relatively simple circuit, as well as
an opportunity to delve into the inner workings as we build the relay
4 Silicon Chip
and thermistor models. I also wanted
to show how handy it is to be able to
simulate circuits at mains potential,
since it’s so difficult (and dangerous)
to probe the real device.
Relays are arguably the single most
common and useful component missing from LTspice, so I thought it would
be considerably helpful to readers to
provide a working model as well as
take them through the process so they
can understand how to build their own
subcircuits for other components that
are missing from the libraries.
The Thermistor model, published
this month, turned out to be a great
(albeit complex) vehicle for delving
into the more esoteric parts of SPICE
and many of the building blocks and
techniques demonstrated in that article will be handy for simulating many
other types of devices and ICs.
As stated at the end of the this
month’s article, we will get into audio
circuits and ICs (especially op amps)
in the next SPICE tutorial. We will also
describe simulating filters and doing
AC circuit analysis. Over time, we
hope to cover all the useful aspects of
LTspice, so that readers are confident
in simulating their own circuits (and
ours too).
Most IC manufacturers have provided SPICE model downloads, from
their websites, for a subset of their catalog for some time now, however, we’ve
encountered difficulties getting these
to work on many occasions.
Some are encrypted while others
only work with specific SPICE software. Many turn out to be quite crude
and don’t simulate the IC’s behaviour
very accurately.
Larger online retailers such as DigiKey, element14 and Mouser now provide download links to SPICE models
for their products, if available.
If you’re serious about simulating prototypes, for these reasons and
more, you will often find that you have
to build your own models. That’s why
we’ve concentrated on this aspect of
SPICE in the last couple of tutorials.
With the requisite knowledge, you
can take a generic device (eg, an op
amp) and adjust its parameters according to the device’s data sheet, to
at least approximate its behaviour.
For the simpler ICs, you can build
your own models from scratch.
LED lamp life falls short of expectations
Your article entitled “LED Downlights and Dimmers” in the July 2017
issue (www.siliconchip.com.au/
Article/10712) was informative and
useful. However, it could have been
more so if the life of LED lamps and
luminaires had been canvassed.
There was one brief mention of this
in the caption under an image of two
downlights on page 28, where it was
stated that their rated life is 25,000
hours. It is my understanding that this
life is really the elapsed operating time
when the light output will have fallen
to 0.7 of the value when new, and not
the actual time to failure.
This matter is raised because of
problems being experienced with
LED ceiling luminaires installed in
the stairwells of the unit block where
I reside. A figure of 35,000 hours is
claimed for these lights on the packaging and data sheets, but they have
been failing after approximately
10,000 hours.
That wouldn’t be a problem if the
luminaires contained LED globes that
could be replaced by lay persons but
instead there is a non-replaceable
LED array and a switchmode power
supply. The result is that we have to
discard the complete luminaire and
the lighting supplier happily sells us
a replacement; not to mention that the
changeover must be done by a qualified electrician.
I have been advised unofficially
that our luminaires are not suitable
for continuous operation all night, an
siliconchip.com.au
Mailbag: continued
More on measuring lamp brightness
I previously wrote a letter to
S ilicon C hip on measuring the
brightness of LED lamps, which was
printed in the Mailbag section of the
July 2017 issue (pages 12 & 14; www.
siliconchip.com.au/Article/10701).
After that, I decided to get a real
lux meter from eBay which only cost
$14.79, since it would be difficult
to build anything for less than that.
This is what I purchased: www.ebay.
com/itm/162361509733
With the operating instructions,
there is a table of suggested readings
but it does not tell you the distance
from the lamp. As one might know,
as you double the distance from
average time of 12 hours over a year,
but this is not stated on the packaging
or data sheet.
Standards bodies and the lighting
industry must get this matter sorted
out. Preferably, manufacturers should
be required to produce luminaires that
endure up to 0.7 initial output.
If not, they should be required to
include more information on packaging and data sheets to make purchasers aware of any limitations. Perhaps
Silicon Chip might consider these
issues in a future article.
Russell Howson,
Bronte, NSW.
Editor’s note: consider that even if the
35,000-hour figure is the mean time between failures (MTBF) for that lamp,
that doesn’t mean you won’t get failures after a shorter period.
After all, it’s an average figure; it
could mean that half the lamps are
expected to fail after 10,000 hours
while the other half continue on for
60,000 hours.
We too have noticed trend towards
LED light fittings with lamps that can’t
be replaced by the user and it seems
unfortunate. Possibly, the reason they
don’t want you using the lamps twelve
hours a day is because that way, you
will quickly figure out that they don’t
last very long!
We would recommend using standard bayonet fittings with LED bulbs in
that sort of situation. They’re avail6 Silicon Chip
light source, the lux reading falls to
one quarter.
An article comparing different
lamps and their efficiencies might
make a good follow-up to your article on LED Downlights and Dimmers from the July issue (www.
siliconchip.com.au/Article/10712).
By keeping the meter in the same
place (just over 150cm from the light
source and not directly in-line) I got
the following readings:
13W LED: 80 lux
140W incandescent: 240 lux
23W CFL: 16 lux at switch-on,
creeping up to 53 lux
Eric Richards,
Auckland, New Zealand.
able in a range of brightnesses, are
still very efficient and residents and/
or cleaners could then easily (and
cheaply) replace any that fail. Economies of scale are on your side if you
use standard bulbs.
Spring Reverb DC power supply error
I just built up one of your new
Spring Reverb controllers (April
2017; www.siliconchip.com.au/
Article/10610) and noticed an error
with the power supply.
The diode used in the DC version
doesn’t connect to the barrel jack because it’s on the opposite AC leg of the
bridge. This means that the DC barrel jack is unusable unless the diode
bridge is fitted.
The diode can easily be moved to
use the other AC bridge leg, and the
jack will work, but in this instance the
positive supply should be fed into pin
3 of CON5 instead of pin 1.
The component overlay picture for
the DC supply can’t use the barrel jack,
but will otherwise work.
A simple solution would be to just
fit the bridge rectifier in either circumstance, ignoring the diode.
Thomas Skevington,
Perth, WA.
Comment: you are right, we connected
the anode of the diode to the AC input that isn’t connected to the barrel
jack and fitting BR1 for a DC supply
would solve this.
Alternatively, solder a link between
pins 1 and 3 of CON5 (being careful
not to short to pin 2) or fit a 3-way terminal block for CON5 and place a wire
link between pins 1 and 3.
Notes & Errata for this were published in the June 2017 issue.
Worried about “Internet of Things”
being hacked
For a long time, I have thought
that using the internet for controlling power stations, keeping records
of all kinds, carrying out banking and
other financial transactions and in so
many other places and ways is not
only wrong but downright stupid. In
fact, every time things go wrong, my
first thought is: why are people so
surprised?
I have read and listened to my
friends all telling me how the future
is the morphing or merging of devices.
I was told that separate computers,
phones, television sets would all become one device.
The list then got longer by adding
the refrigerator, the washing machine,
the toaster, the vacuum cleaner and
more and in the new order, they would
all become one.
And generally, the common element was being connected to the internet. The internet is the public toilet
of communications; you might hear
something you would not hear anywhere else but it is, just like a public
urinal, dirty.
As an example, the thousands of
switches (generally at the 11kV level)
located in the substations, for most of
the life of the grid, were controlled by
dedicated phone lines or dedicated
microwave links. Almost all these controls, worldwide, are now via devices
using the internet.
This makes it a bit cheaper and yet
it would only take one very bad hack
to cause damage that would exceed by
many times the savings of using the
internet as opposed to the old way of
controlling these switches.
Anyone who resists internetisation
in all sorts of situations no doubt
would find their career severely cut
short for not being forward-thinking.
In fact, no one seems to question the
siliconchip.com.au
C
M
Y
CM
MY
CY
CMY
K
siliconchip.com.au
September 2017 7
Mailbag: continued
Helping to put you in Control
Pressure/Temperature Transducer
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4-20mA Current Transducer
The KTA-366 is a current
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U6 Data Acquisition Module
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device with 14 analog
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S Type Load Cell 0-500Kg
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Programmable Stepper Pulser
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Large Temperature Display
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For Wholesale prices
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Ph: (03) 9782 5882
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Prices are subjected to change without notice.
8 Silicon Chip
wisdom of using the internet in these
situations.
A modern army is controlled by
emails. Naturally, all sorts of encryption is used and frequently, the communication pathways are not the public internet.
Yet a lot of the equipment shares
many elements that are functionally
ubiquitous with the rest of the community and the internet itself is sometimes used.
My notebook was purchased from a
shop that had won a contract to supply 2000 notebooks to somewhere in
defence. The shop bought 300 more
all at a good price and I bought one.
How could anyone be sure there was
no phone-home hardware or software
capabilities in such a device?
One of the largest entities to be attacked on May 12th, 2017 was the NHS
in the UK. I have read that 90% of the
British National Health Service still
uses Windows XP and that the “problem” was that these “old” systems have
vulnerabilities. What a lot of rubbish.
The problem was using Windows in
the first place.
The great strength of Microsoft is its
open nature. Anyone can write add-on
software and therefore so can a hacker.
Maybe not all but many of the socalled vulnerabilities of all the versions of Windows in my mind are
not mistakes but rather deliberate
portholes put in the operating system
that can be used by security services
when required.
Unfortunately, all systems leak and
knowledge of these portholes got out
and known to people who exploit them
for no good. The so-called patches really are patches to close over these
openings.
Bank and hospital records, power
stations and grids, water supplies and
all infrastructure and all the other really important things in our life should
not use the internet and equipment
using Microsoft or Apple or the like.
The internet has its place but like the
public toilet it is impossible to make
it suitable for managing the key elements in our life.
The first thing that needs to change is
the mindset that suggests that using the
internet and something like Windows
is modern and clever and that doing
things this way is progress.
They might be good for keeping my
grandchildren amused but they are inappropriate to open and close the 11kV
switches at my local substation. There
are no fundamental problems; all that
needs to change is the group-think that
suggests this is progress.
Ken Moxham,
Urrbrae, SA.
Editor’s note: we have commented
about the lax security of “Internet of
Things” devices (including cars and
pacemakers!) in past issues.
But we do not think that securing
devices accessible over the internet is
impossible; merely that most companies selling internet-connected products have insufficient incentive to take
security seriously.
Redesigned LED traffic lights
could save money and space
As in most cases no two lights in a
given set of three are on at the same
time, traffic management signals could
be incorporated within a single display.
Two-thirds of the individual lights
now used would become redundant.
Millions of dollars in savings are there
for the taking. A single display needs
to only change its colour.
The colour-blind could still read the
signal if each colour also had a unit
shape. For example, stop could be a
red square, go a green circle and prepare to stop an amber star. Direction
arrows etc could have their coloured
arrow symbol in a separate display.
At present, in Queensland, typical intersections can have some forty
to seventy separate displays and this
makes for a somewhat ugly road-scape.
Am I dreaming, or is it technically
complicated? Could a small colour
monitor be used?
H. Wrangell,
Elimbah, Qld.
Editor’s response: it isn’t technically
difficult and in fact, if you go to China,
you will see lights similar to what you
have described.
They are animated LED arrays and
even count down how long you have left
before the light changes (red to green,
siliconchip.com.au
siliconchip.com.au
September 2017 9
Mailbag: continued
Bill being introduced to federal parliament in attempt to
restore ABC shortwave services
On the 31st of January 2017, the ABC switched off
all high frequency (shortwave) broadcasts. This included ABC Territory Radio covering all of NT and
beyond as well as Radio Australia to the Pacific and
Papua New Guinea.
This has left many in the outback with no Australian
radio at all, particularly when in vehicles or boats. Senator Xenophon has introduced a bill which is designed
to force the ABC to restore high frequency broadcasts.
The ABC have had two Digital Radio Mondialecapable transmitters which have never broadcasted in
this mode. They enable FM stereo sound quality over
huge areas with the ability to transmit image and multipage text along, with an Emergency Warning System
(see www.drm.org for more details).
For more information about the proposed bill, see:
http://siliconchip.com.au/l/aaen (“Australian Broadcasting Corporation Amendment (Restoring Shortwave
Radio) Bill 2017”).
Alan Hughes,
Hamersley, WA.
Editor’s Note: see the article about DRM on page 61
of this issue.
10 Silicon Chip
green to red etc). Even some pedestrian crossings in Australia have count-downs.
Internet of Things hazards and serial error checking
I agree with most of what was stated in the Publisher’s
Letter of November 2016. Australia has a number of positives for running a business. It is just a pity that some government polices are so hostile to business. Of course, in the
end, we, the people, lose.
The November 2016 issue also had a good collection of
letters and articles. One article, on the Internet of Things
(“IoT”) by Ross Tester, deserves some comment. Aside from
being a nicely written article, its subject does worry me.
It seems to be another case of having technology and looking for a way to use it. Just to justify my dislike, my friend
sent me an email concerning the hacking of Philips Hue
smart light bulbs which are controlled using ZigBee wireless.
Some researchers decided to test the system security
and created a Zigbee worm which they proved was able to
spread within minutes.
However, the problem was corrected by Philips before the
paper was released. Even so, it is a wake-up call. I do not
have a link to the research paper but its title is: “IoT Goes
Nuclear: Creating a ZigBee Chain Reaction” and the authors
are; Ronen, O’Flynn, Shamir, and Weingarten.
Just imagine the problems that could be caused with the
use of IoT in healthcare. Already one vendor has had to
patch their pacemakers because hackers could potentially
break in and control the patient’s heart rate!
In the mailbag section of the October 2016 edition of
Silicon Chip, a reader mentioned the LIN standard (“Using
CANBUS for home automation”). He just mentioned CAN
and LIN which are both used in cars.
Except for car technicians, I am probably one of only a
handful of people who would have recognised it. It is effectively a low speed, low-cost system for non-critical communication in cars.
It reminded me of one of the problems of networked micros. The problem is the synchronisation of the transmitter
of the sender unit with the receiver of the destination unit.
A few years ago, I designed a machine with a master controller and nine slave controllers linked with an RS-485 bus.
The longest cable was only a few metres and there was
very little electrical noise. Yet, faulty packet errors were occurring at about one in a thousand. With just two devices
talking to each other, there were no errors for hundreds of
thousands of packets but with three or more devices, there
were errors.
The solution came from a feature of the LIN standard.
Every LIN standard packet starts with a break character. It is
a purposely designed faulty character which is longer than
normal. When the destination unit receives this character,
a frame error is generated which is ignored. However, the
receiver is reset and is now ready for the start bit of the next
character to be sent.
If anyone is considering networking micros using RS-485,
implement packet communication and incorporate the LIN
siliconchip.com.au
siliconchip.com.au
September 2017 11
Mailbag: continued
July 2017 issue comments
I would like to make some comments about the July 2017 Silicon
Chip magazine issue.
1) The review of the Tecsun
S-8800 reads more like an advertising blurb rather than a review. I had
to check who the author was. Looking at the specs quoted on page 58,
I can see why it is an AM set. With
a quoted 5dB signal/noise ratio for
FM, I can’t see anyone wanting to
listen to it!
Also, the specification sheet says
output power with 10% distortion
is “> 450mW” yet in the text, it
refers to 2W of output power. That
must be a square wave with 100%
distortion!
There is no specification given for
the three different bandwidths mentioned in the text, which are presumably set by the “AM BW” knob – are
these IF filters?
There is mention of DSP in the text
but not what it does. Is it just used as
a fancy audio low pass filter to give
the 3 AM bandwidths or is it used to
do IF filtering & demodulation? The
review is mute on this point.
2) In the drawing of the Geeetech
VS1053 shield on page 74 it looks
like the green LED is connected to
the wrong line (SCK) whereas the
break character. I use PIC chips and the
later UARTs contain a bit, SENDB, in
the UART transmit status and control
register which is used to initiate the
break character.
With regards to the packet format,
there are a large number in use with
RS-485, including IP, UTP, FTP, HTTP,
CAN, USB, LIN etc but they all generally follow the format of leading dummy bytes, destination address, sender’s
address, number of data bytes, data,
checksum or CRC, and a termination
byte or bytes. A good packet system
with error checking can prevent a lot
of headaches.
George Ramsay,
Holland Park, Qld.
What about a digital graphic equaliser?
I noticed upon reading about the
12 Silicon Chip
text says it connects to the CS line.
3) Now after the brickbats, a plaudit! I thoroughly enjoyed the Vintage
Radio article on the DKE38 radio. It
was very much appreciated that the
reason/function of each component
was covered in detail, so I learned
something too.
However, there also seems to be
an error in the text or drawing. The
text on page 94 says “The amplified
signal is developed across the 2MW
resistor R3...”. But looking at the
drawing on page 93, the pin 1 anode load is marked R2 and is 200kW.
While R3, which is marked 2MW, is
a feedback resistor.
4) Enjoyed the article on LEDs and
dimmers which explained the issues
very well. Excellent, thank you.
David Williams,
Hornsby, NSW.
Editor’s note: a pure square wave has
a harmonic distortion of 48.3% but
we take your point. Power specifications at distortion levels above 10%
are not very useful since increasing
the volume beyond may not make
the sound any clearer.
The VS1053 shield circuit diagram is correct but the text is wrong.
You are correct about the discrepancy between the text and circuit
diagram.
new 10-band Graphic Equaliser by
John Clarke in the June and July 2017
issues (www.siliconchip.com.au/
Series/313) that it uses analog “set
and forget” sliders. Have you considered designing a digitally controlled
graphic equaliser like the AKAI EAA7 from the 1980s? Here is a YouTube video about it: https://youtu.be/
efvunFs4XkA
Maybe John Clarke can reverse engineer the AKAI EA-A7 and then duplicate his design in a digital form, or
at least add an LCD screen? Note that
in the video by Techmoan, the graphic
equaliser is used to help compensate
for unilateral hearing loss. The AKAI
EA-A7 has digital presets for both sides
of the stereophonic sound.
Many of your digital controlled projects use full colour LCD touchscreens.
Note the abundance of available features in the Akai EA-A7 graphic equaliser Yes, it only has seven bands but
it’s the way it is controlled. Note the
independent left and right control
pre-sets. Note the audio bypass circuit
when the Akai EA-A7 Graphic equaliser is off, so other stereo equipment
can keep functioning.
John Crowhurst,
Adelaide, SA.
Editor’s response: funny you should
bring this up as we are publishing
the first article on our new 2/3-way
Active Crossover in this issue and
we had quite an internal debate over
whether to use digital control or not
in that project.
The problem came down to this: digital control had numerous benefits such
as the ability to adjust the crossover
frequencies for both channels simultaneously using a single knob, however,
to get the same level of performance
as an analog project, it would make it
a lot more expensive to build.
That’s because you would need to
use many high quality digital pots to
give low noise and distortion, which
are quite expensive, plus a micro to
control them all, possibly a touchscreen and the low operating voltage of
low distortion digital pots would also
complicate the surrounding circuitry.
Or it could be done using digital
signal processing (DSP) but then to
avoid compromising sound quality
you would need a very high quality
CODEC which is also expensive, plus
a fairly serious processor and complex
software to drive it. In the end, the oldfashioned approach using ganged pots
and op amps seemed better overall.
We do appreciate digitally controlled equipment but it can be so
much more complex to design and
build. That, in combination with the
higher cost of parts would mean that
in all likelihood, fewer people would
build the design, even if the digital
version had more features.
So that’s why we have tended to stick
with analog designs for the moment.
But we wouldn’t rule out doing as
you suggest and designing a digitally
controlled or DSP equaliser/crossover/
etc in future.
siliconchip.com.au
siliconchip.com.au
September 2017 13
Mailbag: continued
Radio History under the hammer
Wideband
Communication
Receiver
ICOM5012
Multiple Digital
Mode Decode
Well-known radio collector and restorer Lou Albert is
putting his vast collection up for auction over the weekend of September 30 and October 1st.
Lou has one of the largest and most diverse collections
of vintage radios in the country. It covers everything from
Marconi to the mid-sixties. Myriad parts, literature, and
ephemera will be on sale in a parallel market set up at
the same venue. In total, there will be thousands of pieces
on offer.
Some of the items set for auction hark back to the dawn
of wireless experimenting in Australia. There is an original and primitive coherer receiver, which Lou believes to
have been part of the 1903-4 experiments at St Stanislaus
College in Bathurst, when Father Joseph Slattery transmitted Morse signals over a distance of three miles.
There are other items with indisputable provenance.
Father Shaw’s famous Maritime Wireless Company, established during 1911 in Randwick, Sydney, is represented
by a superb double detector crystal receiver. It is a faithful
replication of the Marconi Flexible Crystal Receiver (Type
16) and is clearly engraved with the legend “Royal Australian Navy, Randwick”. It dates to the First World War.
Introducing Icom’s newest wideband receiver,
the IC-R8600. Capable of receiving between
10kHz and 3GHz, the IC-R8600 will decode
diverse digital communication signals and the
advanced FPGA processing technologies will
ensure clarity and accuracy.
The fast moving, real-time spectrum scope
and waterfall function on the large TFT screen
allows the user to search for unknown signals
whilst scanning the bands.
To find out more about Icom’s products email
sales<at>icom.net.au
WWW.ICOM.NET.AU
14 Silicon Chip
siliconchip.com.au
Beyond these are other extremely rare Marconi sets for
both detection and amplification (the latter rather engagingly known as “Note Magnifiers”).
Most of the big names in early manufacture and retail are represented. Harrington’s and Levensons’, Wiles
Wonderful Wireless, Astor, Udisco, Colmovox, Healing,
Stromberg Carlson, Kriesler, Tasma, Airzone – the list is
comprehensive, and of course includes AWA.
The collection includes Bakelite and timber cathedral
radios, magnificent consoles, some of the most sought
after of rare and coloured Bakelites of the Art Deco era,
early transistor radios, as well as horn speakers, rare early
loop antennas, and some of the best early TRF sets you’ll
ever see.
Plus there are early gramophones, telephones and an
absolute plethora of parts and accessories: headphones and
Morse keys, early valves and components, microphones,
early crystal sets, literature; the list is almost endless.
The auction will be held in the Guides Hall, 6 Lamington Drive, Warners Bay, NSW (near Newcastle). Open for
inspection 8.00am both days, with the auction starting at
10.30am Saturday and 9.30am Sunday.
Further information is available on the HRSA website
at www.hrsa.asn.au
Richard Begbie,
SC
via email.
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siliconchip.com.au
September 2017 15
As we go to press, the 20-year-long mission of the Cassini-Huygens
space probe is reaching its spectacular climax. Cassini is entering some
of the last of its 22 weekly “dives” between Saturn and its rings, sending
back to Earth new and unique scientific data. At the end of the final
orbit, scheduled for 10:44am UTC on September 15th, Cassini will be
intentionally steered into Saturn’s gas clouds, almost certainly burning
up in a dramatic last hurrah. It is being destroyed for two main reasons:
it’s running very low on fuel and NASA wants to ensure it cannot collide
with (and possibly pollute) any of Saturn’s moons, thus affecting future
exploration.
Here we look at the remarkably successful Cassini-Huygens mission
and what it has meant to scientists back on Earth.
by ROSS TESTER
cassin
grand
16 Silicon
iliconCChip
hip
siliconchip.com.au
T
he name “Cassini Grand Finale” was chosen
from a public competition, reflecting its exciting
journey to date, while acknowledging that it’s a
big finish for what has been a truly great show. In fact,
NASA invited applications from the public to join it at
the Jet Propulsion Laboratory in Pasadena, California,
for a Grand Finale party on September 15 (sorry, you’re
too late to apply!).
In a 3.2 billion dollar collaboration between NASA,
the European Space Agency and Agenzia Spaziale Italiano – the Italian Space Agency. Cassini was
launched on October 14th 1997 and entered into orbit
around Saturn on 30th June 2014.
The two spacecraft are named after astronomers Giovanni Cassini and Christiaan Huygens.
Cassini/Huygens had several specific mission objectives:
• Determine the three-dimensional structure and
dynamic behavior of the rings of Saturn.
•
Determine the composition of the satellite surfaces and the geological history of
each object.
• Determine the nature and origin
of the dark material on Iapetus’s
leading hemisphere.
•
Measure the three-dimensional structure and dynamic
behavior of the magnetosphere.
•
Study the dynamic behavior
of Saturn’s atmosphere at cloud
level.
•
Study the time variability of
Titan’s clouds and hazes.
•
Characterise Titan’s surface
on a regional scale.
These objectives have not only
been met – they’ve been massively
over-achieved.
It’s not the first time Saturn has been visited by a spacecraft from Earth. Pioneer 11 was the first, launched by NASA
on April 6, 1973 to study the asteroid belt, the environment
around Jupiter and Saturn, solar wind, cosmic rays, and eventually the far reaches of the Solar System and heliosphere.
Last contact with the spacecraft was on September 30, 1995.
Then in the early 1980s, NASA’s twin Voyager spacecraft had flown by and photographed Saturn and
its largest moons but these were brief encounters
and with mid-20th-century technology.
Cassini was a whole new ball game,
with 21st century technology, a mission
measured in years, rather than hours
and a huge array of instrumentation
and data-gathering equipment on
board. And while Voyager was
able to send photographs back
to Earth, Cassini (and Huygens) photography was in
glorious, detailed, highdefinition. And colour!
The launch and mission was previewed
in SILICON CHIP September 1997, “The
C assini Space
Probe: unravelling Saturn’s
Secrets” www.
siliconchip.
com.au/Article
/4835
The launch
vehicle was
a Titan IV
r o c k e t ,
which propelled the
ni’s
Finale
Artist’s impression courtesy NASA
siliconchip.com.au
SSeptember
eptember 2017 17
It’s not quite as simple as “aim, light the touch paper and stand back” (OK, you have to be old enough to remember
skyrockets!). Cassini-Huygens travelled in an ever-increasing elliptical path using the gravity of Venus (twice), Earth
and Jupiter to increase its speed and place it on a trajectory to intersect with Saturn, almost 93 months after its launch.
(Courtesy NASA/JPL)
5.5 tonne probe into an Earth orbit in preparation for its
journey to Saturn. Of the rocket’s 940,000kg launch weight,
840,000kg was fuel.
Along the way, in January 2005 it successfully dropped
a probe named Huygens (hence the mission name, CassiniHuygens) onto Saturn’s largest (and best known) moon, Titan.
The Huygens craft was developed by the European Space
Agency and “hitched” a ride on the side of Cassini.
We covered this section of the mission in an article in
May 2005: “Knocking on Titan’s Door”(www.siliconchip.
com.au/Article/3056).
Titan is huge: at 5150km in diameter, it’s about half the
size of the Earth. Then again, Saturn itself dwarfs the blue
planet – at 120km in diameter, you could fit 764 Earths
inside Saturn!
Even at its closest, Saturn is 1.2 billion (yes, B for billion!) kilometres from Earth. To put that in perspective, the
Sun is only 150 million kilometres away.
But it wasn’t a straight A-to-B flight. Ignoring the fact
that Saturn wouldn’t be in anywhere near the same position after more than a decade, the Cassini-Huygens spacecraft made close fly-bys of Venus (twice), Earth and Jupiter,
using their gravity to “slingshot” the craft on its journey.
In fact, Cassini orbited the Sun twice before setting out
on the long path to Saturn.
Without these gravity-assisted fly-bys, which used energy
from the planets to increase Cassini’s velocity and change
its direction relative to the Sun, there is simply no way
that it could have carried enough fuel to make it to Saturn,
let alone travel more than 2 billion kilometres around the
planet once it arrived.
18 Silicon Chip
Some anti-nuclear protestors on Earth claimed that having the radioactive-powered craft flying so close to Earth
posed an unacceptable risk. NASA countered by showing
that the closest Cassini would approach the Earth was more
than one thousand kilometres. The also claimed that the
chances of a collision were “less than one in a million”.
So what’s it been doing?
In a word, exploring! In many more words, conducting
an amazing array of scientific and astronomic research not
only on Saturn itself (even though it has never landed, and
never will) but also on its many moons (many more than
previously thought) and, of course, those rings which have
fascinated man ever since he had the telescopes powerful
enough to see them.
The 22 “dives” Cassini is taking in the weeks up to its
demise have actually been in and through those rings and
between the rings and Saturn’s surface.
Its speed is nearly 122,000 kilometers per hour relative
to Saturn’s center and about 110,000 kilometers per hour
relative to Saturn’s cloud-tops. At that speed you could
travel coast-to-coast in Australia in less than three minutes,
and it would take just over an hour to travel three times
around the Earth at the equator.
Scientists use the Doppler Shift in radio signals to measure its speed and the signal’s timing to determine its distance.
The Cassini mission program was originally planned to
end in 2008. That it has lasted another nine years is testament to the initial planning and design, the build quality
and the “nursing” of the craft – and of course, it meant that
siliconchip.com.au
A somewhat stylised artist’s impression of Huygens parachuting to make a soft landing on Titan, which it did in
January 2005. Titan was believed to be the only body (except for Earth) in the solar system with a liquid on its surface (a
hydrocarbon, not water) but Cassini found clear evidence of water on another moon, Enceladus. (Courtesy NASA/JPL)
an enormous increase in the amount of experimentation
and sampling could occur.
In April, Cassini started its dives through the gap between Saturn and its innnermost ring at nearly 122,000
kilometers per hour relative to Saturn’s centre, and about
110,000 kilometers per hour, relative to Saturn’s cloud-tops.
At that speed you could travel from New York City to
Los Angeles in less than three minutes and it would take
just over an hour to travel three times around the Earth at
the equator.
On the way: Saturn’s moons
Even before Cassini started orbiting Saturn itself, it had
undertaken valuable research on the many moons and rings
surrounding the planet itself.
One of the defining features of Saturn is its number of
moons. Excluding the trillions of tonnes of little rocks that
make up its rings, as of September 2012, Saturn has 62
discovered moons.
Perhaps Cassini’s most detailed look came after releasing
the Huygens lander towards Titan, Saturn’s largest moon.
Huygens descended through the mysterious haze surroundsiliconchip.com.au
ing the moon and landed on January 14, 2005.
It beamed information back to Earth for nearly 2.5 hours
during its descent, and then continued to relay what it was
seeing from the surface for 1 hour, 12 minutes.
In that brief window of time, researchers saw pictures
of a rock field and got information back about the moon’s
wind and gases on the atmosphere and the surface.
Cassini’s (and Huygen’s) discoveries and findings sent
back to Earth revealed previously unknown data about
their environments and appearances. Some of the achievements include:
• Completed first detailed reconnaissance of Saturn’s family of moons and rings.
• Delivered the Huygens probe to Titan for the first landing on another planet’s moon.
• Discovered erupting geysers and a global subsurface
ocean on Enceladus (In 2015, Cassini did a series of flypasts of Enceladus to get more information about the gas
and dust in the plumes).
• Found clear evidence of present-day hydrothermal activity on Enceladus – the first detection of hydrothermal
activity beyond Earth.
September 2017 19
Saturn’s largest moon, Titan, passes in front of the planet and its rings in this true colour snapshot from NASA’s Cassini
spacecraft. This view looks toward the northern, sunlit side of the rings from just above the ring plane. It was taken on May
21, 2011, when Cassini was about 2.3 million kilometers from Titan. Credit: NASA/JPL-Caltech/Space Science Institute
Cassini Mission Quick Facts
Cassini Orbiter
Dimensions: 6.7m high; 4m wide
Weight: 5,712kg with fuel, Huygens probe, adapter etc; (unfueled orbiter alone 2,125kg)
Orbiter science instruments:
composite infrared spectrometer, imaging system, ultraviolet imaging spectrograph, visual and infrared mapping
spectrometer, imaging radar, radio science, plasma spectrometer, cosmic dust analyzer, ion and neutral mass
spectrometer, magnetometer, magnetospheric imaging instrument, radio and plasma wave science
Power: 885W (633W at end of mission) from radioisotope thermoelectric generators
Huygens Probe
Dimensions: 2.7m in diameter
Weight: 320kg
Probe science instruments: aerosol collector pyrolyser, descent imager and spectral radiometer, Doppler wind
experiment, gas chromatograph and mass spectrometer, atmospheric structure instrument, surface science package
Huygens Probe Titan Release: December 24, 2004
Huygens Probe Titan Descent: January 14, 2005
Huygens’ Entry Speed into Titan’s Atmosphere: about 20,000km/h
Mission
Launch vehicle: Titan IVB/Centaur
Weight: One million kilograms
Launch: Oct. 15, 1997, from Cape Canaveral Air Force Station, Florida USA.
Earth-Saturn distance at arrival: 1.5 billion km (10 times Earth to Sun distance)
Distance traveled to reach Saturn: 3.5 billion km
Saturn’s average distance from Earth: 1.43 billion km
One-way Speed-of-Light Time from Saturn to Earth at Cassini Arrival: 84 minutes
One-way Speed-of-Light Time from Saturn to Earth During Orbital Tour: 67 to 85 minutes
Venus Fybys: April 26, 1998 at 234km; June 24, 1999 at 600km
Earth Flyby: August 18, 1999 at 1,171km
Jupiter flyby: December 30, 2000 at 10 million km (closest approach 5:12am EST)
Saturn Arrival Date: July 1, 2004, UTC
Primary Mission: 4 years
Two Extended Missions: Equinox (2008-2010) and Solstice (2010-2017)
Cost of Mission: about $3.27 billion (U.S. contribution is $2.6 billion and European partners’ contribution $660 million)
20 Silicon Chip
siliconchip.com.au
• Revealed Titan as a world with rain,
rivers, lakes and seas.
• Revealed Saturn’s rings as active
and dynamic – a laboratory for how
planets form.
• Discovered and then pinned down
details about a giant methane lake
on Titan.
• Discovered 80km-wide landslides on Iapetus.
• Took a close-up view of Rhea, revealing a pockmarked surface.
• Discovered a huge ring, 8 million
miles away from Saturn, probably
made up of debris from Phoebe.
Cassini reaches Saturn
Cassini went into orbit around Saturn on July 1, 2004. On September
27, the spacecraft then moved on to
siliconchip.com.au
the next, primary, stage of its mission,
called the Cassini Equinox Mission.
This phase allowed scientists to study
seasons and other long-term weather
phenomena on the ringed planet and
its moons and to continue observations
of the magnetic bubble around the
planet, known as the magnetosphere.
Originally planned to end on July
30, 2008 the mission was extended to
June 2010.
This studied the Saturn system in
detail during the planet’s equinox,
which happened in August 2009.
The spacecraft’s life was further
extended in 2010, with the Cassini
Solstice Mission, which concludes
with Cassini making its final dive into
Saturn’s atmosphere on September 15
this year.
The extension enabled another 155
revolutions around the planet, 54 flypasts of Titan and 11 flypasts of Enceladus.
Earlier this year, an encounter with
Titan changed its orbit in such a way
that, at closest approach to Saturn, it
will be only 3,000km above the planet’s cloudtops, below the inner edge
of the D ring. This sequence of “proximal orbits” will end when another
encounter with Titan sends the probe
into Saturn’s atmosphere.
To say that scientists around the
world have been enthusiastic about
Cassini (and Huygens) is a massive
understatement.
While it has been 20 years since
launch, they will spend that long again
analysing the data!
SC
September 2017 21
Another Notable 2017 Space Anniversary:
I
n this account of the rather incredible (in the true sense of
the word) achievements of Cassini and Huygens in September this
year it would be remiss of us NOT
to mark an even more incredible
anniversary also occuring this year
– that of the launch of the first manmade Earth satellite, Sputnik 1, by
the Soviet Union on October 4, 1957.
Arguably the only comparison
between Sputnik and Cassini is that
they were both launched into space!
Where (huge) Cassini has been responsible for virtually continuous
transmission of data and pictures
since its launch, the tiny Sputnik (a
585mm, 85kg sphere) was capable of
“only” transmitting a series of beeps
as it orbited the Earth.
Thousands of amateur radio operators listened out for the faint signals from Sputnik on 20.005MHz
(close to the 21MHz amateur band
and well within the capabilities of
most amateur equipment using that
22 Silicon Chip
band) and 40.002MHz (a VHF signal
requiring more specialised receiving
equipment).
What those thrilling at the sound of
those 0.3s pulses didn’t know was that
they were also listening to the first data
from space: Sputnik’s radio signals
from its one watt, 3.5kg transmitter
were encoded with (quite elementary!)
telemetry data, not only initially telling
controllers of the satellite’s successful deployment but during the flight,
information on the electron density
of the ionosphere along with satellite
temperature and pressure.
After several unsuccessful test firings of R-7 launch vehicles, Sputnik
was carried aloft on an 8K71PS rocket
(itself a modified R-7) from Site No.1
at the 5th Tyuratam proving ground in
Kazakh SSR (now known as the Baikonur Cosmodrome), at 19:28:34 UTC.
The control system of the Sputnik
rocket had an intended orbit of 223
by 1,450km, with an orbital period of
101.5 minutes; the actual orbit turned
out to be 223 x 950km with an orbit
every 96.2 minutes.
There are several reasons for this
difference – remember that even with
the brightest minds in the Soviet Union working on the project, much of
the work was theoretical, unproven
technology.
Not all to plan!
Even the launch didn’t go exactly
to plan: a booster failed to reach full
power at lift-off, causing the rocket to
tilt over at 2° just six seconds after liftoff. The booster reached full power just
one second before the launch would
have been automatically terminated.
This would have caused the spacecraft
to crash close to the launch pad.
Then 16 seconds into the flight, a
fuel regulator in the booster also failed,
resulting in excessive fuel consumption and 4% higher than expected engine thrust.
This resulted in termination of the
thrust one second early – hence the
siliconchip.com.au
60 Years since Sputnik
different orbit than expected. However, at 19.9 seconds after engine cutoff, the second stage separated and the
radio transmitter was automatically
activated, indicating a successful deployment.
Engineers listened to the “beepbeep-beep” for two minutes, until the
craft disappeared below the horizon.
They waited some 90 minutes until
Sputnik was once again in “view” and
confirmed radio reception, before calling Soviet premier Nikita Khrushchev.
TASS, the Soviet news agency, then
announced to the world the successful
launch and deployment.
Strangely enough (considering the
times) it took some time for the Soviets to start making any real propaganda mileage out of Sputnik. But in the
USA, the launch was met with some
fear and trepidation with the realisation that they had, at least then, lost
the lead in the “space race”.
Three week life
Sputnik had a design battery life of
just 14 days – it continued to trans-
mit for three weeks until its battery
finally gave out. But the craft itself
continued to orbit the Earth (where
it could often be seen, depending
on its height) for another three
months, until it re-entered the
Earth’s atmosphere and burned
up on January 4, 1958, having
completed 1,440 orbits.
How many Sputniks?
While there was only one Sputnik
to claim the title of “the first”, there
were at least three (and possibly more)
duplicates built. One of these, a complete system, is in the “Energia” corporate museum just outside Moscow,
where it is viewable by appointment
only.
Another is in the Museum of Flight
in Seattle, Washington – while it has
been authenticated (and even shows
some signs of wear) it doesn’t have
any internal components. And there
are said to be at least two other duplicates in private collections.
There are dozens of “replica” Sputniks in various museums and collec-
tions around the world – one even in
Australia at Sydney’s Powerhouse
Museum.
And there were three studentbuilt one-third scale Sputniks deployed from the Mir space station
between 1997 and 1999 (the first
launched to mark the fortieth anniversary of the original Sputnik).
Yet another “went down with the
ship” when Mir burned up on its
controlled re-entry on March 23,
2001.
SC
Image Credit: http://unusualsuspex.deviantart.com/art/Sputnik-1-Tech-Readout-new-470662574
siliconchip.com.au
September 2017 23
3-Way Fully Adjustable Stereo
Active Crossover
for Loudspeakers
This Stereo 3-Way Adjustable
Active Crossover is not only a fantastic
tool for loudspeaker design and development but it can also be
integrated into a 2-way or 3-way Active (powered) loudspeaker.
The crossover points and levels for tweeter, midrange and woofer
are fully adjustable with separate controls for each driver.
By JOHN CLARKE
24 Silicon Chip
siliconchip.com.au
FEATURES:
•
•
•
•
•
•
•
•
Stereo crossovers
3-bands (Bass, Mid and Tweeter) or 2-band use (low pass and tweeter)
Optional use of the bass output as a subwoofer output in 2-band mode
Adjustable crossover frequencies
Individual level controls for each band
Overall volume control
Balance control
Limiter for Bass output (optional)
Of course, passive crossovers can
be designed with steeper roll-offs,
but these are more complex and expensive.
Another drawback with passive
crossover design is that loudspeakers
are not simply resistive, even though
their nominal impedance may be 4Ω
or 8Ω, for example. Impedance varies with frequency so an 8-ohm loudspeaker may only have an impedance
of 8Ω at one frequency.
At other frequencies, the impedance
can be lower or higher; maybe much
higher than the nominal impedance.
So why does the impedance value
vary? Because all loudspeakers have
inductance.
Loudspeaker impedance also varies because of cone resonances and in
the case of the woofer, due to the air
loading on the speaker cone inside the
box. These need to be compensated for
if the crossover is to work correctly.
(The lowest impedance value for
a loudspeaker will typically be just
above its cone resonant frequency and
will be close to its DC resistance).
This why you cannot take a passive
crossover off the shelf and hope that
it will work well with a random selection of drivers mounted in a given
enclosure.
Nor can you simply substitute a
tweeter or woofer for the original drivers in a loudspeaker system with a
passive crossover network – it is not
likely to work well!
Solving the problems
M
ost hi-fi loudspeaker systems
have passive crossover networks to separate the audio
signal into different bands, to suit the
tweeters, midrange drivers and woofers. Passive crossovers comprise inductors, capacitors and resistors.
This approach can be simple and
economical for a 2-way loudspeaker
(ie, with tweeter and woofer) but it can
be much more complex and expensive for 3-way loudspeakers (ie, with
a midrange driver added), especially
if there are big disparities between the
efficiencies of the different drivers and
if quite steep crossover roll-off slopes
are required.
With active crossovers, it’s easier to
produce steeper roll-off rates and the
signal level can be optimised for each
driver via its own amplifier.
siliconchip.com.au
In more detail, one of the major
disadvantages of a passive crossover
is that the changeover between the
separate frequency bands is usually
not very sharp.
A typical crossover slope is only
6dB/octave or maybe 12dB/octave,
in theory.
In practice, as we shall see, the slope
can be much less and that means there
is a wide frequency range over which
the two drivers will be both producing
the same sound frequencies.
That can mean that a woofer will be
fed with higher frequencies than it ideally should (eg, above 1kHz) and the
tweeter may be fed with lower frequencies (eg, below 1kHz). This means that
both drivers are operating outside the
regions where they produce the lowest distortion.
By contrast, active crossovers can
solve many of the above problems.
Firstly, the frequency overlap between
two loudspeaker drivers can be minimised by steep roll-off slopes.
Secondly, the impedance of each
driver does not affect the crossover
frequency. Nor is there any interaction
between the crossover components, as
can be the case in passive crossover
networks.
Thirdly, the electrical damping of
the driving amplifier is not reduced
by the impedance of the components
in a passive crossover.
This means better damping of woofer cone motion, ie, lower distortion
and less boominess.
OK, so active crossovers do have
advantages but most designs are not
easily adjustable without changing
lots of components.
Our new design is fully adjustable
September 2017 25
Fig.1: the stereo audio signal is split into three separate stereo signals covering different frequency
ranges, to suit the
woofers, mid-range drivers and tweeters. For a two-way system, the third signal can optionally be used for subwoofer(s).
for both crossover frequencies and
driver signal levels – just use the control knobs!
Low pass, high pass
Before we go any further we should
explain some terms which often confuse beginners: low-pass, high-pass
and band-pass filters.
Exactly as its name suggests, a lowpass filter is one that allows low frequencies to “pass” through it and it
blocks the higher frequencies.
Hence, a circuit to drive a subwoofer
would be called a low-pass filter since
it only delivers frequencies below
200Hz or thereabouts.
Similarly, a high-pass filter is one
that allows high frequencies to pass
through it and it blocks low frequencies. The part of a crossover network
which feeds a tweeter is said to be a
high-pass filter, even though it may
consist of only one capacitor.
You would probably realise that as
the frequency drops, the impedance
of a given capacitor increases, hence
blocking the higher frequencies.
(Incidentally, the ultra-handy
S ILICON C HIP Inductance/Capacitance Ready Reckoner Giant Wall
Chart (see www.siliconchip.com.
au/l/aaek or www.siliconchip.com.
au/Shop/3/3302) demonstrates this
perfectly – you nominate a capacitance value and as you move up the
frequency scale, you can see that the
impedance increases. If you’re designing filter circuits, this chart is a must!).
If we cascade (ie, connect in series)
a high-pass filter with a low-pass filter, the combination will pass a band
of frequencies and we then refer to it
as a “band-pass filter.” We use a bandpass filter for the midrange output in
this active crossover circuit.
Other points you need to know
about high and low-pass filters are the
so-called cut-off frequency and the filter slope roll-off.
Typical filter slopes are specified in
dB/octave where the dB (decibel) term
is the attenuation. Typical slopes are
-6dB/octave (quite gradual), -12dB/oc-
Fig.2: eight active
filters are used to
produce the signals
for each channel,
along with four
variable attenuators,
a bass limiter. The
stereo volume and
balance controls
operate on both
channels.
26 Silicon Chip
siliconchip.com.au
Fig.3(a): this is the configuratio of each second-order low-pass filter, which is known as a Sallen-Key type. Its expected
frequency response is shown at right. Note that the variable resistances required are of the same value.
tave, -18dB/octave and -24dB/octave
(quite steep for a crossover network).
The filter slope applies for frequencies after the cut-off frequency. The
cut-off frequency is where the signal
output is -3dB down on the normal
level.
For example, in a low-pass filter we
might have a cut-off frequency of 1kHz
(ie, -3dB point) and at slightly above
that frequency, the slope will be -12dB/
octave. And for the filters described
here, this means that the response at
2kHz (ie, one octave above) will be
-12dB and at 4kHz it will be -24dB.
Two or three filter bands?
Fig.1(a) shows the three filter bands
available with our new Active Crossover. While it may not be immediately
apparent, this involves two crossover
points and no fewer than four filters.
Starting from the left-hand side,
we have a low-pass filter for the bass
frequencies and it “crosses over” to a
high-pass filter for the midrange frequencies. Further up the audio spectrum, we have another low-pass filter
which blocks out higher frequencies
and then it “crosses over” to another
high-pass filter which handles the frequencies fed to the tweeter.
Note that when we shift the low
crossover frequency, we are actually
simultaneously changing the cut-off
frequencies of the respective low-pass
and high-pass filters – they are ganged
together.
Similarly, when we shift the high
crossover frequency, we simultaneously change the cut-off frequencies
for the midrange low-pass and upper
high-pass filters.
Fig.1(a) shows the new Active Crossover used in a 3-way configuration,
with bass (woofer), midrange driver
and tweeters.
But Fig.1(b) shows that it could be
used in an alternative configuration
as a 2-way system with a midrange/
woofer and a tweeter, together with
an optional subwoofer. The circuitry
remains the same but the way you connect is a little different. We will talk
about that later.
Block Diagram
Fig.2 shows the block diagram for
the 3-Way Adjustable Active Crossover. Only the left channel is shown;
the right channel is identical.
It actually comprises four low-pass
and four high-pass filters. Hmm, we
just mentioned that only four filters
were needed to produce the three
bands shown in Fig.1. Why are there
now eight filters involved?
Patience, now – all will be revealed!
The left and right channel inputs are
fed to a stereo volume control (VR1a
and VR1b) and the signal is then buffered with op amps IC1a & IC1b and
their outputs connect to the balance
control, VR2.
After further buffering by op amps
1C2a & IC2b (for the right channel),
the signal is passed to two adjustable
high pass filters involving IC4 and IC5
(signal path in green) and also fed to
two adjustable low pass filters involving IC3 (signal path in blue).
The signal from the high-pass filters
is fed to the tweeter level control and
then to the tweeter output, CON2a.
The signal from the low-pass filters is
fed to a second pair of adjustable highpass filters involving IC7 & IC8 and to
a second pair of adjustable low-pass
filters involving IC6.
The output from the second pair of
high-pass filters is fed to the midrange
level control and then to the midrange
output, CON3a.
The output from the second pair
of low-pass filters is fed to the bass
level control (signal path in red) and
then goes via the bass limiter (can be
switched in or out) to the woofer (or
subwoofer) output, CON3b.
Why do we need a bass limiter?
Because we envision that in some applications, the bass output will need
to be boosted substantially and that
could lead to overload of the woofer
or woofer driver amplifier on loud pas-
Fig.3(b) & (c): the Sallen-Key high-pass filter requires
two different resistances, however, the circuit at right
shows how we have reconfigured it for identical
resistance values so that ganged pots can be used.
siliconchip.com.au
September 2017 27
The equation for calculating the
fc for the filter is shown (in Fig.3(a))
though this calculation only applies
to a Butterworth filter.
High-pass filter
By swapping the resistors and capacitors in the circuit of Fig.3(a), we
can obtain a high-pass filter, as shown
in Fig.3(b).
Once again this arranged to have a
Butterworth response with a Q=0.7071
but instead of having capacitors with
values of C and 2C, we have resistors
of 2R, between the non-inverting input of the op amp and ground, and R
at the output of the op amp.
Both these resistive elements are
adjustable using potentiometers and
that presents a big problem since our
Active Crossover uses an 8-gang potentiometer for each crossover output;
each potentiometer element needs to
have the same value, eg, 10kΩ.
To solve that problem, we use an exFig.4: the simulated response of a single pair of Sallen-Key low-pass/high-pass
tra op amp, as shown in Fig.3(c). The
filters with a corner frequency of 1kHz (red) and the cascaded pairs of Sallensecond op amp is connected as a unity
Key filters (red), known as a Linkwitz-Riley arrangement. The flat green line
gain buffer and is driven from a voltage
shows the overall response when the signals are acoustically summed.
divider connected to the output of the
sages (hint: see page 33!).
filter which gives a roll-off slope of first op amp, to drive the bottom end
The bass limiter will prevent this 12dB/octave.
of the potentiometer (R).
while having negligible effect on the
The basic design is referred to as
This resistor now has half the sigsignal at other times.
a Sallen-Key filter (after R. P. Sallen nal current through it and so acts as
and E. L. Key of MIT Lincoln Labora- though it has a value of 2R – which is
Two-way configuration
tory in 1955).
what we want.
As noted above, this Active CrossoThe graph to the right of the circuit
So that shows the configuration of
vers can also be built as a 2-way system shows the roll-off slope beyond the all the low-pass and high-pass filters
with an optional subwoofer output. In cut-off frequency (fc). The passband in the circuit but it does not explain
that case, you would have a tweeter region refers to the frequencies below why we using four of each.
output (CON2a), the midrange/woofer fc where the signal level is mostly unThe reason is that the circuits of
output (CON2b) and the subwoofer affected by the filter.
Fig.3 are second-order filters and their
output (CON3b). The circuitry for IC6,
For this particular circuit, the filter filter slopes are equal to 12dB/octave
IC7 & IC8 could then be omitted.
has a Q of 0.7071 and has a Butter- which is not particularly steep – we
So now let us explain why we need worth response. The Q value means want twice that: 24dB/octave. So we
eight active filters in each channel that the frequency response below fc use identical cascaded low-pass and
rather than four.
remains as flat as possible rather than high-pass filters to get the desired reFig.3 a, & b show the basic circuits with any amplitude ripple or peaking. sult.
for the low-pass and highWe simulated the filter
filters used in our Active
circuits using LTspice to
Crossover.
obtain the actual responses
Let’s talk about the lowfor the filters.
If you wish to do some calculations of responses for these
pass filter first, as shown
If you use LTspice or are
filters, an excellent website is available. This calculates the filin Fig.3(a). This consists of
following our series on this
ter responses for the Sallen-Key configuration and shows plots
a single op amp together
in SILICON CHIP, you may
and filter Q for values of R and C.
with two identical (adwish to use the SPICE file.
For the low pass filter C1 is the capacitor that needs to be
justable) resistors R and
This file (Active filter.asc)
twice in value to C2. R2 is double the resistance of R1 in the
two capacitors, C and 2C.
will be available from the
high pass filter.
(2C is actually two identiSILICON CHIP website.
For a cut-off of 1kHz (fc), use 22nF for C (44nF for twice the
cal capacitors in parallel).
Fig.4 shows the results
value) and 5.11543kΩ for R (10.23086kΩ for twice the value).
The op amp is connected
for the low-pass filter when
as a unity-gain buffer and
the cut-off frequency is
For the high pass filter see: siliconchip.com.au/l/aaei
because it uses two RC net1kHz. The response for the
works, it is a second-order
single stage Butterworth
For the low pass filter see: siliconchip.com.au/l/aaej
siliconchip.com.au
28 Silicon Chip
Calculating R & C
siliconchip.com.au
September 2017 29
Fig.5: the main portion of the Active Crossover circuit, built around 22 LM833 dual low-noise/low distortion op amps. The
layout is similar to that of block diagram Fig.2, so you should be able to identify the corresponding sections. VR3-VR6 are
four eight-ganged 10kΩ linear potentiometers which allows the corner frequency of each set of four active filters which
makes up a crossover network to track. So only two adjustments need to be made to change the crossover point for either
bass/midrange or midrange/tweeter. The bass limiter and power supply sections of the circuit are shown separately.
30 Silicon Chip
siliconchip.com.au
siliconchip.com.au
September 2017 31
filter is 3dB down at the cut-off frequency. At 10kHz (one decade away)
the response is down by 40dB, as expected. That’s a 40dB per decade (or
12dB/octave) roll-off.
When the two filters are cascaded,
we get a response that is referred to as
“Butterworth squared” (also called a
Linkwitz-Riley) filter. The combined
filter Q is 0.5; obtained by multiplying the Q (0.7071) of each Butterworth
stage together. The cascaded filter response is 6dB down at fc and 80dB
down at 10kHz.
Putting it another way, the combined filter slope, beyond fc, is 24dB/
octave.
Similar results for the low-pass filter are also shown in Fig.4; -3dB down
at 1kHz for the single stage and 6dB
down at 1kHz for the cascaded filters.
At 100Hz (one decade away), response
is 40dB down for the single stage filter
and 80dB down for the cascaded filter.
We use the Linkwitz-Riley filters
because when both the low and high
pass filters are summed, acoustically
the response is flat.
Using the Linkwitz-Riley filters
means that there are no dips or peaks
in the frequency response across the
crossover frequency region.
For more information on LinkwitzRiley filters, see siliconchip.com.au/l/
aaeh
The left and right channels have separate frequency adjustments. Ideally,
both left and right channels should
be able to be adjusted together for the
same crossover frequencies. However,
we were not able to do this easily and
we shall see why later.
Main circuit
The main circuit of the Active Crossover is shown in Fig.5 and again, this
only shows the left channel. Just so you
can recognise the various low-pass and
high-pass filters, dual op amps IC4 and
IC5 are the cascaded first and second
high-pass filters while dual op amp
IC3b and IC3a are the cascaded first
and second low-pass filters.
All op amps in the circuit are
LM833s for very low noise and distortion.
Similarly, dual op amps IC7 and
IC8 are the cascaded third and fourth
second high-pass filters while dual op
amp IC6b and IC6a are the cascaded
third and fourth low-pass filters.
Also note that all the potentiometer elements for the filters of IC3, IC4
and IC5 are part of the same 8-ganged
potentiometer, VR3. Similarly, all the
potentiometer elements for the filters
of IC6, IC7 and IC8 are part of the same
8-ganged potentiometer, VR4.
However, that means that this Active Crossover is not able to simultaneously adjust the crossover frequencies
in both channels; each channel must
be done separately. If we wanted to
do both channels simultaneously, we
would need 16-element pots and that
is simply not practical.
However, the level adjustments for
each channel output are made using
dual ganged pots, so these are done
simultaneously.
Now let’s track the signal through
the crossover circuitry. The input signal is applied to an RF suppression
network comprising ferrite bead L1,
a 100Ω stopper resistor and a 10pF
capacitor. The signal is then coupled
to the volume control VR1a via a 22µF
non-polarised capacitor.
The signal from the wiper of VR1is
buffered by IC1a and its output is con-
Fig.6: the bass limiter circuitry, which prevents bass drivers which are driven with significant levels of gain from
being overloaded. It uses pairs of LEDs and LDRs to form a variable gain amplifier for each channel, similar to a
compressor but with a much longer attack and decay times.
32 Silicon Chip
siliconchip.com.au
Coming soon: a 3-way active dipole loudspeaker
One of the main reasons why we have produced this
highly flexible 3-way active crossover is that we are developing a 3-way active dipole loudspeaker with some
most unusual features. For a start, there is no enclosure.
All three drivers are mounted on a simple baffle. How can
that possibly work? Don’t you need some sort of enclosure
in order to produce adequate bass response? Normally, the
answer is a resounding “yes!” but we have taken a similar
approach to speaker design in producing a dipole loudspeaker – it radiates equally from the front and rear of the baffle.
Doesn’t that lead to bass cancellation? Yes it does but a
dipole enclosure can work well in a small room provided there
is considerable bass boost. That is just not possible with a
passive crossover but our new 3-way active crossover makes
it quite simple to achieve, because it allows large differences
in the signal power applied to each driver.
We hope to feature this most interesting loudspeaker system
in a few months. Watch out for it!
nected to one side of the balance balance control, VR2.
The balance control has a limited
range of action and it works as follows.
When centred, there is an equal loss
in signal level for both channels that
amounts to -1.42dB.
When the pot is rotated off centre,
more signal is shunted to ground in
one channel than in the other channel.
When the balance pot is rotated
fully in one direction, it causes a loss
of 8.3dB in one channel and slight
increase in the other. So there is an
overall 8.9dB change in level between
one channel and the other.
Following the balance control, the
signal is again buffered by IC2a and
then fed to the first high-pass and first
low-pass filters involving IC4 and IC3,
respectively.
So the signal progresses through the
first and second high-pass filters of IC4
and IC5 and also to the first and second low-pass filters of IC3b and IC3a.
Then the respective tweeter and
midrange signals are fed to the respective level controls, involving VR7b
and VR8b.
These are Baxandall circuits which
give a logarithmic response when
using a linear potentiometer. This
is highly desirable since we want to
use linear dual ganged pots and these
have far better matching and tracking
between channels than logarithmic
taper pots.
Two op amps are involved for each
level control. The tweeter control,
VR7b, involves op amp IC15a, configured as buffer, and IC16a, an inverting
op with a gain of 4.5.
Hence the overall gain range of the
circuit is from unity to 4.5 which is
more than adequate for this application. Another advantage of this Baxandall level control is that it reduces
noise at the lower gain settings.
Further filter stages
The output of the second low-pass
filter involving IC3a is also fed to the
third and fourth high-pass filters involving op amps IC7 and IC8 and also
to the third and fourth low-pass filters
involving IC6b and IC6a.
The output of the fourth high-pass
filter IC8a is fed to the midrange level
control VR9b involving op amps IC19a
and IC20a.
Finally, the output of the fourth
low-pass filter IC6a is fed to the bass
level control VR10a involving op amps
IC21a and IC22a.
However, the bass level control can
also be fed to the bass limiter which can
Fig.7: the power supply section of the circuitry, which is on the same PCB as the rest. Power can come from either an
AC plugpack or centre-tapped mains transformer. The transformer output is rectified, filtered and regulated to
produce the ±15V supply rails for the op amps.
siliconchip.com.au
September 2017 33
Parts List – Three-Way Active Crossover
1
1
1
1
2
2
1
2
4
6
2
1
1
1
2
2
1
1
8
4
4
4
2
4
main PCB, coded 01108171, 284 x 77.5mm
front panel PCB, coded 01108172, 296 x 43mm
rear panel PCB, coded 01108173, 296x 43mm
16VAC 1A (or higher current) plugpack
DPDT PCB mount push button switches (Altronics S1510) (S1,S2)
knobs to suit push button switches S1 & S2 (Altronics H6651)
two-way vertical stacked PCB-mount RCA socket (Altronics P0210) (CON1)
four-way vertical stacked PCB-mount RCA sockets (Altronics P0211)
(CON2,CON3)
knobs to suit VR3-VR6 (Mouser 5164-1227-J)
knobs to suit VR1,VR2,VR7-VR10) (Jaycar HK-7734)
TO-220 heatsinks, 19 x 19 x 9.5mm (Jaycar HH-8502)
PCB-mount 2.5mm DC power socket (Jaycar PS-0520, Altronics P0621A)
(CON4)
2.5mm DC line plug (Altronics P-0635A, Jaycar PP-0511)
3-way PCB-mount screw terminals with 5.08mm spacing (CON5)
5mm ferrite suppression beads (L1,L2)
ORP12 (or equivalent) LDRs (Jaycar RD-3480)
50mm length of 6mm diameter black heatshrink tubing
set of black Acrylic case pieces (SC4403)
16mm long M3 tapped spacers
9mm long M3 tapped Nylon spacers
M3 x 32mm machine screws
M3 x 5mm black machine screws
M3 x 6mm screws & nuts
self-adhesive or screw-on rubber feet
Semiconductors
25 LM833D SOIC (SMD) dual op amps (IC1-IC25)
1 7815 +15V three-terminal regulator (REG1)
1 7915 -15V three-terminal regulator (REG2)
2 1N4148 diodes (D1,D2)
2 1N5819 Schottky diode (D3,D4)
1 W04 1.2A bridge rectifier (BR1)
2 5mm 7500mcd green LEDs (Jaycar ZD-0172) (LED1,LED2)
1 3mm blue LED (LED3)
Capacitors
2 470µF 25V PC electrolytic
1 100µF 16V PC electrolytic
10 22µF NP 50V PC electrolytic
12 10µF 35V (or greater) PC electrolytic
20 120nF 63V or 100V MKT polyester
25 100nF X7R 50V SMD (1206) ceramic
20 22nF 63V or 100V MKT polyester
11 100pF X7R 50V SMD (1206) ceramic
2 100pF 50V ceramic
Resistors (0.25W, 1%, through-hole or 1206 SMD as specified)
2 100kΩ
7 100kΩ SMD 8 22kΩ
2 10kΩ
1 5.6kΩ
8 2.2kΩ
2 2.2kΩ SMD 2 1kΩ
2 620Ω
8 150Ω
2 100Ω
26 10kΩ SMD
38 1kΩ SMD
Potentiometers and trimpots
1 10kΩ log dual 9mm potentiometer (Jaycar RP-8756) (VR1)
1 10kΩ linear single 9mm potentiometer (Jaycar RP-8510) (VR2)
4 10kΩ linear 8-gang 9mm potentiometers, Bourns PTD9081015FB103 (VR3-VR6)
(Mouser)
4 10kΩ linear dual 9mm potentiometers (Jaycar RP-8706) (VR7-VR10)
1 5kΩ 25-turn top adjust 3296W style trimpot (VR11)
34 Silicon Chip
be switched in or out using switch S2.
Limiter circuit operation
The Limiter circuit is shown in Fig.6
and it acts on the signals from both
channels, left and right.
In essence, the bass signal from each
channel (left from IC22a; right from
IC22b) is fed to a passive attenuator
comprising a 10kΩ resistor, a 100kΩ
resistor to ground and a paralleled
light-dependent resistor (LDR). LDR1
is used for the left channel and LDR2
for the right channel.
Normally, the LDR resistance will be
very high and the reduction in signal
level will be less than 1dB. Op amp
IC23b buffers the signal from LDR1,
while IC23a buffers the right-channel
signal from LDR2.
Each LDR is located next to a LED
and both are encased in a light-proof
housing (made of heatshrink tubing).
So light from LED1 can reduce the resistance of LDR1 and LED2 does the
same for LDR2. Both LEDs are driven
with the same current so that the signal level in both channels is reduced
by the same amount.
The drive signals to LED1 & LED2 are
derived by dual op amps IC24 and IC25.
The bass signals from IC23a and IC23b
connect to the inverting inputs of IC24a
and IC24b via 1kΩ resistors which mix
the signals from both channels.
These amplifiers have a gain of 100
by virtue of their 1kΩ input and the
100kΩ feedback resistors.
The amplifiers also have their noninverting inputs connected to separate
voltage references formed using a resistive divider across the ±15V supply.
The attenuator comprises a 10kΩ resistor from the +15V supply, two 2.2kΩ
resistors and another 10kΩ resistor to
the -15V supply.
The centre point of the attenuator
where the two 2.2kΩ resistors meet is
connected to the ground (0V). A 5kΩ
trimpot (VR11) connects across the
two 2.2kΩ resistors and can be used
to adjust the voltages at TP1 and TP2.
With VR11 set for 5kΩ, the voltage
at TP1 and TP2 will be +1.57V and
-1.57V respectively. This voltage can
be reduced down to 0V, with VR11at
the opposite extreme.
When the combined signal from
IC23a and IC23b swings positive but
less than the TP1 voltage, IC24b’s output will be high; ie, above 0V. When
the combined signal from IC23a and
IC23b swings negative but less negasiliconchip.com.au
tive than TP2, IC24a’s output will be
low; less than 0V. In effect, IC24b &
IC24a operate together as a window
comparator.
The signal from IC24b is inverted by
IC25b, change any negative-going signal to positive-going. Then the positive
going signals from IC25b and IC24a are
fed to diodes D1 and D2, respectively.
So any positive-going signal from
IC25b or IC24a will cause D1 or D2 to
conduct and charge the 100µF capacitor via the 1kΩ resistor.
IC25a monitors the signal across the
100µF capacitor and drives LED1 &
LED2 (in series) and these LED control
the resistance of LDR1 & LDR2 to limit
the bass signals when the exceed the
thresholds set by TP1 & TP2.
The time constant for the 100µF
capacitor to discharge via the 100kΩ
resistor is ten seconds. This time-constant prevents the audio signal from
being modulated by the limiter circuit.
The associated 1kΩ resistor sets the
attack time-constant to 100ms, so that
limiting does not instantly occur with
brief transients.
Note that the maximum 1.57V
threshold at TP1 and -1.57V threshold
at TP2 will start signal limiting for a
sine wave that’s 1.57V peak or 3.14V
peak to peak. That is about 1.1V RMS.
Power supply
Fig.7 shows the power supply circuit. It can be powered using a centretapped 30V transformer or a 16VAC
plugpack – either transformer feeds
the bridge rectifier via switch S1.
However, the bridge rectifier works
differently, depending on which transformer is used.
The 16VAC plugpack connects via
CON4 with one side going to ground
while the centre-tapped transformer
connects to 3-pin CON5. The net result
is only two diodes are involved when
the power comes via CON4 and S1a
and we have half-wave rectification
for the positive and negative rails fed
to the 3-terminal 15V regulators.
When the power comes via CON5,
the full bridge rectifier is involved.
Either way, the rectified DC is filtered
using 470µF capacitors.
Next month . . .
Have we whetted your appetite sufficiently with the description of the
Three-Way Active Crossover?
Next month, we’ll move on to the
construction, setup and use of this
project.
MPPT REGULATOR + SOLAR PANELS PACKAGE
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LOOKING FOR A
PCB?
PCBs for most recent (>2010)
SILICON CHIP projects are
available from the SILICON CHIP
PartShop – see the PartShop
pages in this issue or log onto
siliconchip.com.au/shop
You’ll also find some of the
hard-to-get components to build
your SILICON CHIP project, back
issues, software, panels, binders,
books, DVDs and much more!
So in the meantime, use the parts
list opposite to start gathering the bits
you’ll need (there are some that aren’t
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plus P&P) – and remember, if you’re a
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off all items from the shop (subscriptions and postage excepted).
While you’re about it, why not order
one of the giant L-C-R Wallcharts as
well – you won’t believe how handy
SC
it will be in your workshop!
12V SOLAR PANELS AND REGULATORS
Framed Polycrystalline 30W and
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TO R E Q U E S T A
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siliconchip.com.au
September 2017 35
CIRCUIT NOTEBOOK
Interesting circuit ideas which we have checked but not built and tested. Contributions will be
paid for at standard rates. All submissions should include full name, address & phone number.
Automatically rebooting NBN modem
I connected to NBN wireless about
nine months ago and found that
over time, my internet speed slowed
down to such an extent that streaming video was no longer possible.
On contacting my ISP, they suggested that I reset the router by removing the power to it for about a
minute and then reconnecting it.
This I did with the result my internet speed was back to normal and
streaming was possible.
After about a week, the same thing
happened and resetting the router
again fixed the problem. I re-flashed
the router with the latest firmware
but this made no difference. I then
tried a second router with exactly
the same result.
As a workaround to solve the
problem, I built the circuit shown
here which switches off the power to the router for one minute at
3:00am every morning. Since then,
I haven’t had any further problems
with streaming movies. Others may
36 Silicon Chip
have similar problems and may benefit from building this circuit.
It’s designed to be powered up at
noon. It will then wait until 3:00am
that night, reboot the router and
repeat every 24 hours. 9V back-up
battery BAT1 keeps the circuit operating during blackouts, so the timekeeping isn’t affected.
It uses a 4060 CMOS IC, IC1,
which is a 14-stage divide-by-16,384
counter with internal oscillator. The
frequency of oscillation is set by
32768Hz watch crystal X1 and when
divided by the counter, this gives a
2Hz output pulse on pin 3. This is
applied to the GP2 input, pin 5, of
PIC12F675 microcontroller IC2.
The positive edge of this pulse
triggers an interrupt routine. This
routine counts the number of seconds, minutes and hours and resets
to zero after 24 hours have passed.
When the time reaches 3:00am,
output pin GP0 is driven high for
one minute, turning on the transistor
Q1 which energises relay RLY1,
switching off the router. The circuit runs from the router’s 12V DC
plugpack.
This voltage is regulated to 5V by
REG1, an LP2950-5. Diodes D1 and
D2 combine the mains-derived and
battery power supplies so that the
12V supply powers the circuit when
mains is present and BAT1 powers
it during blackouts.
Transistor Q2 is biased on only
when the mains-derived 12V power
is present. When on, it allows current to flow from LED1’s cathode to
ground. LED1’s anode is driven by
a 2Hz signal from the GP1 output of
IC2. So LED1 flashes when mains
power is present and the circuit is
operating correctly.
The firmware for IC2 was written
in BASIC and compiled to a HEX file
using PICBASIC Pro. Both the BASIC
source code and HEX file are available for download from the Silicon
Chip website (free for subscribers).
Les Kerr,
Ashby, NSW. ($50)
siliconchip.com.au
Using a VL53L0X laser rangefinder module with Arduino
The VL53L0X is, according to ST
Micro, the world’s smallest timeof-flight laser rangefinder (lidar)
IC. It comes in a 4.4 x 2.4 x 1.0mm
SMD package, operates off 2.6-3.5V
and measures distances up to about
2.4m. It is controlled using an I2C serial interface. Various small breakout
boards with this IC are available on
websites like AliExpress and eBay,
for less than $10.
This circuit diagram shows a
VL53L0X laser range-finding module connected to an Atmel ATmega328P micro which is programmed
using the Arduino IDE. This device
measures the distance to an object
(eg, the top of a body of water) and
the local temperature and periodically transmits the results using
long-range digital radio to a remote
receiver.
The circuit is quite simple, with
the microcontroller (IC1) running off
3.3V, derived from a rechargeable
battery using a 3.3V linear regulator.
The VL53L0X module runs off this
same 3.3V supply and its interface to
the micro is via SDA (data) to pin 27
(PC4/Arduino A4) and SCL (clock)
to pin 28 (PC5/Arduino A5).
siliconchip.com.au
The DS18B20 temperature sensor
runs off the same supply with its Dallas 1-Wire interface connected to pin
14 of IC1 (PB0/Arduino D8), with
the required 4.7kW pull-up resistor
included. The “LoRa” digital radio
module’s serial interface is wired up
to pins 11 and 12 of IC1 (PD5/PD6;
Arduino D5/D6).
Its AUX, M0 and M1 control inputs go to digital pins 4 (PD2/D2),
5 (PD3/D3) and 6 (PD4/D4) respectively. M0 and M1 are also fitted
with 3.3kW pull-down resistors to
set their default states.
The Arduino sketch makes use
of the following libraries: SoftwareSerial, Wire, OneWire, Low-Power,
DallasTemperature and VL53L0X.
SoftwareSerial and Wire are supplied with the Arduino IDE; the
others are included in the software
download, along with the sketch
itself, on the Silicon Chip website.
Having installed these libraries,
using the Sketch → Include Library
→ Add .ZIP Library menu option,
ensure the board selected is Arduino/Genuino Uno and then you can
Verify/Compile the sketch. It should
complete without errors. You can
then upload it to your Arduino.
If you plan on using the bare ATmega328P processor to power the
unit, as shown in this circuit diagram, you will need to first install
the Arduino 8MHz bootloader onto
the chip so that it can run without
an external crystal. Details on how
to do this are at: www.arduino.cc/
en/Tutorial/ArduinoToBreadboard
The software sketch is reasonably
easy to understand. The setup() routine initialises the input and output
pin states, the serial port and the
sensors. The loop() function then
echoes any data received over the
digital radio to the serial console
before calling a function to read the
data from each sensor, form it into a
data packet (a short text string) and
then send it over the digital radio.
The unit then powers the radio
and sensors down and goes into
sleep mode for around 16 seconds
before repeating the process. The
data can be received on a PC using
a second LoRa serial transceiver attached to a USB/serial converter.
Bera Somnath,
Vindhyanagar, India. ($60)
September 2017 37
Level shifting the output of the High-Temperature Digital Thermometer
The High Temperature Digital
Thermometer, published in Performance Electronics for Cars (www.
siliconchip.com.au/Article/8638)
and sold as a kit by Jaycar (KC5376),
requires a panel meter that has differential inputs.
That is because the output voltage
from the thermometer is 2.49V when
it is measuring 0°C and this needs
to be subtracted from the reading
within the meter so it gives the correct display.
With the panel meter that the unit
was originally designed for, its INLO
(low) input connects to a 2.49V reference voltage and the INHI (high)
input connects to the thermometer
output.
38 Silicon Chip
When the thermometer output is
at 2.49V, both the INLO and INHI
meter inputs are at the same voltage
and the display shows 0 (°C).
The thermometer output ranges
from 2.49V up to 2.59V (ie, an increase of 100mV) at 1000°C. So when
the thermometer output is 2.59V the
panel meter should show 1000.
However, many panel meters available today don’t have a differential input and their input ground is shared
with the power supply ground.
This means they can only read
the input voltage relative to 0V. To
use one of these meters in the HighTemperature Digital Thermometer,
an additional op amp is required to
level shift the output voltage, which
is highlighted in the pink-shaded
box on this circuit.
Op amp IC4a (half of an LMC6482
dual op amp, IC4a) is used as a differential amplifier (you might find an
LT1490A better for low-temperature
readings). The two 10kW resistors
from the centre pin of LK1 (the thermometer output) to ground via the
non-inverting input (pin 3) of IC4a
form a voltage divider.
The effect is that half the thermometer output voltage is applied
to pin 3, ie, when measuring 0°C, the
voltage at pin 3 is 2.49V ÷ 2 = 1.245V.
There is also a 10kW + 10kW
divider between the output of IC4a
and the 2.49V reference voltage, via
pin 2, the inverting input.
siliconchip.com.au
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So when the output of IC4a is at 0V,
pin 2 is at 2.49V ÷ 2 = 1.245V, ie, the
same voltage as at pin 3 when measuring a temperature of 0°C. Since
the op amp tries to keep its inputs
at the same voltage, this means the
output of IC4a (pin 1) is at 0V when
measuring 0°C.
As the output of the thermometer
rises above 2.49V, the output of IC4a
must also rise by the same amount
to keep its pin 2 voltage equal to the
pin 3 voltage. Thus, it subtracts 2.49V
from the thermometer’s output voltage. Note that IC4 is a rail-to-rail op
amp so the output can swing all the
way down to 0V.
You may need to adjust VR3 in the
thermometer to counteract the inherent offset voltage due to inaccuracies
in IC4. Negative temperatures cannot
siliconchip.com.au
be shown using this circuit, since it
would require a negative supply rail.
If you only want the thermometer
to show temperatures up to 200°C,
the gain of the thermometer amplifier can be increased to 24.652 so the
40.6µV/°C coefficient of the thermocouple results in 1mV/°C at the output (rather than 0.1mV/°C).
To do this, change the 120kW and
15kW resistors connected between
pins 2 and 6 of IC3 to 620kW and
330kW respectively.
The right-hand decimal point
on the panel meter should then be
switched on (usually accomplished
by shorting a pair of pads on the back
of the panel meter) to give a reading
with 0.1°C resolution.
John Clarke,
Silicon Chip.
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September 2017 39
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A
ustralia’s only dedicated trade
event for the electronics industry returns to Melbourne
in September.
Electronex is being held from 6 –
7 September at the Melbourne Park
Function Centre in Batman Avenue,
Melbourne (between the MCG and Rod
Laver Arena).
With over 90 exhibitors and a technical conference plus free seminars
featuring leading international and
local industry experts, this is a “must
see” event for decision makers, enthusiasts and engineers designing or
working with electronics.
Attendees can pre-register at no
charge at www.electronex.com.au
This year’s event will feature a host
of new product releases and continues
to reflect the move towards niche and
specialised manufacturing applica-
tions in the electronics sector as well
as the increased demand for contract
manufacturing solutions.
There are around 20 new companies
at the Melbourne event which reflects
the growth from local manufacturers
for specialist applications that recognise the expertise and quality that is
available from Australian based suppliers.
Last years’s event in Sydney attracted over 1200 electronics design
professionals including electronic
and electrical engineers, technicians
and management; along with OEM,
scientific, IT and communications
professionals, defence, government
and service technicians.
Electronex was launched in 2010 to
provide professionals across an array
of industry sectors with the opportunity to learn about the latest technology
*Denotes - Co-Exhibitor Company/Brand
Represented by Exhibitor
electronex.com.au
40 Silicon Chip
siliconchip.com.au
developments for systems integration,
design and production electronics.
The SMCBA Electronics Design &
Manufacture Conference (founded in
1988) brings together local and international speakers to share information
critical to the successful design and
development of leading-edge electronic products and systems engineering
solutions.
Free seminars
A series of free seminars with overviews on key industry topics will also
be held on the show floor throughout
the two day event and the program
can be viewed on the show website.
This year’s conference program
comprises six main workshops to
be conducted by internationally renowned speakers Vern Solberg and
Phil Zarrow, and a series of training
and certification courses.
The Conference offers engineers,
designers, technicians and managers
the opportunity to hear from our international experts and includes the
following topics:
• Best Practices for Improving Manufacturing Productivity – Phil Zarrow,
• Flexible and Rigid Flex Circuits - Design,
Assembly and Quality Assessment
– Vern Solberg
• The “Deadly Sins” of SMT Assembly –
Phil Zarrow,
• Embedding Passive and Active Components: PCB Design and Assembly
Process Fundamentals - Vern Solberg
• Implementing Advanced “Leading Edge”
and “Bleeding Edge” SMT Component
Technology – Phil Zarrow
• Design and Assembly Process Implementation for Flip-Chip, Wafer Level
and 3D Semiconductor Package Technologies – Vern Solberg
Training/Certification
People involved in electronics manufacturing can enrol to be trained and
certified in a range of IPC programs by
two of the SMCBA Master IPC Trainers
Ken Galvin and Mike Ross:
• ESD Control for Electronics Assembly
• Handling Moisture Sensitive Devices
• Foreign Object Debris (FOD) Prevention
in Electronics Assembly
• Stockroom Materials – Storage and Distribution.
Full Conference details can be seen
at www.smcba.asn.au/conference or
contact Andrew Pollock at the SMCBA
on (03) 9571 2200.
For further information on Electronex 2017, call Noel Gray at Australasian Exhibitions and Events Pty
Ltd on (03) 9676 2133.
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September 2017 41
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New Rigol 4GHz Oscilloscope at Electronex 2017
Emona Instruments, a leading supplier of electronic test and measuring
instruments is exhibiting at Electronex
2017 at Stand A23.
Recently RIGOL Technologies announced the release of their Phoenix
Oscilloscope chipset. This allows Rigol
to bring their unique price performance
value proposition to a new class of cus-
tomers needing advanced instrument
performance and application support.
To celebrate the release of the new
chipset, Emona will be displaying
Rigol’s new high performance oscilloscope with 4GHz Bandwidth, 20GSa/
sec real time sample rate and 1 billion
point memory depth.
Visit www.emona.com.au/rigol
Pi Desktop – see it at element14
stand C17
Pi Desktop, from element14, is a set of Pi accessories which can
convert Raspberry Pi 1/2/3 to a real computer. The accessories insiliconchip.com.au
clude a cap board and an attractive box. The user can plug the cap
board into the 40-pin I/O connector of Pi, install a high capacity
Solid State Drive (SSD) on the cap board and put Pi and cap board
into the box. It becomes a real computer which has all of features of
PC, such as ethernet, WiFi, Bluetooth, hard disk and real time clock.
Users can link the Pi Desktop to a display through HDMI interface.
Key Features:
• Intelligent and safe power controller – users don’t have to remove
the power adapter from Pi board, they just simply push a button
to turn the power on or off like a desktop or laptop
• SSD expansion – It allows users to install a mSATA SSD (up to
1TB) onto the Raspberry Pi.
• RTC – Real Time Clock will provide independent time for any application on the Pi.
• A heatsink – it will cool down the Pi CPU.
• A beautiful enclosure – protect the Pi Board and convert a PCBA
into a real electronics product.
You can find element14 and the Pi Desktop on stand C17 at this
year’s Electronex expo.
September 2017 43
24 Hours Turnaround – The fastest PCB assembly service
launched by QualiEco Circuits
QualiEco Circuits has recently
launched a 24 hours turnaround
service for PCB assembly using their
in-house facility. Overnight delivery
to all major cities of Australia is now
possible once PCB, components and
stencil is ready for assembly. The
company is already offering express
turnaround for PCB manufacturing
from their off-shore plant.
The team at QualiEco Circuits Pty
Ltd is well-known for providing excellent quality electronic manufacturing services and solutions.
The company offers express services
in all product categories. Their customers have been enjoying excellent
quality, low prices and on-time delivery for years. The company has various
customised delivery solutions for all
customers at affordable prices. Customers can choose from the fastest to
semi-fast and normal delivery options
based on their budget and urgency.
QualiEco Circuits bagged two prestigious awards this year – Gallagher
Fuel System’s Supplier of The
Year 2017 and Elite Sup-
plier of The Year 2017. This vibrant,
growing company offers outstanding technical support and attention to detail. Proud of providing
reliable services for more than 14
years, QualiEco Circuits is currently
a market leader in New Zealand.
The company is now enjoying a
successful sixth year of operation
in Australia.
ELECTRONEX STAND A15
Complete solution in specialised PCBs
– Give wings to your imagination!
Rigid PCBs
(Up to 32 layers)
Flexible PCBs
(Single and Multilayer)
Ultra-Low Cost InfiniiVision 1000
X-Series Oscilloscopes from Keysight
Keysight Technologies will show their
InfiniiVision 1000 XSeries oscilloscopes
at Electronex.
With a starting
price of AUD$637,
there are 50 and 100MHz models.
• Ideal for students and new scope users
• Includes an educator’s resource kit with built-in training signals and comes standard with a comprehensive
oscilloscope lab guide at no additional cost
• 6-in-1 instrument integration including a feature unique
to Keysight – built-in frequency response analyser
with Bode plotting
The 1000 X-Series uses Keysight’s MegaZoom IV custom
ASIC technology, which enables a high 50,000 waveforms
per second update rate. This makes it easier to see random
and infrequent glitches and anomalies. The 1000 X-Series
also has a high sampling rate of up to 2GSa/s and comes
standard with two probes.
Information about the InfiniiVision 1000 X-Series oscilloscopes is available at www.keysight.com/find/1000XSeriesinfo
Or visit the Keysight Technologies stand (A12) At Electronex Melbourne and experience the InfiniiVison 1000
X-Series for yourself!
44 Silicon Chip
Rigid-Flexible PCBs
(Single and Multilayer)
Metal Core PCB
(Single and Multilayer)
New Electrolube resins on display
at the HK Wentworth Stand (B15)
Electrolube, distributed in Australia by HK Wentworth,
will showcase some specialist encapsulation resin systems and thermal management materials for Australia’s
LED manufacturers at this year’s Electronex (stand B15).
New products on show will include ER2224, which
provides high thermal conductivity and excellent thermal cycling performance, making it ideal for use in LED
lighting units where it helps to promote heat dissipation
and prolong unit service life.
The thermally conductive epoxy resin system offers
an improved method of cure and subsequent health and
safety benefits for the user.
The tough new UR5638 polyurethane resin provides
a clear, transparent finish and is a low exothermic resin,
making it ideal for LED applications involving the encapsulation of larger LED lighting units.
As an aliphatic polymer, the resin also offers superior
UV stability as well as excellent transmission of visible
light, making it an excellent resin for white light LEDs.
siliconchip.com.au
PANEL SWITCHES
PCB SWITCHES
INDICATORS
JOYSTICKS
KEYBOARDS
APEM offers the broadest range of quality HMI products
in the industry. With exciting new products released each
month, APEM‘s large portfolio of switches, joysticks,
indicators and keypads tailor to several markets.
siliconchip.com.au
Unit 17, 69 O’Riordan Street, Alexandria 2015 NSW, AUSTRALIA
Freecall
September 2017 45
RTB2000 Entry-level Oscillscope
from R&S
Where experience and innovation
come together.
In the formulation, manufacture and global supply of conformal
coatings, thermal pastes, encapsulants, cleaners and lubricants,
we have the solutions of the future. Our ethos of collaboration
and research, combined with a truly global presence and
manufacturing capability has led to the development of ISO
standard, environmentally friendly products for the world’s
leading industrial and domestic manufacturers.
Our unique provision of the complete solution, combined with
the scale and scope of our capabilities ensures a reliable supply
chain, and exemplary service.
Find out how you could become part of the solution. Simply call
or visit our website.
Rohde&Schw
arz
Stand B30 at
Electronex
At Electronex 2017, Rohde & Schwarz premieres its
new R&S RTB2000 entry-level oscilloscope for education, R&D and manufacturing.
Rohde & Schwarz broadens its growing oscilloscope
portfolio with the RTB2000, the first low cost oscilloscope to offer touchscreen operation as well as 10-bit
vertical resolution, providing R&S quality at an extremely competitive price.
Power of ten (10-bit ADC, 10 Msample memory and
10.1” touchscreen) combined with smart operating concepts make the R&S RTB2000 digital oscilloscope the
perfect tool for university and laboratories, for troubleUntitled-1
shooting embedded designs during development and
for production and service departments.
Key Facts:
• 70MHz to 300MHz
• 10-bit ADC
• 10 Msample standard memory
• 10.1” capacitive touchscreen
You can experience the R&S RTB2000 along with
other quality oscilloscopes from the Rohde&Schwarz
range at their stand (B30) at this year’s Electronex Expo.
Stand B15
+61 (0) 2 9938 1566
www.electrolube.com.au
Electronic & General
Purpose Cleaning
Conformal
Coatings
46 Silicon Chip
Encapsulation
Resins
www.hakkoaustralia.com.au
Thermal Management
Solutions
Contact
Lubricants
Maintenance
& Service Aids
A division of H K Wentworth PTY Ltd. (Australaisa)
Unit 3/98 Old Pittwater Road, Brookvale NSW 2100,
1
02/08/2017 09:42:22
Mektronics is Australia’s leading supplier of quality
tools and equipment. We proudly represent and support many of the world’s premium brands.
With over 35 years of experience within the industry
our sales team have unsurpassed industry and product
knowledge and are happy to assist with any queries
you may have.
Mektronics are on Stand B18 at Electronex.
Australian Stencils from Mastercut Technologies
Mastercut Technologies have confirmed
their confidence in the Australasian elec-
Approved Distributor
Australia / New Zealand
tronics industry with the purchase of a
new stencil laser. This new generation fibre
laser by LPKF in Germany is now up and
running, producing stencils for customers
throughout Australia and New Zealand.
Mastercut’s Director of Marketing, Bill
Dennis says “we looked around the world
for the best stencil laser we could find.
Happily, that turned out to be the G6080
from LPKF, the manufacturer of our original laser. This investment means we can
produce faster, cleaner and more accurate
stencils than ever before.”
The performance of the new machine
Electronex Stand C18
has been confirmed with high speed and
repeatable accuracy of around 2µm. Dennis
says “this is ability surpasses any current
fine-pitch requirements both now and well
into the future.”
The machine can handle all stencil types
including shim only, standard meshed,
Zelflex and DEK Vectorguard. An interesting new feature is its ability to produce
oversize stencils up to 1.8m long (1.6m
print area) which is ideal for LED lighting
manufacturers.
Mastercut will be exhibiting again at Electronex in Melbourne (Stand C18).
siliconchip.com.au
siliconchip.com.au
September 2017 47
www.okw.com.au
TO EACH HIS OWN HOUSING
VISIT US AT
AND D24
EX 2016 / ST
ON
TR
ELEC
ROLEC OKW
Australia New Zealand Pty Ltd
Unit 6/29 Coombes Drive,
Penrith NSW 2750
Phone: +61 2 4722 3388
E-Mail: sales<at>rolec-okw.com.au
Here’s a switch . . . from Control Devices
Founded in 1997, Control Devices is Australasia’s leading
supplier of industrial, defence, broadcasting and recording
components and are proud to support the world’s quality engineering products.
Their key objectives are to provide a quality product and customer satisfaction, with a cost effective service.
Among the many new and interesting products that Control
Devices will have on their stand at Electronex (Stand A19) is a
new range of “PBA” 30mm pushbutton piezo sealed switches
from APM.
With their large actuation surface, the new series is in line with
the AV 30mm and FP 40mm series.
Exclusively available on PBA 30 mm models, the prominent
ring option increases the visibility of this piezo switch. It is available in single color, bi-color and tri-color versions.
The 30mm actuation surface improves user comfort and ensures better switch visibility, while the piezo technology ensures
very long life (50 million
cycles) making it ideal
for applications where
reliability is key.
Because the switches are totally sealed (IP68 and IP69K) they
are perfectly suited to humid applications (eg, yachting, spa, swimming pools, etc) and for sectors requiring
a regular cleaning of control surfaces (eg,
medical and food industries).
Available in flush or prominent, translucent or coloured, the
illuminated ring is available in single colour, bi-colour and tricolour versions.
Control Devices will be delighted to discuss your particular
switch, sensor, control and other electronics requirements at
Stand A19 at Electronex 2017.
Rolec OKW has a new range of “different” cases . . .
The new BODY-CASE is the latest
product series in the range of wearable
enclosures by OKW Gehäusesysteme
and is perfect for applications on or
near the body.
Thanks to its small, compact format,
it is perfect for wearing on the body: on
your arm, around your neck, in shirt
and trouser pockets or carried loose in
an article of clothing.
The body case has a three-part design
consisting of a top and a bottom part and
a matt TPE sealing ring. The enclosures are made of ASA
material in the colour traffic white and have a modern appearance thanks to highly polished surfaces. The top parts
are available from stock, either with or without a recessed
surface for decor foils or membrane keyboards. The sealing
ring, available in vermilion and lava (similar to anthracite)
48 Silicon Chip
colours allows protection classes IP65 and
IP67. The dimensions of the enclosure are
54 x 45 x 17.5 mm (L x W x D). Possible
applications include mobile data recording
and data transmission, measuring and control engineering, digital communications
technology, emergency call and notification
systems as well as bio-feedback sensors in
the fields of health care, medical technology, leisure and sports etc.
OKW enclosures can be customised on
request, modification services include CNC
milling and drilling, digital or screen printing of legends
and logos, special finishes, EMC shielding, keypads and
labels, all modifications are carried out by the in-house
service centre.
Rolec-OKW will demonstrate the BODY-CASE and various other cases at Electronex 2017 Stand B11.
siliconchip.com.au
Power of ten
Get in touch with the
new ¸RTB2000
series oscilloscopes.
¸RTB2000 oscilloscopes (70 MHz to 300 MHz) team top technology
with top quality. They surpass all other oscilloscopes in their class,
delivering more power plus intuitive usability at a convincing price.
For more information visit
www.scope-of-the-art.com
sales.australia<at>rohde-schwarz.com
Visit our stand number B30
at Electronex Melbourne
siliconchip.com.au
September 2017 49
吀栀攀 䬀攀礀猀椀最栀琀 䈀攀渀挀栀
吀栀攀 戀攀渀挀栀 琀漀漀氀猀 礀漀甀爀 戀甀搀最攀琀 眀椀氀氀 氀漀瘀攀
吀栀攀 搀攀攀瀀攀猀琀 戀攀渀挀栀 椀渀 琀栀攀 椀渀搀甀猀琀爀礀
眀眀眀⸀欀攀礀猀椀最栀琀⸀挀漀洀
50 Silicon Chip
siliconchip.com.au
Pb
siliconchip.com.au
September 2017 51
Design, Develop, Manufacture with the latest Solutions!
Showcasing new innovations and technology in electronics
In the fast paced world of electronics
you need to see, test and compare
the latest equipment, products and
solutions in manufacture and systems
development.
Make New Connections
• Over 90 companies with the latest
ideas and innovations
• New product, system & component
technology releases at the show
• Australia’s largest dedicated
electronics industry event
• New technologies to improve design
and manufacturing performance
• Meet all the experts with local
supply solutions
• Attend FREE Seminars
Knowledge is Power
SMCBA CONFERENCE
The Electronics Design and
Manufacturing Conference delivers
the latest critical information
for design and assembly.
Local and International presenters
will present the latest innovations and
solutions at this year’s conference.
Details at www.smcba.com.au
In Association with
Supporting Publication
Organised by
Free Registration online!
www.electronex.com.au
52 Silicon Chip
siliconchip.com.au
Melbourne Park Function Centre 6-7 September 2017
YOUNG
MAKER FUN!
SHARE YOUR LOVE OF ELECTRONICS WITH YOUR KIDS!
LEARN TO CODE
DRAW CIRCUITS
Friendly, easy-to-use robots to learn about electronics,
programming and robotics. Hours of fun and a great way
to teach "young engineers" about science, technology,
engineering and mathematics (STEM). Visit our website
to see videos on how engaging these robots really are.
ONLY
$
69
95
MEET EDISON KR-9210
A compact, pre-assembled robot that
is built to last. Pre-programmed with
6 robot activities set by barcodes,
can be programmed using simple
drag-and-drop programming
blocks or a Python-like written
language. Modular and easily
expandable using LEGO®
bricks. Ages 5+.
$
99 95
BASIC KIT
KJ-9340
Contains a Circuit Scribe pen, six modules, battery,
workbook and accessories to get started. Explore basic
circuit concepts like conductivity and work up to creating
a touch-sensitive circuit using the NPN transistor. 11pc.
LEARN
ABOUT
...BASIC
ELECTRONIC
S
WITH Circu
it
S
cribe
There’s now
a new way to
teach kids the
fundamentals
of electronics.
Like the name
suggests, kids
can draw the
circuits with th
e conductive pe
n
and then watch
them come to
life. Each kit in
clud
sketchbook with es a detailed
examples and
templates to w
ork through, as
well as magne
tic modules, LE
Ds
and component
s. The modules
magnetically at
tach using the
steel sheet that
go
paper. Visit our es behind the
website for vid
eos
and full list of co
ntents.
LEARN MORE
AT:
www.jaycar.com
.au
INTRODUCING
MBOT KR-9200
ONLY
149
An easy-to-assemble,
entry-level robot that
can avoid obstacles,
follow lines, play soccer,
and more. Control
from your Smartphone
or Tablet using the
freely available app,
or program using
simple drag-and-drop
programming blocks or
Arduino® IDE. Ages 12+.
$
ONLY
119
$
ULTIMATE KIT
MAKER KIT
KJ-9310
17 piece kit to take your circuit sketches
to the next level with inputs, outputs, and
signal processing in your circuits.
199
$
/stem
KJ-9300
32 piece kit for more complex, robust circuits, which you
can hook up to programmable platforms like Arduino®
(Arduino® not included).
TEACH YOUR KIDS ELECTRONICS
WITH LITTLEBITS
A clever range of kits to help educate and inspire kids (and
yourself) about electronics and programming. Each littleBits
kit has easy-to-use colourcoded building blocks, with
step-by-step instructions.
RULE YOUR ROOM KIT
KJ-9120 $199
GIZMOS AND GADGETS KIT
KJ-9100 $389
$
49 95
CIRCUIT STICKERS
STEM STARTER PACK KJ-9330
Uses copper tape with component stickers to allow kids to merge
art and electronics. Includes copper tape, batteries, LEDs and
heaps of templates and exercises, including circuits, switches.
Even the box can be turned into a project!
FROM
199
$
SEE ALL OF OUR STEM RANGE AT jaycar.com.au/stem
Catalogue Sale 24 August - 23 September, 2017
To order phone 1800 022 888 or visit www.jaycar.com.au
LEARN & HAVE FUN
O® BASICS
IN
U
D
R
A
E
H
LEARN T
Includes handy
storage case!
ALL-IN-ONE LEARNING KIT XC-3900 WAS $79.95
This starter kit includes the UNO main board, breadboard, servo motor,
light sensor, RGB LED, joystick, buzzer, LED matrix, line tracer, and
assorted components and cables. All supplied in a handy carry case with
dividers, and a quick start guide with links to online tutorials.
LEARN MORE AT:
www.jaycar.com.au/arduino-learning
$
6995
SAVE $10
1. BEGINNER PROJECT:
BUILD A SNAKE GAME KIT
Once you have successfully performed some
of the online tutorials, you can build this fun old
‘Snake’ game (Reminiscent of the old Nokia phone
and Atari days – showing our age?). All of the
necessary components are already included in
the XC-3900 kit above.
LEARN MORE AT:
www.jaycar.com.au/snake-game
LINKER 4-DIGIT
7-SEGMENT MODULE
MAKE PROTOTYPING EASIER
This Linker module and accessories range is
based around a series of Arduino® compatible
modules, shields and cables that make
prototyping easy. It is ideal for schools, big
or small kids keen to learn and play with
Arduino®. Simply attach linker shields to Jumper
mainboards and connect with Linker
Leads (XC-4558-59-60)
Shields. No soldering required.
Red LED (XC-4566)
Green LED (XC-4565)
LEARN MORE AT:
www.jaycar.com.au/linker
Linker Shield (XC-4557)
LINKER TOUCH
SENSOR XC-4572
Arduino® Board
(sold seperately)
LINKER BASE SHIELD
$
XC-4557
This is the base shield
of Linker kit, it allows a
connection between all
Linker sensors/modules and
Arduino®/pcDuino.
• Connections: 1 x SPI,
2 x IIC, 1 x UART
• 69(W) x 59(H) x 18(D)mm
24 95
LINKER JUMPER LEADS
Connects Linker kit sensors/
modules and Linker kit base
shield. 2.54mm headers for
easy and tidy connection.
4 pins, 2.54mm spaced.
• Sold individually
200MM XC-4558
500MM XC-4559
1000MM XC-4560
4 ea
$ 95
TECH TIP
PROGRAMMING MADE EASY
WITH ARDUBLOCK:
LINKER LED BAR XC-4568
• Controls 10 LED's
• Create bar graph displays
• 44.1(W) x 24.2(H) x 11.5(D)mm
$
1195
10 95
9
$ 95
6
$ 95
Uses a Thermistor to detect
the ambient temperature. The
resistance of a thermistor will
increase when the ambient
temperature decreases.
• 20.0(L) × 20.0(W) ×10.6(D)mm
TO LEARN MORE ABOUT ARDUBLOCK VISIT:
www.jaycar.com.au/ardublock
Page 54
A capacitive touch sensor
to replace a push button.
Low in power consumption,
fast response and easy to
operate. Voltage reads 0V
when idle, changes to 5V
when touched.
• 28(W) x 24(H) x 8(D)mm
LINKER
TEMPERATURE
MODULE XC-4576
ArduBlock is a graphical drag-and-drop type
programming environment for Arduino®. Ideal
for kids! By dragging and dropping colour coded
blocks into the workspace, a fully functioning
Arduino® program can be created easily!
$
XC-4569
Uses a chipset of TM1637 to
drive a 12-pin 4-digit command
anode 7-segment LED. The
MCU only needs two GPIO
lines to control it.
• l2C interface
• 46.2(W) x 24.3(H) x 14.5(D)mm
Follow us at facebook.com/jaycarelectronics
Catalogue Sale 24 August - 23 September, 2017
WITH ARDUINO®
BUNDLE
$
89 95
3
SAVE $19.95
BUNDLE
2
$
Advanced
finished project
79 95
SAVE $11.35
YOU WILL ALSO NEED:
Ethernet Expansion Module XC-4412
KIT VALUED AT $109.90
Intermediate
finished project
1
YOU WILL ALSO NEED:
Temperature and Humidity
Sensor Module XC-4520
Relay Board
XC-4419
Jumper Leads WC-6028
KIT VALUED AT $91.30
Snake Game
finished project
NO ADDITIONAL
PARTS NEEDED
2. INTERMEDIATE PROJECT
3. ADVANCED PROJECT:
Once you have had your fun with the Snake Game, build this kit for something practical
for real-world applications. In this project we show you how to create an Arduino®based Temperature Controlled Relay (called Thermostat). You’ll need to have the
XC-3900 kit opposite and a few more parts in-store to get this going.
LEARN MORE AT: www.jaycar.com.au/arduino-thermostat
By adding an Ethernet Shield to your project, you can get your Arduino® serving
up webpages, displaying sensor information and being controlled by a browser
interface. You could even develop your own Arduino® based home
automation system!
LEARN MORE AT: www.jaycar.com.au/diy-ethernet-controller
BUILD A TEMPERATURE CONTROLLED RELAY
CONTROL YOUR ARDUINO® FROM YOUR PHONE OR COMPUTER
DON'T FORGET THE MAKER ESSENTIALS
FROM
4
$ 50
PC BOARDS - VERO TYPE STRIP
Alphanumeric grid, pre-drilled 0.9mm,
2.5mm spacing.
95MM(W) X 75MM(L) HP-9540 $4.50
95MM(W) X 152MM(L) HP-9542 $7.95
95MM(W) X 305MM(L) HP-9544 $11.50
5 ea
$ 50
7
$ 95
LIGHT DUTY
HOOK-UP WIRES WH-3000
ARDUINO® COMPATIBLE
BREADBOARD PB-8820
Quality 13 x 0.12 tinned hook-up wire on
plastic spools. 8 different colours available.
• 25m roll
Mid-sized prototyping breadboard with
400 tie points. 83(W) x 55(H)mm
• 300 tie points in centre section
• 100 tie points on power rails
9
$ 95
BREADBOARD POWER MODULE
XC-4606
Adds a compact power supply to your
breadboard. Concave design saves space.
• Plugs straight into most breadboards
• Can be set to 3.3V or 5V
DUINOTECH CLASSIC (UNO) XC-4410
13 50
$
ELECTROLYTIC CAPACITORS
RE-6250
Ideal for prototyping. Values range from
1uF to 470uF.
• Pack of 55
1150
$
POLYMORPH PELLETS NP-4260
Softens to be formed into any shape at
around 62 - 65° C. It can be drilled, sanded,
ground, machined or heated and reformed
again and again. 100g bag of 3mm pellets.
To order phone 1800 022 888 or visit www.jaycar.com.au
The duinotech classic is a 100% Arduino®
compatible development board. Its
stackable design makes adding expansion
shields a piece of cake.
• Powered from 7-12VDC or from
your computers USB port
• ATMega328P Microcontroller
$
2995
See terms & conditions on page 8.
Page 55
FUN FOR KIDS TO BUILD
AGES 6+
14 95
$
REMEMBER WHEN YOU FELL IN LOVE WITH ELECTRONICS?
Give one of these kits as a gift to your child, grandchild, niece or nephew so they can fall
in love with electronics as well. Imagine the joy you’ll get while you build it with them.
No soldering required.
$
34 95
$
KIDS CLOCK KIT KJ-8996 CAR OR BOAT SNAP ON KIT KJ-8972
Bright coloured parts. Easy
to assemble. No batteries
required. 31 pieces.
195mm Dia.
49 95
$
49 95
24-IN-1 SNAP-ON SOLAR PROJECT KIT KJ-8987
GYRO ROBOT KIT KJ-8957
Up to 24 projects including a solar coloured lamp, hand crank Up to 7 experiments - Robo Gyro, Gyro
fan and police siren. Supplied with dynamo hand crank, solar Compass, Gyrorector, Segway, Rope Walker,
panel and base board.
Balance Game& Flight Simulator.
Requires 3 x AAA batteries.
50+ projects including magnet controlled
lamp or fan, air propelled car, and
underwater or air propelled boat. Requires
2 x AA batteries.
AGES 8+
$
24 95
4-IN-1 SOLAR
ROBOT KIT KJ-8965
$
FROM
39 95
DIY METAL CONSTRUCTION KITS
Easy to assemble kits for kids. Tools and instructions
included. No soldering required.
It can 'transform' between
a T-Rex or Rhino beetle with RC DUMP TRUCK 185mm long. LED lights. 4ch remote. 3 x
moving legs and jaw, Robot
AAA & 4 x AA batteries required. KJ-8998 $39.95
with walking legs and moving LAMP 300mm tall. Power using USB (cable supplied) or 2 x
wheels, and a futuristic
AAA batteries. KJ-8999 $49.95
miners drilling machine.
AGES 12+
$
ROBOT ARM KIT
KJ-8916
Capable of 5 separate
movements and can easily
perform complex tasks. The
kit is supplied as parts and
makes an excellent project for
anyone interested in robotic
construction. 100g lift capacity.
Requires 4 x D batteries.
6995
$
29 95
69 95
34-IN-1 SNAP ON
SOLAR PROJECT KIT
698-IN-1 SNAP ON
ELECTRONIC PROJECT KIT KJ-8985
KJ-8983
Build up to 34 projects including electric
fan, FM radio and learn parallel and
series circuits. Requires 4 x AA batteries.
Build you own helicopter, alarm clock,
lighthouse, sound effects and more using
various controls like light, magnets, sound,
water and touch. 50pce kit, requires
4 x AA batteries.
AGES 10+
$
Battery not included.
$
49 95
SOLAR
POWERED
ROBOT KIT KJ-8966
Transforms into 14
different functional robots.
$
49 95
SMART FRILLED LIZARD KIT
KJ-8968
Build this interactive lizard, it can be
set to follow you or scamper away after
spreading its frill. 370mm long. Requires
4 x AAA batteries.
6-IN-1 SOLAR EDUCATIONAL KIT CAN ROBOT KIT
$
59 95
$
59 95
HYDRAULIC ROBOT ARM KIT
3-IN-1 ALL TERRAIN ROBOT
KJ-8997
Use it to command 6 axes of varied
movement. Use the gripper or the suction
cup to lift items up to 50g. Built-in braking
system. No batteries required.
KJ-8918
Use the 6 terrestrial tracks/crawlers to create
a working gripper, rover or forklift. Electric
motors and detailed instructions included.
Requires 4 x AA batteries.
Page 56
KJ-8936
Build any one of six different
projects: windmill, car, dog,
plane, airboat, revolving
plane. Power from the
sun or household
50W halogen light.
12 95
$
Follow us at facebook.com/jaycarelectronics
KJ-8939
Build wacky robots out
of a coke can, a water
bottle or wasted CDs! No
batteries required.
12 95
$
Catalogue Sale 24 August - 23 September, 2017
EXPLORE BASIC ELECTRONICS
TEACH KIDS THE FUNDAMENTALS WITH "OLD SCHOOL" ELECTRONICS
The Electronics magic happens when
electrons flows through a conductive
circuit, the thing pushing the electrons
is called the voltage, and the flow of
electrons is called the current. Electronic
components include passive components
like resistors and capacitors, as well
as active components like diodes,
transistors and Integrated Circuits (IC).
It is important to understand how a
transistor works, because this is the
building block of most modern circuits
including IC’s.
A transistor has three terminals, the
Base, the Emitter and Collector. When
current flows in the Base it causes a
larger current to flow through the Emitter,
this is called the transistor gain, and it
has an amplification effect. This is the
theory behind the cool amplifier projects
in Short Circuit Volume I, 2 and 3, like
stereo amplifiers, and electric guitar
special effects amplifiers.
Transistors can also be used as a switch,
if the current flowing in the Base of
the transistor is large enough, it forces
the transistor to enter what is called a
saturation mode, where it basically acts
like an ON/OFF switch, the Jaycar Short
Circuits Intruder alarm, Light Scanner,
and Dasher Flasher for cars all utilise this
special feature of the transistor circuit.
TOOLS TO GET YOUNG ENTHUSIASTS STARTED
2ea
13 95
$ 95
DURATECH LEAD-FREE SOLDER - 25W 240V
HOBBY PACKS
SOLDERING IRON TS-1465
• 99.3% tin, 0.7% copper lead-free
• 12g tube
0.71MM NS-3086
1.00MM NS-3092
$
$
Ideal for the hobbyist and handy person. Has a stainless
steel barrel and orange cool grip impact resistant handle.
Fully electrically safety approved.
SHORT CIRCUITS BOOK - VOL.1
AND PROJECT KIT KJ-8502
3995
A great way to teach kids about electronics – no soldering required!
Kit includes baseboard, springs and components to make 20+ projects,
and 96-page coloured Short Circuits Vol. 1, which is complete with
comprehensive assembly instructions and a full technical discussion
explaining exactly how the circuit works.
ALSO AVAILABLE: SHORT CIRCUITS BOOK - VOL.1 BJ-8502 $9.95
SHORT CIRCUITS BOOK VOL. 2 BJ-8504
12 95
$
$
BENCHTOP WORK MAT HM-8100
Durable A3 size PVC cutting mat to protect
your work benchtop.
• Ruled with a centimetre spaced grid for
easy referencing
• 3mm thick- 450 x 300mm
Once kids have learnt the basic
skills and knowledge from Short
Circuits 1, they can move onto
learning how to solder with circuit
board-based projects. With this
book and kits sold separately,
they can make such things as; a
mini strobe light, police siren, mini
organ, etc. All projects are safe
and battery powered.
29 95
STAINLESS STEEL
CUTTER PLIERS TH-1812
Set of five 115mm cutters and pliers for electronics,
hobbies, beading or other crafts. Soft ergonomic grips.
Includes flush cutters, long nose, flat nose, bent
nose & round nose pliers.
STARTER KIT WITH
SOLDERING IRON & DMM
TS-1652
The ideal starter package for young electronics
enthusiasts or the home handyman, this
kit contains everything needed for
basic electronics work. Includes
DMM, 25W soldering iron,
de-soldering tool, lead free
solder, screwdrivers, side
cutters, & long nose pliers.
To order phone 1800 022 888 or visit www.jaycar.com.au
$
3995
21 project kits sold separately –
see website or in-store
12 95
$
SHORT CIRCUITS BOOK VOL. 3 BJ-8505
Volume 3 describes how to build
over 30 circuit board-based
projects (sold separately) such
as Ding Dong door bell, simple
intruder alarm and amplifier.
Soldering techniques are
discussed in detail and proper use
of digital multimeter.
30 project kits sold separately –
see website or in-store
14 95
$
TO LEARN MORE VISIT:
www.jaycar.com.au/short-circuits
See terms & conditions on page 8.
Page 57
MY FIRST WORKBENCH
$
NOW
24 95
SAVE $5
5
1
Most of us adults have a workbench of some kind, be it an entire
workshop with shadow board or a temporary area on the kitchen
table. Why not make a work area for the kids too so they can get
“hands-on”. Here’s just a small selection of the tools to get your
kids (or Grandkids) started in the world of making and electronics.
14 95
$
4
2
6
9
NOW
24 95
SAVE $5
3
8
$ 95
$
$ 95
19 95
$
1. 30 PIECE TOOL KIT WITH CASE
TD-2166 WAS $29.95
• Side cutters, long nose pliers,
snap-blade knife
• Precision screwdriver with bits
• Folding allen keys 1.5, 2, 3, 4, 5, 6mm
• 210(L) x 160(W) x 48(H)mm
4. 10W 240VAC SOLDERING STATION
TS-1610 WAS $29.95
• Compact & lightweight
• 10W heating element
• Rotary temperature control dial
• Integrated soldering pencil holder
• 100-450°C Temperature range
2. LOW COST DIGITAL MULTIMETER
QM-1500
• Includes transistor & diode test.
• 500V, 2000 count
• AC voltages up to 750V
• DC voltages up to 1000V
• DC current up to 10A
5. 28 COMPARTMENT
STORAGE CASE HB-6313
• Removable partitions allowing
customised arrangements to suit
your needs
• 2 snap action latches secure
the hinged lid
• 357(W) x 48(H) x 220(D)mm
3. THIRD HAND WITH LED MAGNIFIER
6. MAGNIFYING GLASS QM-3505
TH-1987
• 2 x Magnifying lens, soldering iron holder, • 2x magnification
• Huge 4.5” diameter viewer allows hands
2 x strong adjustable alligator clips
free operation
• Heavy cast iron base for added stability
• Foldable for easy storage
• Requires 3 x AAA batteries
5MP USB DIGITAL
MICROSCOPE
$
24
95
SOLDERING STARTER KIT
TS-1651
Includes all soldering essentials for
various projects. Pack includes 240V
20/130W turbo soldering iron, spare tip,
stand, solder, metal solder sucker with
spare tip and O-ring.
149
$
QC-3199 WAS $189
Excellent for educational
purposes or a wide range
of applications such as
technicians, jewellers,
laboratory work, and
much more.
• 10x to 300x magnification
• LED illumination
• Adjustable focus dial
SAVE $40
12 95
$
8x10" MAGNETIC MAT TH-1867
Great for keeping nuts and bolts in place. The magnetic side
of the mat is the "Whiteboard" side which allows you to write
references or notes next to the nuts and bolts.
14 95
13 95
$
$
SOLDERING TOOL KIT TH-1851
DIGITAL
VERNIER
Selection of hand-tools and accessories
for soldering work. Phillips screwdriver,
CALIPERS TD-2081
tweezers, heatsink and 3 double-ended
Excellent value for money, ideal for general use. 245mm long.
tools for poking, scraping, leg-bending, and
• 150mm measurement range
flux-removal.
• Digital display
6 ROLLS INSULATION
TAPE NM-2806
19 95
$
• One roll each of green, black,
yellow, white, blue and red
• 19mm wide
• Each 5m in length
PCB HOLDER TH-1980
Hold PCBs of up to 200 x 140mm in size.
Page 58
3
$ 95
16 95
$
WIRE STRIPPER TH-1824
Strips cable without damaging the conductors.
• Automatically adjusts to insulation diameter
• One hand operation
• Spring return
JUMPER LEAD KITS WC-6010
Ideal for connecting devices for testing.
10 leads supplied.
STANDARD WC-6010 $6.95
HEAVY DUTY WC-6020 $11.95
FROM
6
$ 95
Follow us at facebook.com/jaycarelectronics
COMPONENT LEAD
FORMING TOOL TH-1810
Get the hole spacing for your
resistors and diodes perfect
every time. Provides uniform
hole spacing from 10 to 38mm.
• 138mm long
8
$ 95
Catalogue Sale 24 August - 23 September, 2017
EXCLUSIVE
CLUB OFFERS:
20% OFF
20% OFF
F
F
O
20%
ENCLOSURES*
FOR NERD PERKS CLUB MEMBERS
WE HAVE SPECIAL OFFERS EVERY MONTH.
LOOK OUT FOR THESE TICKETS IN-STORE!
* Includes Sealed Polycarbonate, Potting Boxes, Jiffy, Bulkhead, Sealed
ABS, Polystyrene boxes and Instrument Cases.
ENCLOSURES*
*
OSURES
ENCL
EXCLUSIVE
* Includes Sealed
Polycarbonate,
Potting Boxes,
Jiffy, Bulkhead,
ABS, Polystyrene
Sealed
boxes and Instrum
ent Cases.
NOT A MEMBER? Visit www.jaycar.com.au/nerdperks
Sealed
Jiffy, Bulkhead,
Potting Boxes,
Polycarbonate,
ent Cases.
* Includes Sealed
boxes and Instrum
ABS, Polystyrene
NERD PERKS CLUB OFFER
CLUB OFFER
EX
CLUS E
CLUB OFIV
FER
NERD PERKS CLUB
OFFER
Sign up NOW! It’s free to join.
NOT A MEMValid 24/7/17 to 23/8/17
BER?
E Sign up NOW! It’s free to join.
EXCLUSIV
R
JUST
CLUB OFFE
BUY 2 GET 1
FREE
PARTS
CABINETS
$39.95
BER?
NOT A MEM! It’s free to join.
Valid 24/7/17 to
30%
SMALL HB-6317
REG $9.95ea.
CLUB 3 FOR $19.90
LARGE HB-6318
REG $24.95ea.
CLUB 3 FOR $49.90
Valid 24/7/17 to
23/8/17
Sign up NOW
SAVE
NERD PERKS CLUB OFFER
NOT A MEMBER?
SOLDERING
ACCESSORIES
KIT
VALUED AT $55.65
SOLDER
NS-3088
BRAID
NS-3020
23/8/17
SAVE
25%
FREE
SB-1737
4 PACK AA BATTERIES*
NI-CD &
NI-MH
BATTERY
CHARGER
$
MB-3551 RRP $59.95
SAVE
1595
FLUX CLEANER
NS-3070 NA-1008
3x
HB-6317
shown
* 2000mAh Ni-MH batteries 4pk valid with purchase of MB-3551
NERD PERKS
NERD PERKS
NERD PERKS
NERD PERKS
SAVE
SAVE
SAVE
SAVE
30%
25%
10M CAT 5E PATCH LEAD
YN-8205 REG $14.95 CLUB $9.95
Blue.
15%
12W LED RECTANGULAR FLOOD
LIGHT SL-3931 REG $39.95 CLUB $29.95
IP68. 1,136 lumen output.
CCTV VIDEO & POWER CABLES
WQ-7279 REG $19.95 CLUB $16.95
18m.
NERD PERKS
NERD PERKS
NERD PERKS
SAVE
SAVE
SAVE
25%
20%
20%
20%
AUTOMOTIVE FUSED RELAY
SY-4077 REG $9.95 CLUB $7.95
SPST 12V 30A.
NERD PERKS
SAVE
10%
DIGITAL THERMOMETER
MULTI FUNCTION TOOL
DIODE 1N4007 1000V 1A D041
QUICK CONNECTOR PACK
QM-1602 REG $39.95 CLUB $29.95
Includes K-Type Thermocouple.
TH-1843 REG $24.95 CLUB $19.95
Cutter/stripper. 160mm long.
ZR-1008 REG $12.95 CLUB $9.95
Pack of 100.
PT-4536 REG $39.95 CLUB $34.95
300 pieces.
NERD PERKS
NERD PERKS
NERD PERKS
SAVE
SAVE
SAVE
10%
10%
10%
12V PROGRAMMABLE INTERVAL NIBBLING TOOL
TIMER MODULE
TH-1768 REG $14.95 CLUB $12.95
AA-0378 REG $39.95 CLUB $34.95
Cuts aluminium, plastic and copper.
SAVE
10%
75 OHM RG59 COAX CABLE
RESISTOR PACK
WB-2005 REG $17.95 CLUB $15.95
30m roll.
RR-0680 REG $16.95 CLUB $14.95
300 pieces. 1/2W 1%.
NERD PERKS CLUB MEMBERS RECEIVE:
20%
OFF
ENCLOSURES
YOUR CLUB, YOUR PERKS:
CHECK YOUR POINTS &
UPDATE DETAILS ONLINE.
LOGIN & CLICK
"MY ACCOUNT"
*
* Includes Sealed Polycarbonate, Potting Boxes, Jiffy, Bulkhead, Sealed ABS, Polystyrene boxes and Instrument Cases.
To order phone 1800 022 888 or visit www.jaycar.com.au
NERD PERKS
See terms & conditions on page 8.
Conditions apply. See website for T&Cs
Page 59
WHAT'S NEW
WE'VE HAND PICKED JUST SOME OF OUR LATEST NEW PRODUCTS. ENJOY!
20MHZ USB OSCILLOSCOPE
QC-1929
Ideal for the traveling or compact
workbench. Provides 20MHz
bandwidth and high accuracy.
Includes 2 x probes.
• USB interface plug & play
• Automatic setup
• Waveforms can be exported as
Excel/Word files
• Spectrum analyser (FFT)
• External trigger input
$
199
$
AIRBLOCK MODULAR
PROGRAMMABLE DRONE
KR-9220
A 7-piece modular drone that can be turned into a
hovercraft, car, spider and more! It is made from light
but durable plastic foam so you can bump into walls
without making dents. Control it from your Smartphone
or iPad via Bluetooth using a freely available iOS or
Android app. Control and program your aerial stunts
through the Makeblock App. Simply drag-and-drop
different blocks of commands - like forward, pause,
turn, and forward - and connect
them together to create a seamless
action. Ages 8+.
• 6-axis Drone:
235(L) x 54(H)mm
• Hovercraft:
335(L) x 208(W) x 126(H)mm
ONLY
899
$
100MHZ DUAL
CHANNEL OSCILLOSCOPE QC-1936
Lightweight and compact unit with large 7-inch colour-LCD
for detailed readings. Built-in waveform generator for various
testing applications. Includes 2 probes and USB cable.
• PC connection via USB
• SD card support
See website for specifications
12V/24V BATTERY
TESTER W/LCD QP-2263
$
Displays the charge condition
of your 12V or 24V car, RV
or boat batteries. Includes
battery clamps, eye terminals,
and cigarette lighter socket.
75(W) x 48(H) x 19(D)mm.
• Voltage range:
11-17VDC / 22-30VDC.
12VDC 30A SINGLE RELAY
WIRING KIT SY-4081
Safe and easy method to install any
high current 12V device in the car
such as a fridge or driving lights.
• Includes 2m wiring loom, 30A relay,
& contura style switch
COMING SOON...
24 95
DUE OCTOBER. KEEP AND EYE
ON OUR WEBSITE FOR LAUNCH.
1080P AHD STARLIGHT
CAMERAS
299
Airblock's Visual
Programming Software.
Tablet not included
USB TO RS-485/422
CONVERTER XC-4136
QC-8678
Starlight is a revolutionary new sensor
technology, providing increased clarity
and full colour in low light
conditions. Vari-focal
2.8-12mm lens for optimum
coverage. Built-in infrared
LEDs for zero light situations.
BULLET QC-8678
DOME QC-8680
$
QC-8680
199ea
$
RS-485/422 is commonly found in thermal
printers (eg, point of sale), modem
communications, etc. This converter
provides that connection from your modern
USB port with great reliability.
• Automatically detects serial signal rate
• Plug & Play
• Up to 480Mbps
$
39 95
49 95
NOTICED SOMETHING
DIFFERENT?
Regular CMOS
Starlight Technology
TERMS AND CONDITIONS: REWARDS / NERD PERKS CARD HOLDERS FREE GIFT, % SAVING DEALS, DOUBLE POINTS & MEMBERS OFFERS requires ACTIVE Jaycar Rewards / Nerd Perks Card
membership at time of purchase. Refer to website for Rewards/Nerd Perks Card T&Cs. PAGE 2: Intermediate Kit includes 1 x XC-3900 + 1 x XC-4520, 1 x XC-4419, + 1 x WC-6028. Advanced Kit includes
1 x XC-3900 + 1 x XC-4412. PAGE 7: Nerd Perks Card holders receive special price of $39.95 for Soldering Accessories Kit (1 x NS-3088, 1 x NS-3020, 1 x NS-3070 & 1 x NA-1008) when purchased as
bundle. Nerd Perks Card holders receive special price of $19.90 for 3 x HB-6317 Small Parts Cabinets & $49.90 for 3 x HB-6318 Large Parts Cabinets. Nerd Perks Card holders receive FREE Rechargeable
AA batteries (SB-1737) valid with purchase of MB-3551 Battery Charger. Nerd Perks Card holders receive 20% OFF Enclosures applies to Jaycar 230 Plastic Boxes product category.
You'll have noticed that store details have
disappeared on this page. With over 100 stores
across Australia & New Zealand, we can no
longer fit them into the space allocated, instead
- we are going to use the space to highlight NEW
products. If you are looking for store details please
visit www.jaycar.com.au or call 1800 022 888
FOR YOUR NEAREST STORE &
OPENING HOURS:
1800 022 888
www.jaycar.com.au
92 STORES & OVER
140 STOCKISTS NATIONWIDE
NEW STORE: JINDALEE
2/601 Seventeen Mile Rocks Rd, 4073 QLD
PH: 07 3715 6377
Head Office
320 Victoria Road,
Rydalmere NSW 2116
Ph: (02) 8832 3100
Fax: (02) 8832 3169
Online Orders
www.jaycar.com.au
techstore<at>jaycar.com.au
09-17-01-01
Arrival dates of new products in this flyer were confirmed at the time of print but delays sometimes occur. Please ring your local store to check
stock details. Occasionally there are discontinued items advertised on a special / lower price in this promotional flyer that has limited to nil stock
in certain stores, including Jaycar Authorised Stockist. These stores may not have stock of these items and can not order or transfer stock.
Savings off Original RRP. Prices and special offers are valid from Catalogue Sale 24 August - 23 September, 2017.
Are we about to make yet another monumental mistake?
Let’s face it: Australia has had some really dumb decisions over the
years when it comes to communications. Like plonking VHF TV
channels in the international FM Radio band many years ago. Like
recently shutting off Radio Australia shortwave services so the bush has
no viable alternative. Are we about to make yet another one with DAB+?
What’s next for
Australian
Broadcast Radio?
by
ALAN HUGHES
C
urrently we have a mish-mash
of broadcast radio services in
Australia. Depending mainly
on topography, the capital cities are
relatively well-served with AM, FM
and DAB+
Move to regional then to outback
areas, the choice quickly reduces to
less, to not much, to none at all.
But Australians could have truly
national radio services and countries
such as New Zealand and Indonesia
are showing the way with DRM – Digital Radio Mondiale.
Currently we have AM, FM and
DAB+ digital radio in all mainland
State capitals, and AM and FM covering regional areas.
But since 31st January this year,
when the ABC in its wisdom switched
off all shortwave broadcasts, there are
no radio services for the 628,000 in
the “outback”.
Of course, you can listen to literally thousands of radio stations from
all around the world, streaming via
the mobile phone network or the internet. The former assumes you have
mobile phone coverage – there are
huge areas of Australia without it – and
which costs you a significant amount
of money.
siliconchip.com.au
Typical streaming radio consumes
up to 60MB per hour, so depending
on your plan, could gobble up your
allowance in very short time.
Alternatively, you can listen to some
radio services (mainly ABC/SBS) in
the home via VAST – Viewer Accessed
Satellite Television – but you cannot
watch TV and listen to radio at the
same time. And this is obviously impractical for mobile (vehicle) listening.
It hasn’t always been this way; until
last January Radio Australia had 50kW
shortwave transmitters in Katherine,
Tennant Creek and Alice Springs and
seven 100kW transmitters in Shepparton, although only three were in use.
Now they are all switched off.
The ABC claims to be using the
money saved from switching off HF
broadcasting (reported to be just $1.9
million a year) to pay for the extension of DAB+ transmitters. But even
if this happens, the turn-off has left
the outback areas without any viable
radio service.
AM, FM and DAB+
All told, there are 540 AM transmitters in Australia radiating from 50W
to 50kW and almost 2,500 FM transmitters in Australia radiating from 1W
to 250kW plus there are 73 standby
transmitters. Each transmitter carries
a single program with some transmitting Radio Data Service (RDS) for the
display of a line of text. Some ABC
transmitters are not fed with stereo
sound, even though they might show a
“stereo on” indication on the receiver.
By contrast, each DAB+ transmitter carries between 15 – 26 programs.
The ABC is transmitting 11 programs
and SBS eight programs. All DAB+
sites have three 50 kW(erp) transmitters except Adelaide and Perth which
have two each. In addition there are
37 on-channel repeaters.
Mobile broadband streaming
through the mobile phone network of
cellular transceivers is being promoted
particularly by AM broadcasters.
But while this may work (at a cost)
in more populated areas, this is not a
solution for remote areas since mobile
phone coverage is sporadic, at best.
Satellite phones are available but
their operating costs are very high
compared to cellular (mobile) phones.
To cover the bush, a huge number of
uneconomic mobile phone transmitters would be required – and unlike
a broadcast radio receiver, the phone
network must track the movement of
September 2017 61
the phone through the network, which
drains the phone battery.
So currently there is no effective
radio coverage for the outback. At the
time of writing, a bill is before the
Senate to force the ABC to resume
shortwave transmissions, but there is
no guarantee of success.
Does AM/FM radio even have
a future?
If you live in the major cities or regional areas, you may not care about
radio in the outback.
But it is possible, even probable, that
we may not always have AM and FM
in our cities – and that might happen
sooner than you may think.
The future may mean DAB+ only in
the cities and not much in the regions.
You might scoff but look at the trends.
Currently there are 3.8 million people able to access DAB+ stations out
of a licence area covering 14.8 million people. There are also 826,000
vehicles which have DAB+ radios,
compared with a total of 10.4 million
vehicles.
In 2016 more than 33% of new passenger vehicle sales were fitted with
DAB+ radios, a huge rise, which will
continue because of the widespread
adoption of DAB+ in Europe. Many of
the AM radio transmitters in Europe
(and even many FM) have been permanently switched off.
Take Norway, for example: by
the end of this year they will have
switched off their remaining FM transmitters, leaving only DAB+ radio.
99.5% of the Norwegian population
have access to DAB+ and 98% of new
vehicles sold there have DAB+ radios
factory fitted (DAB+ adaptors are available for older cars).
Back here in Australia, receivers
for AM radio are becoming harder to
buy. As a result in a trip to a major
chain store, I found only one receiver/
AV system which would receive AM.
Most are either DAB+/FM or FM only.
The same applies to receivers available on line – they’re cheaper to make
because they don’t have AM.
The AM broadcasters can see this
trend even if the listeners are unaware.
DAB+ expansion
Next year, DAB+ broadcasting will
start in the regions, as shown in Table
1. One would expect the largest populations would be the first to receive
their new transmissions. This matches
62 Silicon Chip
Area
Population
Dwellings/
Ch
Power ea
(000s)
Vehicles (000s)
(kWerp)
Gold Coast
570
465
9D, 8B
5#
Newcastle/Lower Hunter
518
417
Sunshine Coast
347
298
Central Coast
328
260
Illawarra
293
216
Geelong
279
238
Canberra/Queanbeyan
253
198
8D, 9C
5
Cairns
240
186
Townsville
229
181
Hobart
222
168
9A, 9C
20
Darwin
137
105
9A, 9C
20
Data sourced from the 2016 Census. # with possibly 3 repeaters
Table 1: planned expansion during 2018 of DAB+ services to major regional
population centres. However, with limited transmitter power, the coverage area
will also be limited.
the multi-broadcaster capability of
DAB+ but also has the smallest coverage area of the options available.
Some regional areas will be restricted to one transmitter to carry
maximum of four commercial broadcasters, two community broadcasters,
ABC local Radio and two high-power
open network broadcasts such as the
TAB, religious and particular language
broadcasts.
With a capacity of nine broadcasters for each transmitter, there will be
unused capacity.
Major areas may have a second
transmitter, which will carry all other
ABC/SBS programs using a single frequency network. This means that the
transmitter and all those geographically adjacent to it must use the same
channel and have identical programs
at the same time. This will cause the
ABC problems near state borders, as
news bulletins are different.
In addition on the NSW/Qld and
Vic/SA borders, the time zone changes
will result in channel 9C being used
on one side of the border and channel
8B on the other.
But this has major drawbacks because the proposed DAB+ transmitters are mostly 5kW – and this would
mean that their coverage is even less
than existing FM transmitters, so that
is not going to extend radio coverage
in regional or outback areas.
DAB+ was initially designed for
Europe, which has 500 million people spread over an area of 10 million
square kilometres compared to Australia with 24 million people spread
over 7.7 million km2.
Currently the planning is to use low
power DAB+ which will produce an
effect like mobile broadband coverage.
Both need for large numbers of low
powered transmitters which produces
an uneven “spotty” coverage.
This is mainly caused by the approximately 200MHz transmission
frequency of DAB+ and the coverage
will be smaller than for the present
FM broadcasts (which transmit around
100MHz).
DRM: the solution for covering
low population density
It’s not something that many people
have even heard about in Australia but
the only real solution is Digital Radio
Mondiale Plus (DRM+).
This is basically long-distance digital radio, designed to cover large areas
at much lower cost than DAB+. Rather
than the eight DAB+ channels, there
are 119 transmission channels available between 56 – 68MHz (the old
analog TV channels 1 and 2).
Because their frequency is around
a quarter of that used for DAB+, these
signals have very much wider coverage
and penetrate buildings better.
A DRM+ channel could carry ABC
local radio at its present 64kbit/s and
the pair of current commercial programs at 48kbit/s each, which is common practice, leaving 26kbit/s for pictures and text.
The transmitter could be located at
the current commercial broadcasters’
FM transmitter site which is close to
their audience.
So how does DRM work? Jim Rowe
SC
explains it opposite . . .
siliconchip.com.au
By JIM ROWE
The Future of
Radio
Broadcasting?
There is no doubt that DRM digital radio would provide the best way of
extending radio broadcasting over the whole of Australia – and further. Here’s
how it works.
D
RM or Digital Radio Mondiale
was developed and is promoted
by the DRM Consortium, an international not-for-profit consortium
which has over 100 member organisations in 39 countries.
Many of the members are broadcasters, but there are also many transmitter
and receiver manufacturers as well as
broadcasting standards bodies.
The aim of the Consortium is to support and spread a digital broadcasting system suitable for use in all of
the frequency bands up to VHF band
III. You can find more about the DRM
Consortium at www.drm.org
By the way, “mondiale” simply
means “world wide” in both French
and Italian.
There are two main variants of
DRM. First there is DRM30, intended
specifically for use on the traditional
low, medium and high-frequency
(shortwave) bands below 30MHz and
on the existing AM broadcasting channels within them. The other variant is
DRM+,which uses frequencies from
47-108MHz – these include the old
analog TV channels 1 and 2 as well
as the FM broadcast band.
They can also carry digital data
services along with the audio signals,
such as station names, time, date and
program information.
DRM30, DRM+ and DAB+
So where does DAB+ fit into this
proposed DRM-based digital radio future? After all, we’ve now had digital
radio broadcasting in Australia for the
last eight years or so using the DAB+
system.
But because DAB+ works in VHF
Band III (174–240MHz), it has a relatively short range and as a result is really only suitable for the larger cities
and their suburbs.
Although DRM30 looks set to become the world standard for digital
radio broadcasting below 30MHz,
DRM+ might well end up competing
with DAB+ in the VHF band.
This is quite possible, because
DRM+ is being promoted as a replacement for analog FM broadcasting in
the 88–108MHz band.
Receivers able to receive both DAB+
and DRM+ – as well as DRM30 , analog
AM and FM – are starting to appear.
But what’s the difference between
DRM and DAB+ anyway? In fact, there
are many technical similarities and not
many differences.
All are digital audio broadcasting
systems which use OFDM – the technique of modulating digital information on an array of closely-spaced RF
subcarriers, instead of a single main
carrier.
This is exactly the same kind of
modulation used in DVB-T television,
wireless LANs (IEEE 802.11a, g and
n) and ADSL broadband over copper
telephone lines.
DRM has now been updated to xHEAAC which is backward-compatible
to HE AAC V2. The xHE AAC can
produce excellent speech quality at
a much lower bit rate. DAB+ is yet to
upgrade. HE AAC is used for sound
in MP4 or MPEG4 video. These compression systems reduce the amount of
data required for transmission so that
it will fit in the channel bandwidth
Vive la différence!
The differences between the two
Fig.1: the main difference between DRM30 and DRM+, apart from frequency, is the
transmission frame length – 400ms for DRM30 vs 100ms for DRM+.
siliconchip.com.au
September 2017 63
systems are rather more subtle.
DAB+ uses 1,536 subcarriers transmitted in parallel, each with a bandwidth of 1kHz and spaced apart by the
same figure. This gives a DAB+ subcarrier channel with a total bandwidth
of 1.537MHz and can convey between
15 and 26 different high quality digital
audio signals as well as their accompanying data.
The program data is assembled into
blocks, labeled and each program is
sent sequentially until all have been
sent and then the sequence is repeated
continuously. The individual signals
are separated again in the receiver.
In contrast with this DAB+ multiplexing system, DRM30 has been designed specifically for use in the ‘AM’
bands below 30MHz.
Since Australian AM radio stations
have an RF bandwidth of 18kHz, this
can also be used. For HF broadcasting
the bandwidth could be 5, 10 or 20kHz
depending on frequency availability.
The greater the bandwidth, the higher
the reliability or better quality.
DRM30, DRM+ and DAB+ can all
transmit stereo sound but HF DRM30
can give continent-wide stereo coverage.
Modes, bandwidth and
QAM options
To achieve the desired level of performance on the bands below 30MHz,
DRM30 broadcasters use four different
encoding ‘modes’ designated A, B, C
and D, while DRM+ broadcasters use
a fifth encoding mode designated (you
guessed it!) E.
Each of these modes is designed to
achieve the best performance in a different broadcasting application, as you
can see in Table 1.
You’ll also note from this table that
the main service channel or MSC (ie,
the digital audio channel itself) of both
DRM30 and DRM+ signals is generally
The idea behind this is that 64-QAM
can encode 64 points in its amplitude/
phase or “I/Q constellation”, allowing the subcarriers to carry five bits
of information in each digital sample
or ‘symbol’ – and hence a higher total bit rate.
However, the 64 points in a 64QAM constellation are inevitably
closer together in both amplitude and
This GR-216
DRM30
receiver has
been evaluated
by Tecsun Radios
(Aust) and they have confirmed
that it receives DRM transmissions from
New Zealand in Australia. This receiver also handles AM and FM reception.
modulated onto the RF subcarriers using the quadrature amplitude modulation (QAM) system. DRM30 broadcasters have the option of choosing either
64-QAM or 16-QAM coding, while
DRM+ broadcasters can use either 16QAM or 4-QAM.
phase, making it more susceptible to
data corruption, due to noise and interference.
In contrast, 16-QAM has only 16
points in its amplitude/phase constellation, so the individual points are further apart – making it more suitable for
noisy conditions, even though it can
encode only 4 bits of information in
each digital symbol (and hence a lower
overall bit rate).
The 4-QAM option available for
DRM+ takes this trade-off even further, allowing it to encode only two
bits per digital symbol and hence a
lower overall bit rate again. But that’s
not really too much of a problem
when DRM+ signals are encoded into
a 100kHz wide channel, as you can
see from Fig.1.
DRM’s three data channels
Table 1: the choice of frequencies, modes and coding options depends to a large
extent on the coverage distance desired.
64 Silicon Chip
The next thing to understand about
DRM is that each DRM broadcasting
signal consists of three basic data
channels.
There’s the Main Service Channel
(MSC), which generally carries the encoded digital audio data; then there’s
the Fast Access Channel (FAC), which
carries a set of data parameters allowing
siliconchip.com.au
Table 2: Australia is significantly lagging behind when it comes to DRM broadcasts
– this table shows Radio New Zealand’s DRM schedule to the South Pacific.
the receiving decoder to quickly confirm things like the modulation system
being used in the DRM signals.
Finally there’s the Service Description Channel (SDC), which carries
advance information like audio and
data coding parameters, program service labels, the current time and date,
and so on.
Fig.1 should give you a basic idea
of the way these three data channels
are grouped into the data stream transmitted in DRM30 and DRM+ digital
broadcasting.
The DRM30 modes group the data
into 1200ms-long “super frames” consisting of three frames 400ms long,
while DRM+ groups the data into
400ms-long super frames each consisting of four frames 100ms long.
In both cases the SDC data is transmitted across all subcarriers for a pe-
riod of two symbols at the start of each
super frame.
For the rest of each super frame, the
FAC data is transmitted using a specific
sub-group of subcarriers during each
transmission frame, while the coded
audio data in the MSC channel is
transmitted using all of the remaining
subcarriers, in parallel with the FAC
data for all of rest of the super frame.
DRM status world wide
While we haven’t heard much about
DRM as yet in Australia, it’s now well
established in the UK, many of the European countries, Canada, India and
Russia – plus in New Zealand.
Radio Australia did transmit DRM30
on shortwave to Papua New Guinea
from Brandon (Qld) but that ended in
March 2015.
Radio New Zealand International
This “Avion” AV-DR-1401DRM Digital Radio sells on Amazon in India for about
AU$330. Touted as India’s first DRM, it will also receive AM and FM broadcasts.
siliconchip.com.au
broadcasts DRM30 on shortwave for
about 20 hours per day, mainly to the
Pacific Islands.
Receivers capable of receiving
DRM30 are still in fairly short supply in Australia, and a lot of the DRM
reception to date seems to have been
using PC-based SDRs (software defined radios) – see our articles in the
November 2013 issue of SILICON CHIP
(www.siliconchip.com.au/Article/
5456 and www.siliconchip.com.au/
Article/5459).
However some of the European manufacturers like Morphy Richards have
been producing DRM30 receivers, and
Indian firm Avion Electronics (India)
lauched its AV-DR-1401 radio recently.
Chinese firm Gospell Digital Technology has also announced its GR-216
DRM receiver.
Other DRM receivers you’ll find on
the web are the Himalaya DRM2009,
the Technisat Multiradio and the Uniwave Di-Wave 100.
Why DRM30 for Australia?
DRM30 digital broadcasting is particularly suitable for Australia, because of its much larger range. For example a DRM30 broadcast transmitter
operating in the ‘AM’ band will have
a range virtually identical to that of
our existing analog AM broadcasters.
And a 250kW HF DRM30 transmitter
located in the geographical centre of
Australia (Kulgera, NT) could cover
just about all of the continent and surrounding waters.
A much lower power DRM30 transmitter located in the geographical centre of Tasmania (Liena) could similarly
cover the whole of that state.
So adopting DRM30 would be the
best way to ensure that ALL Australians received good broadcast radio
reception – even those living in or
moving through remote areas.
And this brings up another point:
DRM30 operating at HF provides much
better reception in moving vehicles
than either FM or DAB+ – which operate in the VHF spectrum.
Best of all, though, is that existing
AM and shortwave transmitters could
in most cases be converted for DRM30
broadcasting at very low cost.
The question really is this: why is
Australia dragging its heels and letting just about all the rest of the world
move into the digital radio future with
DRM30 – when we could join them
with very little outlay?
SC
September 2017 65
Dead-easy Superhet
IF Alignment using
Direct Digital Synthesis
• Touch-screen convenience
• Really quick and easy IF alignment!
This project is based on the
touch-screen Micromite DDS
Signal Generator project and makes aligning the IF stage
of superhet sets a snap, whether they are valve or transistor-based.
It also lets you examine the IF stage bandwidth, which gives a good
indication of the set’s selectivity, as well as the shape of the IF curve.
I
n the simplest terms, a superheterodyne AM radio works by mixing (ie, heterodyning) the radio
station signal with a tracking oscillator
signal that has a fixed frequency offset above (ie, super) that of the tuned
station.
The output of the mixer includes
components at the sum and difference
frequencies of the two input signals.
The following stages reject all but the
difference frequency and this carries
the same audio (amplitude) modulation as the incoming signal from the
radio station.
The difference frequency is known
as the Intermediate Frequency (IF)
and the IF circuitry normally comprises two stages with tuned resonant
circuits, each involving a transformer
with adjustable cores (slugs).
In more detail, the primary and secondary windings of each transformer
have parallel capacitors and their
cores need to be adjusted so that their
resonant frequency matches the IF, eg,
455kHz or 450kHz.
66 Silicon Chip
Adjusting the transformers in this
way maximises the gain of the radio
and the whole process is referred to
as IF alignment. IF alignment also
optimises the Q of each stage and this
increases the rejection of unwanted
signals (outside the tuned circuit’s
resonant range).
This has the effect of increasing the
selectivity of the radio which means
that it is easier to tune when stations
are crowded together on the dial.
Normal alignment also involves adjusting the antenna input circuits so
that stations at the top and bottom of
the dial (ie, the full timing range) are
actually received at the marked points
(ie, the station call sign or the transmitter frequency on the dial).
Note that some sets with a wide audio bandwidth (say 10kHz or more)
may have the IF transformer cores adjusted to slightly different frequencies,
say 447kHz and 463kHz, in the case of
by Nicholas Vinen
a 455kHz IF. This “staggered tuning”
gives a wider audio bandwidth but
slightly lower gain.
For more information on how a
superhet set works, see the AM Radio
Trainer project in the June 1993 issue;
it’s available as a PDF download from
our online shop at www.siliconchip.
com.au/Shop/5/3435
We also published a detailed description of the operation of the IF
stage in the December 2002 issue; see
www.siliconchip.com.au/Article/
6698
Aligning the IF stages
There are a number of methods by
which you can do alignment on an
AM radio but the simplest approach
involves injecting a signal into the set
which can be set to the intermediate
frequency.
If this signal is modulated (typically at 400Hz), you can easily judge
the effect of your adjustments by the
loudness of the tone in the radio’s
loudspeaker. That means you need a
siliconchip.com.au
It’s all housed in a small Jiffy Box . . . and if
you’re into restoring vintage radios, for example, you’ll
find this the best thing you’ve ever seen since sliced bread!
modulated RF oscillator which can be
set to precisely 450 or 455kHz.
It is also desirable that its output
is a clean sinewave, ie, with few harmonics to cause problems in the alignment results.
Unfortunately, the output waveform
of most old valve and transistor RF
oscillators is surprisingly distorted
and their output amplitude can also
vary significantly as the frequency is
changed.
But there is a much easier and more
elegant way and here is where modern
technology comes to the rescue.
Sweep oscillator
What we would really like is to plot
of the set’s detector output against the
injected frequency so we can actually see what the IF stage frequency
response looks like.
That’s just what this project does.
It produces a signal which is swept
over a range of frequencies around the
nominal IF and it measures the output
of the voltage detector (usually a diode
just preceding the volume control).
The varying DC output can then be
SWEEP
OSCILLATOR
plotted on an LCD screen.
You can set the centre frequency and
span and it automatically scales the
vertical axis and adds cursors showing the peak frequency and (if visible)
-3dB points.
That makes doing the IF alignment,
and even setting the IF bandwidth,
easy!
But we are getting ahead of ourselves. Fig.1 shows the concept. The
sweep oscillator can be thought of as
an oscillator which can be set to vary
in a linear fashion from say, 440kHz
to 470kHz, repeatedly.
This signal is connected to the input of the IF stages and the output of
the detector is connected to an oscilloscope.
But we have combined the sweep
oscillator and the oscilloscope screen
into the one unit.
For the sweep oscillator, we’re using a Direct Digital Synthesis (DDS)
module based on the Analog Devices
AD9833 IC.
Then we’re using the Micromite
LCD BackPack to provide the oscilloscope function, to display the result.
AM RADIO
Because the Micromite is controlling the DDS, it can synchronise the
plotted result on the screen with the
frequency of the sweep oscillator.
The hardware used in this project is
pretty much the same as that in the Micromite BackPack Touchscreen DDS
Signal Generator that was published
in the April 2017 issue.
The main changes are to the software, to provide the sweep and plotting function. There’s just a slight
change hardware, to provide the required analog voltage measurements.
Circuit operation
The circuit diagram for the DDS IF
Alignment unit is shown in Fig.2. Most
of the work is done by the Micromite
software running on the BackPack and
the arbitrary waveform generator module which contains the AD9833 IC.
If you compare this diagram to the
one from the Touchscreen DDS Function Generator in the April issue (on
page 70), you will see a few minor
changes.
Firstly, we have changed the coupling capacitors from the PGA (pro-
DETECTOR
OUTPUT
IF
Fig.1: an overview of how this unit can be used to plot the frequency response of the IF stage in a radio. A sinewave
signal is produced which sweeps from just below the intermediate frequency to just above and this is injected into the
set via its antenna. The detector voltage is then plotted against the sweep frequency on an LCD screen to produce a
frequency response plot. Note that the sweep oscillator’s output is not amplitude modulated.
siliconchip.com.au
September 2017 67
Fig.2: circuit diagram for the DDS IF Alignment
unit. It consists primarily of the Micromite LCD
BackPack at left, wired to an AD9833-based DDS
module at centre. The DDS module produces
the sweep signal at the output connector and the
resulting DC detector voltage is applied to the input
connector and then fed back to the Micromite, to be
measured and plotted on the touchscreen.
grammable gain amplifier) output of
the DDS module to the output connectors to a single 10nF 630V type,
primarily to provide protection for the
DDS module from accidental connections to HT voltages in valve radios.
We have also added a 10kΩ resistor
in series, to limit inrush current in the
case of a short circuit.
This offers the possibility of inject-
ing the signal into HT-biased parts of
the circuit but as we will see later, that
is generally not necessary.
We’ve omitted the attenuated output terminal since you can adjust the
sinewave amplitude output of the DDS
via the touchscreen and you can also
control the amount of signal coupling
into the radio antenna by how closely
you place the leads (more on that later).
Fig.3: the modified main screen from Geoff Graham’s DDS
Signal Generator. Note the new “IF Align” button at centre
left. You can still use the unit as a signal generator, with all
the same functions of the original unit. We simply added
the extra functions required for IF alignment, accessed via
this new button.
68 Silicon Chip
We haven’t bothered with any DC
biasing of the output since that will
generally be accomplished in the set
if you are using direct signal injection.
In place of the trigger output used in
the original DDS Generator project, we
have an analog input that’s intended to
monitor the DC output of the detector
or AGC (automatic gain control) signal.
This gives the unit direct feed-
Fig.4: we hooked our test unit up to an HMV 64-52 “Little
Nipper” valve superhet and this is the result. The plot
shows that the IF stage needs some re-alignment as its peak
response is not at 455kHz. Note the cursors indicating the
peak and (approximate) -3dB points. The output lead was
simply placed near the ferrite rod antenna while the output
of the detector was taken from the top of volume control
pot VR1 (which doubles as the AGC signal, fed to R4).
siliconchip.com.au
back on the amount of signal passing
through the IF stage. This goes back
to pin 24 on the BackPack since this
is an analog input.
It’s protected from accidental high
voltage application via a 4.7MΩ series
resistor and this also forms a divider
with the 1MΩ resistor to pin 22, if pin
22 is actively driven.
If pin 22 is left floating by the software, it has little effect on the voltage
at pin 24.
For radios which have a negative
AGC/detector output (the majority),
pin 22 is driven high, to +3.3V. This allows pin 24 to measure voltages down
to -15.5V (3.3V x -1 x [4.7MΩ ÷ 1MΩ]).
To measure positive voltages, pin 22
can be left floating for high sensitivity
(0-3.3V) or driven low for low sensitivity (0-18.8V) measurements. This is
all under the control of the software.
We won’t go into a great deal of detail on the operation of the AD9833
DDS module.
This was covered in a dedicated article in the April 2017 issue, starting
on page 18 (see www.siliconchip.com.
au/Article/10608).
It was also explained in the article
on the DDS Signal Generator in the
same issue.
In brief, software running on the
LCD BackPack sends commands to the
DDS module over a three-wire SPI (serial peripheral interface) bus comprising pins SCLK (clock), SDATA (data)
and FSY (module select).
The same SPI bus is used to communicate with a digital attenuator in the
same module, except that the CS (chip
select) line is pulled low when communicating with it, rather than FSY.
By sending serial commands to the
AD9833, the PIC32 in the BackPack
can set the output waveform type (sine,
triangle, square), the frequency (from
0.1Hz to 12.5MHz), the phase and it
can also put the AD9833 IC into lowpower sleep mode, or wake it up.
By sending commands to the digital attenuator, the output level can be
changed in 255 steps, over a range of
about 4mV to 1V RMS.
Software operation
The software for this project is based
directly on the software for the DDS
Signal Generator from April 2017 and
retains all the original features of that
project.
We’ve simply added an “IF Align”
button to the main screen (see Fig.3).
siliconchip.com.au
Parts list – DDS IF Alignment
1 2.8-inch Micromite LCD BackPack kit with microcontroller programmed for
DDS IF Alignment (DDSIFAlign.HEX), laser-cut lid and mounting hardware
(SILICON CHIP online shop Cat SC4021)
1 DDS Function Generator module with AD9833, AD8051 and MCP41010 ICs
(SILICON CHIP online shop Cat SC4205)
1 UB3 plastic Jiffy Box
4 M3 x 10mm Nylon machine screws
12 M3 Nylon hex nuts
11 short single pin female-female DuPoint jumper leads
(Jaycar WC6026; set of 40)
1 USB charger with USB-to-DC-plug cable (see Fig.7)
1 chassis-mount DC barrel socket, to suit cable
2 chassis-mount BNC sockets
1 10nF 630V polyester capacitor
1 4.7MΩ 1W resistor
1 1MΩ 0.25W resistor
1 10kΩ 1W resistor
Once you’ve set up the generator to
produce a sinewave at the expected intermediate frequency, press this button
and the unit will go into sweep mode.
By default, it will sweep from 10kHz
below the current centre frequency
to 10kHz above (ie, a span of 20kHz).
Each sweep takes a couple of seconds.
To do a sweep, the unit first sets the
DDS output frequency to the lower
end of the sweep range, then after a
short delay, measures the voltage at
the detector input. It then increases
the output frequency by 1/80th of the
span and measures the detector input
voltage again.
Once it has at least two measurements, it updates the display with a
short line segment, forming that portion of the IF curve plot.
This process is repeated until the
frequency is at the top of the span (ie,
after 80 steps) and the curve plot is
complete.
The unit then repeats this process
forever, so that the plot is constantly
being updated.
Each time a sweep is completed, it
analyses the data and finds the maximum value, then draws a cursor,
which includes text that shows the
peak frequency and voltage reading,
plus a vertical line down to that part
of the curve.
It then looks for the -3dB points on
either side of this peak and if found,
draws cursors for them too, including
the frequency readings.
The mode buttons that are normally
at the bottom of the screen in the DDS
Signal Generator are still present in
sweep mode, so pressing any of these
will take you out of sweep mode and
back into one of the normal signal generator modes.
Other areas of the screen can be
touched to change the sweep parameters.
You can press on the centre frequency, at the bottom of the plot, to change
it (a keyboard will appear). Similarly,
touching either the lowest or highest
sweep frequency in the bottom corners
will let you set the frequency span.
If you press on one of the cursors at
the top of the screen, you will change
the cursor update interval.
Normally they are updated each
time a sweep is completed but you
can set them to change on every second or fourth sweep, to give you more
time to read them off, by pressing on
the cursors.
The first number in the top-right
hand corner of the plot (before the
comma) indicates the current cursor
sweep update interval.
The second of these two numbers
indicates the detector voltage input
mode. The default mode is “1” which
inverts the voltage measured and gives
a maximum input reading of around
-16V.
In this mode, the pin 22 output is
driven high, in order to shift negative
input voltages up into the range of
0-3.3V, so the micro can measure them.
Pressing on the middle of the screen
will change this mode to “2”, which
sets the pin 22 output low.
Thus, the unit measures positive
voltages, from 0V up to around +19V.
Pressing again will change the mode to
“0”, which causes pin 22 to float and so
September 2017 69
Here’s how it all fits inside
a UB3 Jiffy Box, albeit
with a new laser-cut
acrylic front panel. The
10kΩ 1W resistor attached
to the upper BNC socket
appears to go to nowhere
in this photo; in fact it
is soldered to the 10nF
capacitor immediately
below it. Similarly the
orange cable connecting
to the BackPack solders
direct to the end of the
4.7MΩ 1W resistor. Note
also the small piece of
strip board attached to
the MicroMite BackPack
PCB – we used this to
more firmly anchor the
1MΩ 1W resistor which
connects between pins 22
and 24 of the BackPack.
Incidentally, 1W resistors
were chosen not for their
power dissipation but
instead for their voltage
ratings, assuming the DDS
module will be used with
the higher voltages of
valve radios.
the input voltage measurement range
is 0-3.3V. Another press will take you
back to mode 1.
The input impedance is around
5MΩ, regardless of mode.
Note that current does flow into pin
24 when making analog measurements
and the high source impedance of
4.7MΩ, due to the series resistor, will
cause errors in the readings.
But the whole measurement process
is quite approximate, due to various
factors such as AGC operation, imperfect coupling of the test signal into
the set, non-linearity in the detector,
background noise being picked up by
the set’s antenna (unless it is disconnected), etc.
In general, the measurements are
close enough to get a pretty good plot
of the IF stage’s response and make
any necessary adjustments.
online shop.
You can use the plain BackPack kit (www.siliconchip.com.au/
Shop/20/3321) and load the BASIC
code for the DDS IF Alignment yourself, using a USB/serial adaptor and
the free MMEdit software.
Or for the same price, you can pur-
chase a kit with the software pre-loaded on the microcontroller from www.
siliconchip.com.au/Shop/20/4021
Both kits are supplied with a lasercut lid to replace the UB3 jiffy box lid,
with the required cut-out and holes
already drilled. The kits also come
with the hardware needed to attach
Construction
The majority of the assembly required for this project is to build the
LCD BackPack module. This is available as a kit from the SILICON CHIP
70 Silicon Chip
Fig.5: this diagram shows how the LCD BackPack is attached to the
underside of the 3mm laser cut lid, while the DDS module is mounted in
the bottom of the jiffy box.
siliconchip.com.au
103K
630V
Fig.6: follow this diagram to make the connections between the LCD
BackPack, DDS module and input/output sockets. The components
between the PGA output on the DDS module and the output connector
can be made as shown here while you may prefer to mount the other
two components on a small piece of prototyping board, as we did for
our prototype.
the module to the lid.
Assembly is quite straightforward,
simply fit all the parts where indicated
on the PCB silkscreen label.
For full details, see the February
2016 article describing the BackPack
(www.siliconchip.com.au/Article/
9812) but most constructors won’t
have any trouble figuring it out.
Make sure the 28-pin socket goes in
with its notch in the position shown
and when you plug the micro into its
socket, its pin 1 dot needs to go near
the notch.
The female header for the LCD and
6-pin right-angle in-circuit serial programming (ICSP) header both go on
the same side as the micro and related
components, while the two vertical
male pin headers for the input/output
connections are soldered on the back.
Regarding the three 10µF/47µF capacitors, note that they were shown
as through-hole tantalum types in the
February 2016 article, and you can use
these, but we prefer to use SMD ceramics as they are more reliable and this
is what is supplied in the kit.
The ceramic capacitors are not polarised and the PCB has pads to suit
either type.
The kit is normally supplied with
two SMD capacitors in one pack and
one in another; the one by itself is the
47µF type.
However, it doesn’t actually matter
where you solder them since we only
specified 47µF for VCAP in case tantalum capacitors are used.
When ceramic capacitors are used,
10µF is sufficient for all three. This
has been a point of confusion for some
constructors who have ordered kits.
Once the module is complete, power
it up to make sure it works and then
attach it to the underside of the lid
with the supplied 1mm thick Nylon
washers as spacers.
The touchscreen is held onto the
main board by screws which pass
through the lid, these spacers, the
LCD module and then into the spacers
mounted on the main board. The overall arrangement is shown in Fig.5.
Final assembly
The next job is to place the DDS
module in the bottom of the case and
mark and drill mounting four 3mm
holes, then attach it to the inside of
the case using Nylon machine screws
and nuts, as shown in Fig.5.
This module should be mounted to-
wards the right-hand end of the case,
around 60mm from the end, with the
output connector to the right.
The only other holes you need to
drill are two in the right side of the
case for the BNC sockets (10mm) and
one in the left side for the DC power
socket (8mm).
You can then mount those sockets
and solder the extra components as
shown in the wiring diagram, Fig.6.
The easiest way to do this is to trim
the leads of the 10kΩ resistor short
and solder one to the central pin of
the output socket.
One end of the 630V capacitor can
be soldered to the PGA output of the
AD9833 module before that module
is installed in the case, then trim the
remaining lead and solder it to the free
end of the 10kΩ resistor.
The 4.7MΩ resistor can also be soldered directly to the centre pin of the
input socket and then a short wire
run back to pin 24 on the BackPack
I/O header.
We made up a little plug-in board
out of a piece of prototyping board,
with the 1MΩ resistor onboard and a
header for this wire to plug into so that
we could easily remove it later if we
Fig.7: this power supply cable is made from a USB cable cut short, with a DC plug soldered onto the end. It plugs into a
USB charger, which is a cheap and readily available source of regulated 5V. The unit can also be run from a USB power
bank or the USB port of a computer. The wires inside the USB cable should be colour coded; solder the red wire to the
inner conductor, the black wire to the outer barrel and cut short and insulate the white and green (USB signal) wires.
siliconchip.com.au
September 2017 71
There’s the old way, using a 455kHz generator and
a ’scope to monitor the waveform (and lots of time!)
. . . and the new way, using the touch-screen DDS to
perform the alignment much more easily. Note that
while the oscilloscope’s vertical scale is showing
peak voltage, the display on the DDS Alignment Unit
has a logarithmic vertical scale (ie, it reads in dB) so
the shape of the curve is different. However, they are
effectively displaying the same thing.
needed to. You could solder the 1MΩ
resistor directly between the pins to
save time.
With the four extra components in
place, all that’s left to do is wire up the
various connections using the jumper
leads, as shown in Fig.6, plus the two
wires to the DC socket.
Where you need to go from a header
pin to a soldered connection, you can
simply cut the DuPont socket off one
end of the wire, strip it back and then
solder it in place.
The other end can then just be
plugged in; see the internal photo for
more details.
Now double-check that you have
wired up the DC socket with the correct polarity before powering the
unit up because there’s no protection
against reverse polarity!
The easiest way to do this is to unplug the +5V connection from
the BackPack board (check the
silkscreen labelling to see which
one this is) while leaving the earth
connection attached.
Apply power, then measure between the disconnected pin and the
outer shield of one of the BNC sockets with your DMM, with the black
lead to the BNC socket shields.
If you get a positive reading on the
DMM, close to +5V, plug the cable back
in and the unit should spring into life.
72 Silicon Chip
Once you’ve verified that it’s all
working, you can attach the lasercut lid to the case with the supplied
self-tapping screws and the unit is
complete.
Note that as the lid is slightly thicker
than the one originally supplied with
the case, and doesn’t have recesses
for the screw heads, it’s possible you
may need to substitute longer screws;
we find the ones supplied with UB3
boxes from Jaycar are just long enough.
That’s it, you are ready to start alignSC
ing radios.
Reprinted from the April 2017
feature on the AD9833 module
(siliconchip.com.au/Article/10608)
this shows the circuit of the AD9833-based DDS module
used in this project, The output is taken from the socket
labelled PGA and AGND (lower right).
siliconchip.com.au
SERVICEMAN'S LOG
When a GPS loses its way
GPS satnav systems are widely used in cars,
boats and for personal navigation when
walking in country but it is safe to say that most
of these would be discarded when they stop
working. That is probably the most practical
approach but what if you were using GPS
tracking collars which are fitted to wildlife?
These are much more expensive units that are
quite costly to replace if they fail.
I am certainly getting a variety of
work these days and I can no longer
complain about doing the same “boring” sorts of repairs. I get all sorts of
jobs and I wonder if it is because the
servicing game has changed so much
here in New Zealand. So many repair
business have closed or maybe just
given up. . .
I’ll bet a lot of service businesses
here looked at the silver lining when
the quakes struck Christchurch, with
many taking the seemingly God-given
opportunity to close with dignity.
There are few other explanations as
to why so many of these businesses
never re-opened. Some of us have kept
going though...
siliconchip.com.au
73 S
ilicon Chip
A client from “down south” recently
visited Christchurch and found me
working on my new workshop. He’d
heard that I fixed GPS units and asked
if I was interested in looking at his. I
told him that I’d repaired a few in the
past few years as word got around that
despite many industry claims, they
might actually be fixable.
This guy was a typical kiwi “southerner” and I say that with a lot of respect. I mean that he is one of those
characters that spends much of his life
in the far south of the country, where
bush is thick, the terrain harsh and the
weather beyond inclement. There are
still uncharted areas down there, and
this is my client’s backyard.
Dave Thompson*
Items Covered This Month
•
•
•
•
Garmin GPS animal trackers
Cambridge CD player repair
Fixing a useless machine
A Pony 3 mobility scooter that
just wouldn’t scoot
*Dave Thompson runs PC Anytime
in Christchurch, NZ.
Website: www.pcanytime.co.nz
Email: dave<at>pcanytime.co.nz
Having the GPS working properly
could be the difference between coming home safe or spending a night (or
longer) out in the boonies, so they are
an important piece of kit.
What he wanted me to check over
was a Garmin hand-held GPS unit and
three Garmin Alpha T5 tracking collars, the sort you might fit to a lion or
a bear in order to keep tabs on their
whereabouts. They are certainly not
the dainty “domestic” types sold by
the likes of AliExpress for pet owners
to monitor Snuggles’ nocturnal antics.
My client uses these collars, together
with the hand-held GPS, to monitor
animals in the wild and gather information about their movements so that
SSeptember
eptember2017 73
2017 73
Serr v ice
Se
ceman’s
man’s Log – continued
programs can be devised to ensure
their continued survival.
The collars are made using heavyduty synthetics, hard rubber and some
metal parts for the clasp arrangement,
all of which have to be robust enough
to withstand natural hazards and the
animal’s efforts to rid itself of the annoyance.
Apparently, all of these collars had
failed with the same symptoms; they
no longer acquired satellites and were
thus useless for tracking.
Due to the cost of replacement, the
guy thought he’d ask around to see
if anyone fixed them and for some
reason, my name popped up. However, there was a snag (isn’t there
always?). Garmin made these collars
to withstand the rigours of extreme
conditions; to that end, they are built
like the proverbial masonry ablutions
block.
The external connections are wellsealed with some formerly-liquid armour and the GPS module – which is
housed a separate small plastic “box”
along the collar from the main electronics case and connected by a shielded cable – is completely enclosed in
a case with clear potting compound
and thus completely isolated from the
environment – and potential
repairmen.
74 Silicon Chip
The main box of electronics goodies is three times the size of the GPS
module and is home to the battery,
charging ports and a small, doublesided PCB stuffed with surface-mounted components and edged with tiny,
multi-colour LEDs that indicate what’s
happening with the unit.
At least this board is accessible
after removing half a dozen long, finethreaded screws and prying the lid
away from the seal that (supposedly)
keeps the contents safe and dry.
The guy mentioned that he, and others with the same issue, thought the
problem was the shielded cable from
the GPS module and commented that
it was often under some strain, so they
thought all it needed was re-terminating into the main module. Or at least
that’s what YouTubers and posters in
online forums reckoned.
Just by looking at it, I doubted this
was the issue. The cable was embedded in the plastic collar and appeared
well-connected, with all the strain relief necessary. And given that it really
didn’t flex or move that much when
the collar was worn, I found it difficult
to accept that this was the problem.
We’d see though; I’ve been known to
be wrong before.
The first thing I did was try the collars out. Two of them had flat
batteries since they’d been
sitting on the shelf for
ages after failing and so
they were non-starters.
The third one gave a
healthy series of beeps
on button-push and the
middle of three LEDs
flashed solemnly every
few seconds.
This informs the user
when enough satellites are acquired for accurate operation; one flash
is no satellites;
two flashes indicates two satellites and three
flashes indicates
at least three satellites are acquired
and this will provide
the most accurate positioning.
The problem with this collar was
that it wasn’t acquiring any satellites
at all; the LED only blinked once every
few seconds.
My initial thought was that perhaps
the guys were right in thinking that the
GPS module’s lead had come adrift. It
would certainly explain the lack of satellite acquisition. This would be well
worth checking out anyway, if not to
confirm the diagnosis, then at least to
rule it out.
I decided to start with the one that
powered up; I could use that battery to
check the others as the client neglected
to bring the specialised charging dock
for the collars. Once I had the battery
out I could use my bench supply to
top it up if necessary.
I started by removing the six screws
holding the main module together.
Two of those screws hold a smaller,
separate cover and another, smaller
machine screw and two tiny PK-type
screws beneath that held the GPS
module’s connection harness to the
main module.
With those smaller screws removed,
the end of the collar and the embedded
GPS module’s shielded cable could be
pulled away from the main module.
But not very far; the portal where the
shielded cable enters the main module is heavily potted and the material
is somewhat elastic, but very tough.
The VHF antenna, which is about
350mm long and follows the contour
of the collar due to it feeding through
various holders, is basically a chunk
of heavy gauge, multi-strand steel cable with a basic crimp terminal at the
module end and a red, plastic antenna
tip at the other. This connects to the
main module via a relatively large machine screw but this isn’t potted in and
is easily removed.
With all the screws and bits removed, I used a small flathead screwdriver to gently pry the metal frame
out of the main module’s thick plastic
body. It fits very tightly and aside from
a few animal hairs and some dried
mud, it came out cleanly, revealing two
plugs from the board; one to the battery
and one to the charge port, which were
screwed and moulded into the main
plastic housing respectively.
Once unplugged, the PCB came
away with the metal base, and I could
see the PCB was attached to the base
with a few more of those tiny PK
screws and stuck with potting compound in several places.
siliconchip.com.au
The first thing I noticed was a lot of
grub between the VHF antenna terminal and its connector into the module.
As I said, that end of the antenna is not
potted in and only has an unsealed,
thin plastic cover over it in the wild,
allowing moisture and other debris to
work its way in.
I cleaned the terminal with some
isopropyl alcohol on a rag and used
my 30-year-old contact-cleaning diamond file to clean the face that contacted with the one in the module.
The module side of things was a little
dirty but looks to be nicely polished or
even chromed steel, so I didn’t file that.
Instead, I used my fibre-glass-bristled
PCB cleaning brush to spruce it up.
Looking further onto the PCB, I
could see that moisture had gotten
into this one. There is a rubber O-ring
type seal between the metal base and
the plastic body of the main module
and it looked to be intact, so I’m not
sure how the moisture got in, but it had
started to corrode some of the solder
joints on the board.
Once again, I used my PCB brush to
clean the board and with a very fine tip
in my soldering iron, I went through
and tidied up every dodgy-looking
connection on the board before setting that aside and checking out the
GPS module.
The GPS module had a plastic bottom, which was held on with four
small screws. Once removed, the base
came away easily, revealing a completely potted PCB board taking up
the whole interior space. The connecting cable exited via a purpose-made
channel in the collar and entered the
potting material, which was clear, so I
could see the cable gently curl around
and end up soldered to the PCB.
This cable was also heavily potted in at the main-module end, so it
wasn’t easily accessible for ringing out.
It needed to be tested for continuity
though, if only to prove or disprove the
client’s theory that it was the problem.
The easiest way to do this was to
drill a small hole through the potting
material down to the joints on the
PCB. I used a standard 1.5mm “jobber” drill to start with, drilling slowly
down by hand with a pin chuck until
I was nearly to the joint, a distance of
about 5 or 6mm.
I finished off with the same-sized
drill, but with the bevels ground off,
making it flat-bottomed. This I twisted
in until it just touched the soldered
siliconchip.com.au
joint. Luckily, the refracted light didn’t
throw me off the mark, as it certainly
looked odd from certain angles as the
drill went in.
I then used my dentists’ pick to clear
the way for one of my multimeter leads
and after touching one lead on that,
went to the main module’s board and
used the other lead to “ring” out the
shielded cable.
Although the main board end was
also potted over, I could touch various parts of the board and get readings, and on the grounded side, could
make a one-to-one contact with earth
points on the main board, even when
twisting and manipulating the cable
at either end, so that confirmed to me
that this cable was not the problem
with this collar.
I refilled the holes I’d drilled in
the potting compound with 5-minute epoxy and though probably not
as tough or hard as the original, for
filling a 1.5mm x 6mm hole it was
sufficient for air and moisture protection.
I assembled the VHF antenna and
plugged in the battery – which by this
time I’d removed from the housing –
pushed the ON button and took the
whole caboodle outside and sat it on
the rag top of my car. Within about 30
seconds, it was double-flashing and by
one minute, was flashing three times,
indicating that at least three satellites
had been acquired.
When I fired up the handset and
selected one of the dogs listed, two
didn’t show any data, though the third
indicated a stationary distance of two
metres, and when I moved the collar
to the end of the driveway, twenty metres. That was good enough for me, so
I reassembled everything bar joining
the main housing and metal base together; I’d need the battery for testing
the others.
The second collar was pretty much
a replay of the first; cleaning up all the
connections resulted in another working collar. The client was well pleased,
and at this stage mentioned there was
a YouTube video of a guy fixing one
of these collars with the same symptoms as ours. I had a look, and that
guy simply replaced the GPS module
with a new part, which was overkill
in my opinion.
The third collar defeated my attempts at basic repair and I think the
GPS module has really gone in that
one. I’m currently stripping the potting
compound out of it. After all, I’ve nothing to lose by doing that and I think I
can pick up a suitable module for a lot
less than the YouTube guy paid. We’ll
have to see.
Repair to Cambridge Audio
640C CD player
D. R., is a tinkerer living in a small
country town, who sometimes gets
asked to look at various non-operational devices...
A friend recently asked me to look
at her CD player. I have had a few CD
players requiring a lens clean, but as
the front panel showed that it was reading the info off the disc, that wasn’t the
case here. There was a signal at the
digital output socket, but nothing at
the analog audio output sockets.
I found a circuit diagrams on the
web which showed that there was a
relay which could mute the output.
There was no “mute” button on the
unit or the remote control so it wasn’t
going to be that easy.
The relay was a 5V DC coil unit
and checking around, I found a mute
connection (CN4) on the board near
the relay. This had either five or zero
volts on it depending on whether play
or pause/stop was pressed. I (stupidly)
jumped to the conclusion that the relay
coil must be open. I ordered a suitable
replacement, but of course replacing
the relay made no difference.
Searching around on the board, I
noticed that four capacitors appeared
to have leaked brown gunge onto the
board. I could only get higher voltage
rated versions so one of them had to
be fitted horizontally on long leads. I
half-hoped this might make a difference to the voltages, but the relay was
still not operating.
Servicing Stories Wanted
Do you have any good servicing stories that you would like to share in The Serviceman
column? If so, why not send those stories in to us?
We pay for all contributions published but please note that your material must
be original. Send your contribution by email to: editor<at>siliconchip.com.au
Please be sure to include your full name and address details.
September 2017 75
Partial circuit diagram for the Cambridge Audio 640C CD player showing the
output mute control, as described in the text.
The diagram showed a circuit with
four transistors associated with the
mute relay. I tested these and they all
appeared OK.
To try and work out what was going on, I soldered a few flying leads
around these transistors so that I
could monitor voltages while the unit
was operating. I realised (a bit late)
that the mute 5V signal was present
when the relay should be off and zero
when it should be on.
This meant that the circuit must invert the mute voltage. I finally traced
the fault to R11 which was difficult to
find as it was covered in brown gunge
from one of the capacitors. It was difficult to test in circuit as it effectively
had a large capacitance in parallel, but
it was open.
I did not have a 2.2kW resistor handy
but a 1kW and 1.2kW in series worked
as a replacement. This fixed the problem and it was reassuring to hear the
relay click on and off and get audio
via the sockets on the back.
After removing my flying leads and
reassembling, I checked that all was
still operating. My friend was very
happy to have her music back, but
since I had deprived her of it for so
long (waiting for parts to arrive and
putting it aside out of frustration), I
felt I couldn’t charge her anything.
I might have saved time and frustration if I had done some better testing
at the start and applied (correct) logic.
Pony 3 mobility scooter
J. W., of Aspendale, WA, was recently asked if he could repair a connector on his friend’s mobility scooter
so naturally he agreed to have a look
at the machine. . .
My friend said that the scooter was
not going as fast as it used to. He had
76 Silicon Chip
been fault-finding the problem over
a period of time and had isolated the
fault to a 2-pin Molex connector. So he
delivered the scooter and we set it up
in the workshop. I removed the cover
from the controller and checked the
“faulty” connector. It seemed to be OK
but I gave it a clean anyway.
With the scooter out of gear, we
were able to hear that the motor was
still not revving fast enough, although
at one stage it did rev up for a short
period. I traced the wiring from the
2-pin connector and found that all it
did was connect the ignition switch
to the controller PCB. So it seemed
highly unlikely that this would have
any effect on the speed of the scooter.
I suggested that he leave the
scooter with me and I would
investigate further. I could not
find any service information on the ‘net so decided
to check the obvious and
hope to find a cure.
The speed was controlled by two potentiometers: a throttle
control with levers for
forward and reverse and
a speed control potentiometer which set the
maximum speed.
I disconnected and
removed the throttle
controller which looks
like a rectangular potentiometer. I found
on the ‘net that
this was called
a wig-wag controller with a
self-centring
position that
was supposed
to give a resist-
ance of half the total. The wig-wag
controller was marked as 5kW and it
measured 5kW between the two outside terminals.
I then checked between the outside terminals and the centre one.
The reading showed a variation of approximately 2.5kW when the controller shaft was moved in each direction.
I assumed that this was OK so put it
back in circuit.
I then unsoldered the speed controller pot and checked it with a multimeter. The pot was marked 20kW and
started at a reading of 20kW at the low
speed end of its travel.
The resistance reduced as I turned
it to a higher speed position but as it
reached about ¾ of the travel, the reading reverted to 20kW and stayed there.
So with the pot turned up to maximum
speed it was giving a resistance associated with low speed and not the zero
ohms I was expecting.
I only had a 50kW pot on hand so
I connected it up and found that the
motor now started at low revs and increased to quite a high speed with the
pot turned to zero ohms, the maximum
speed position.
So it was off to my local parts supplier to get the correct replacement
for just $2. Once it was installed and
everything put back together, I did a
few laps of the garden to prove it was
siliconchip.com.au
all OK. My friend was delighted as he
had been quoted over $200 to have it
looked at by the supplier.
Fixing a useless machine
J. G., of Princes Hill, Victoria is having fun in his retirement, reliving those
halcyon days when he made model
planes and played around with electronics. He takes up the story. . .
My most recent project has been to
make a “useless machine”, invented by
Marvin Minsky at MIT in Boston. The
first prototype seems to have been built
in the 1950s by Claude Shannon, the
pioneer of information theory.
A useless machine consists of a box
with an on/off toggle switch on top.
When it is turned on, a hand emerges
and turns it off. That’s all it does. You
can buy useless machines from Jaycar,
but I wanted to make one that is even
more useless! It would be more creepy
if the hand emerged very slowly but
snapped back into its box the moment
it hits the switch.
Servo motors used to control model
planes are ideal for this purpose. They
consist of a small brush motor and a
set of reduction gears which actuate
a “control horn” linked to the rudder
or ailerons.
The servo is controlled by a stream
of pulses, the width of which sets the
position of the control horn. Typically,
a pulse width of 1.5ms sets the horn at
a midway position; a pulse of 1.0ms
moves it to one extreme and 2.0ms to
the other extreme.
It was relatively simple to devise a
circuit using a CMOS version of the
ubiquitous 555 timer IC, where the
pulse width is smoothly increased
by a slowly rising voltage on the control pin, causing the hand to emerge
slowly, followed by a sudden return to
a short pulse, putting the hand back
into the box.
Preliminary testing without the motor connected showed that the circuit
worked well, but the best laid schemes
o’ mice an’ men gang aft agley. With the
servo connected, the hand oscillated
wildly and randomly back and forth.
This problem is well known in the
radio-controlled plane fraternity, and
is known as “servo chatter”. It didn’t
take long to confirm that it was caused
by noise from sparking motor brushes.
Somehow the motor noise was getting
into the control circuit but a variety of
measures including ferrite beads in the
motor wires and a 2000µF capacitor
siliconchip.com.au
across the battery made no difference.
Old-timers will remember a common problem that used to affect valve
radios, aptly known as “motor-boating”; characterised by a loud put-putput-put in the speaker. These days
it is sometimes seen in valve guitar
amplifiers.
Motor boating is caused by feedback
between the power output stage and
earlier voltage amplifier stages via the
high voltage supply line. Badly designed circuits can be prone to motor
boating but it is typically caused by a
faulty electro.
Motor boating is commonly prevented in the design stage by decoupling
the early stages from the power stages,
by using a simple RC filter in the high
voltage line to prevent fluctuations in
the supply line feeding back into the
high gain voltage amplifier stages.
Could decoupling solve my problem
with servo chatter?
The motor and the control circuit
were fed from a 6V battery. Measurements showed that the servo motor
drew a wildly fluctuating current with
peaks of well over an amp and the
scope confirmed that the supply voltage jumped up and down randomly
when the motor moved. The control
circuit only consumed 2mA. How
about decoupling?
All it took was a 220W resistor followed by a 1µF MKT capacitor to
earth. The control circuit still worked
perfectly with less than half a volt
drop in supply voltage, but the servo
chatter disappeared completely. Now
when the hand moves out slowly and
creepily, and snaps back instantly, it
always provokes fits of laughter in
young and old.
Incidentally, while the labelling on
the switch in the accompanying picture may look incorrect, it is not. The
switch is pictured in the ON position.
The hand pushes the switch to the
OFF position. In the “resting” situation, the servo arm presses against
an invisible microswitch, keeping it
in the OFF state. The microswitch is
in parallel with the visible switch but
is not seen in the photo, such that no
power is delivered to the electronics
or the motor.
The hand is activated by moving
the switch to the ON position. This
supplies power to the electronics and
the motor.
The hand slowly moves forward,
such that the microswitch is now
turned on. The hand moves out of the
box, pushing up the lid, and pushes
the visible switch to the OFF position.
The hand then moves quickly back to
the inside of the box, where a hidden
protrusion presses on the microswitch
and turns the power off.
There’s more to it than meets the
SC
eye!
A useless machine is a functional device that serves no useful purpose. This
example was designed such that when switched on, a hand will come out and
turn the switch off; using a servo to provide the hand with a variable speed.
September 2017 77
LTspice
Part 3:
by Nicholas Vinen
Modelling an
NTC thermistor
Last month, we designed a relay simulation and added it to our
SoftStarter circuit. But to completely simulate the SoftStarter, we need
an NTC Thermistor model and LTspice has no such model. Well, there's
only one solution. . . make one! In the process, we'll learn a lot about
designing simulation models and design some very handy building
blocks that can be re-used later.
A
thermistor is a non-linear resistor which changes in value as the
temperature changes. The resistance
of an NTC Thermistor varies inversely
to the temperature. In other words, its
resistance drops as it heats up.
High power NTC thermistors are
useful for reducing inrush current,
especially in mains-powered circuits,
as they have a high enough initial re-
sistance to limit the current drawn by
capacitor-input power supplies and
motors, but a low enough resistance
(once they warm up) that they don’t
interfere with the load’s operation and
don't waste much power.
We took this a step further in our
SoftStarter, published in the April
2012 issue (www.siliconchip.com.au/
Article/705). By building a circuit
which shorts out a current-limiting
thermistor with a relay a few seconds
after mains power is applied, we get
the best of both worlds; once the relay
activates, the power loss in the thermistor is zero. The circuit for that project is shown here, in Fig.1.
Developing that circuit took some
trial-and-error as we had to build it and
assess its performance in order to tweak
Fig.1: the original circuit from our SoftStarter, published in the April 2012 issue. This reduces inrush current to the
connected device each time mains power is applied. This was revised to add load current sensing in the Soft Starter for
Power Tools, in the July 2012 issue but this month we’re simulating the more basic circuit shown here.
78 Silicon Chip
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the component values. If you look
at the original article, we published
some simulation curves showing how
an NTC thermistor can be used to reduce inrush current. So why didn’t we
simulate the circuit before building it?
It was because SPICE does not have
built-in support for any kind of variable resistance device, which would
allow us to simulate the behaviour of
an NTC thermistor. But it is possible
to build a (fairly complex) sub-circuit
to do the job instead and this article
will show you how.
The variable resistance is created using two high-voltage Mosfets in series,
connected source-to-source, with their
gates joined together. They are then
shunted with a resistor, setting the
maximum resistance of the device. The
minimum resistance is determined by
the properties of the Mosfets and how
their gates are controlled.
The reason for using two Mosfets is
to prevent body diode conduction in
one direction, as the body diodes are
facing in opposite directions. Since
their gates and sources are joined,
they both must always have the same
gate-source voltage, so they are simple
to control and the on-resistance of the
combination is simply twice the onresistance of a single Mosfet.
Note that SPICE generally does not
model the body diode conduction in a
Mosfet. To simulate a realistic Mosfet,
you may need to connect a zener diode
across it, with the zener voltage equal
to the avalanche breakdown voltage of
the Mosfet you've chosen.
But just in case SPICE decides to get
clever and simulate avalanche breakdown for us, our back-to-back Mosfets
will work just like they would in reality, preventing current from flowing
unless they are both switched on.
Before we proceed, please note that
all the sub-circuits, symbols and test
circuits shown in this article are available for download in a ZIP package
from the Silicon Chip website (free
for subscribers). So you may wish to
download this and “play along” with
the tutorial. You can easily experiment
with the circuits, changing values and
seeing the effects.
depending on the simulated temperature of the NTC thermistor. We need a
way to track dissipation and average/
accumulate the instantaneous power
to determine the temperature, then use
this to vary the resistance.
The simulated temperature also
needs to drop over time when dissipation is low, simulating the normal
cooling process and that temperature
needs to translate into an appropriate
voltage to drive the Mosfets, to achieve
the right resistance value for a given
simulated temperature.
Broadly, our solution is as follows.
We charge a capacitor via a diode and
resistor to simulate thermistor heating.
The voltage across this capacitor will
represent the temperature. A resistor
across this capacitor will simulate
cooling to ambient temperature.
We will then amplify and level-shift
this temperature-proxy voltage and apply it to the Mosfet gate, and adjust the
amplification factor and RC time-delay
constants until the result closely matches the behaviour of a real thermistor.
To charge the capacitor representing
temperature, we need a voltage that's
proportional to the instantaneous dissipation in the thermistor and this can
be calculated as the product of the
voltage across and current through the
thermistor. That sounds simple but it
isn’t easy to arrange in SPICE.
For a start, heating does not depend
on the polarity of the voltage or the
direction of the current so we need to
compute their absolute values before
multiplication. And unfortunately,
there's no easy way to multiply two
voltages in SPICE. So we have to build
an analog multiplier circuit for this job.
Measuring voltage and current
The complete sub-circuit for our
thermistor simulation is shown in
Fig.2, with its corresponding symbol
at top. In the lower left-hand corner,
you can see our two back-to-back Mosfets, M1 and M2, with 10W resistor
R1 across them. We have chosen 10W
since this matches the nominal cold
resistance of the SL32 10015 type NTC
thermistor used in the SoftStarter.
We are using IPB200N25N3 Mosfets because they have a high voltage
rating along with a low RDS(on) of
20mW. Since they are in series, this
gives a minimum thermistor resistance of 40mW. The SL32 10015 typically measures 48mW at the full rated
current of 15A, with its body temperature at 228°C.
It doesn't matter that the Mosfet
resistance is slightly lower since the
whole sub-circuit incorporates feedback and it will adjust the Mosfet gate
voltage to achieve the required resistance, to keep the body temperature
steady for a given current. The Mosfets
just need to have a low enough RDS(on)
to be able to give the required current.
We have placed a voltage source,
V1, in series with the simulated thermistor. It is set to 0V DC. It might seem
weird to have a voltage source of zero
volts but voltage sources also double
as current meters in SPICE. So V1 is
used to measure the current through
Building the control circuitry
So that's how we're going to provide
a controlled resistance but that leaves a
rather complex problem to solve, which
is how to actually produce a Mosfet gate
voltage to give a resistance which varies
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Fig.2: our complete NTC thermistor simulation sub-circuit, along with its symbol
at top. X1 and X2 are precision rectifiers while X3 is an analog multiplier that
calculates the instantaneous dissipation of the simulated thermistor. This is
accumulated in capacitor C1 and the voltage across it is ultimately applied to
the gates of Mosfets M1 and M2 to control the transconductance appropriately.
September 2017 79
the thermistor. Note that the points labelled "a" and "b" are the ports used for
external connection to the thermistor.
H1 is a current-controlled voltage
source and you can see that its value
field is set to "V1". As a result, the
voltage across H1 will track the current through V1, ie, with 1A through
V1, there will be 1V across H1; you
can change the ratio but in this case,
the default of 1A:1V is fine.
We then feed the output of H1 to subcircuit X2, which produces an output
that is the absolute value of the voltage at the input. Similarly, the voltage
across the thermistor is fed to another
absolute voltage sub-circuit, X1.
Calculating absolute voltage
The sub-circuit to calculate the absolute value of a voltage is shown in
Fig.3. It's quite straightforward.
In the real world, this is typically
done with a "precision full-wave rectifier" comprising two op amps, two
diodes plus some resistors. The op
amps cancel out the forward voltage
of the diodes. We could simulate such
a circuit, however, it would slow the
overall simulation down as it would
have to simulate two op amp ICs plus
a bunch of other components.
So we came up with this much
simpler circuit using just two voltagecontrolled switches (S1 & S2) and two
voltage-controlled voltage sources (E1
& E2).
Both E1 and E2 are set for a gain
of unity ("1"), with the input voltage
and ground connected to their + and
– inputs respectively. So essentially
they are just buffers. But because E1's
output is floating, if we hook up its
output terminals in reverse, it acts as
a voltage inverter.
Both switch models are set up so
that the switch is on its input is positive (ie, positive input voltage higher
than negative input voltage). The
threshold for S2 is 1µV higher than S1,
to prevent them both conducting if the
input voltage is exactly 0V.
So if the input voltage is positive, S1
connects the buffered signal from E2
directly to the output terminal. And if
it's negative, the output of E1 is positive and this is instead connected to
the output terminal.
You can see the simple symbol we
came up with for this sub-circuit at the
top of Fig.3. The test circuit is shown in
Fig.4, with the results of the simulation
shown above. The input is a 3V peak80 Silicon Chip
Fig.3: our precision rectifier sub-circuit is quite simple; it either applies the
input voltage (buffered by E2) to the output, via voltage-controlled switch S1, or
if the input is negative, it is inverted by voltage-controlled voltage source E1 and
this positive voltage is applied to the output instead.
Fig.4: test circuit for the precision rectifier, which shows a sinewave with a DC
offset in green overlaid with the output of the rectifier, in blue.
to-peak sinewave offset by 0.5V and
shown in green. The output is shown
in blue. As you can see, the output is a
perfectly rectified version of the input.
Tracking instantaneous power
So, the outputs of X1 and X2 shown
in Fig.2 are a rectified (always-positive) version of the voltage and current
across the simulated resistor respectively. Both voltages are referenced to
the bottom end of the thermistor (terminal "b"), which is effectively the ground
for this circuit. As a thermistor is only
a two-terminal device, it must "float".
The outputs of X1 and X2 are fed
to voltage-controlled voltage sources
E2 and E3 which both have a gain of
0.05, ie, they attenuate the voltages
by a factor of 20. This is to ensure the
resulting voltages are quite low (just
a few volts), so they can be fed to the
analog multiplier block, X3. X3 has a
"power supply" of 15V, so the inputs
need to be in the range of 0-15V.
We could use resistive dividers to
reduce the voltages for X3 but then the
source impedance seen by X3 would
be non-zero and might affect its operation. SPICE components such as
voltage-controlled voltages sources
are “ideal” in that they have infinite
input impedance and zero output impedance.
The output voltage from multiplier
block X3 is the product of its input
voltages and so the output voltage
corresponds to the instantaneous dissipation in the thermistor, scaled down
by a factor of 400 (20 x 20). So 1V out
corresponds to 400W dissipation in
the simulated thermistor.
siliconchip.com.au
Fig.5: the analog multiplier is based on a real circuit and uses log/anti-log stages
and summation to multiply the two input voltages, at Vin1 and Vin2. Vin2 is
converted into a current which is sunk from the emitters of Q1 and Q2. The
voltage at Vout is almost exactly equal to the product of the two input voltages.
V1 exists to measure the current at
the collector of Q1. F1 is set up to provide exactly the same current, as its
“value” field is set to V1. F1 also has
a gain value, not shown in the circuit,
which we’ve set to 1.
The output voltage which is the
product of Vin1 and Vin2 appears at the
collector of PNP transistor Q3. This is
then fed to voltage-controlled voltage
source E2, which acts as a buffer and
gain stage. We’ve set its gain to 7.3 as
we found that this provides an output
of 1V when Vin1 = 1V and Vin2 = 1V.
The test circuit for this sub-circuit
is shown in Fig.6. Both input signals
(green and blue) are sinewaves which
vary between 0V and 1V but at different
frequencies, so the peaks and troughs
coincide at various points throughout
the 10ms simulation time. The output
of the multiplier is shown in red.
Note that the red curve is very close
to 0V when either input is at 0V and
very close to 1V when both inputs are
at 1V. So it is operating effectively as
a multiplier.
Ideal diode model
Fig.6: our analog multiplier test circuit. Its inputs are sinewaves with 1V peak
amplitude, shown in green and blue, with the resulting product shown in red.
Analog multiplier operation
The internals of X3 are shown in
Fig.5, with its symbol at top. We got
the basis of this circuit from the following URL:
www.sayedsaad.com/montada/
showthread.php?t=22594
Essentially, the circuit computes the
logarithm of the two input voltages,
adds them, then exponentiates the result to produce the output voltage. The
result will be proportional to the product of the input voltages, Vin1 and Vin2.
Vin1 is fed to a voltage-controlled
voltage source, E1, with a gain of unity. This acts as a voltage buffer so that
the source impedance won’t affect the
rest of the circuit. Voltage source V6
provides a -0.15V bias to this signal,
which we experimentally determined
was necessary in order to achieve a 0V
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output when Vin1 = 0V (regardless of
the magnitude of Vin2).
Vin2 is fed to voltage-controlled current sink G1, with resistor R6 (10MW)
in parallel. R6 is not in the original
design but we found that this sped up
the SPICE simulation, because in cases
where Vin2 is very close to zero, the
simulation of this circuit breaks down.
As you can see, G1’s gain factor is one
ten-thousandth, ie, 0.0001. This is so
that for Vin2 of 1V, G1 sinks 100µA,
to match fixed current source I1 and
provide correct scaling of the output.
I1 is connected to the positive rail
(V+) to supply transistors Q4 and Q5
which are configured as diodes. The
collectors of transistors Q1 and Q2 are
fed by a current mirror formed by voltage source V1 and voltage-controlled
current source F1.
As shown in Fig.2, the output of
X2 which represents the dissipation
(labelled “pout” for “power output”)
passes through diode X4 then 10GW
resistor R2, before charging 5nF capacitor C1. R2 limits the rate of C1’s
charging to represent the fact that the
thermistor body doesn’t increase in
temperature instantly when the dissipation increases; it has thermal inertia.
Resistance values that high are rarely seen in real circuits because leakage
currents can overwhelm them but that
isn't an issue in a simulation; it’s the
time constant that’s critical.
The purpose of diode X4 is to model
the fact that the rate of thermistor heating depends on dissipation but the rate
of cooling depends on its temperature.
In other words, a very high dissipation
should heat the thermistor up fast but if
dissipation falls to zero, it cannot cool
down back to its original temperature
in that same time; it might take much
longer. So this diode only allows the
“heat” to flow in one direction.
But we don’t want to use a real diode model because its forward voltage
would interfere with this process. It
would not conduct until the dissipation rose above a certain level and
would then reduce the maximum
voltage applied to C1. We would prefer an “ideal” diode which essentially
September 2017 81
acts as a switch, turning on as soon as
the voltage at the anode is above the
cathode and switching off as soon as
that reverses.
So that’s exactly how we’ve modelled it. The sub-circuit and corresponding symbol are shown in Fig.7.
The voltage controlled switch’s control
terminals are connected directly to
the switch terminals. The threshold is
set to 0.1mV and the hysteresis value
is the same. That means the voltage
across the ideal diode during forward
conduction will be well under 1mV.
Finishing the thermistor model
Getting back to Fig.2, the time constant of R2/C1 determines how quickly
the modelled thermistor heats up due
to internal dissipation while R4/C1 set
its cool-down characteristics.
Placing resistor R4 across C1 accurately models cooling since, in the real
world, the rate of cooling is proportional to the difference between an object’s
temperature and the ambient temperature. In the simulation, current through
R4 is proportional to the voltage across
C1 (a proxy for the temperature) and so
the rate that “heat” leaves the model is
directly related to its temperature.
So the simulated temperature, labelled “temp”, is applied to the inputs
of another voltage-controlled voltage
source, E1, with a gain value of 500.
Besides applying gain, the other reason for E1 is that it stops the following
circuitry from drawing current from C1
and affecting the thermal simulation.
Voltage source V4 has a fixed value
of 3.2V and this provides the Mosfet
gate switch-on bias voltage for M1 and
M2. Note that E1’s negative output
terminal is connected to the sources
of M1 and M2. This means that with
a simulated temperature at ambient, the gates of M1 and M2 are 3.2V
above their source terminals, just on
the edge of conduction. For each 2mV
across C1, the gate-source voltage increases by 1V.
This gain figure was determined
experimentally, by comparing the behaviour of the simulated thermistor to
figures in the SL32 10015 data sheet.
This figure was found to give a realistic
time constant and ultimate resistance
under sustained load.
It’s important to realise that this model contains a negative feedback path. As
the voltage across C1 increases, Mosfets
M1 and M2 switch on harder, reducing
the voltage across R1 and this, in turn,
82 Silicon Chip
Fig.7: another type of precision rectifier, this time in the form of an ideal diode
(ie, a half-wave rectifier). This is basically just a switch which allows current to
flow from input to output only when the input voltage is higher than the output
voltage.
Fig.8: a simple test circuit for our now complete NTC thermistor model, utilised
here as X1. The load is primarily capacitive so draws the most current around
the mains peak. You can see how the capacitor voltage (green) rises relatively
slowly, over around 50ms, while the thermistor dissipation (blue) starts very
high but drops down to a low level after around 100ms.
reduces the dissipation and thus the
voltage at “pout”. That then allows the
voltage across C1 to stabilise at a value
that depends on the voltage and current flow between points “a” and “b”.
1W resistor R3 between E1/V4 and
the gates of M1/M2 provides a tiny
delay for this negative feedback which
helps the simulation converge faster
(see the side panel for more details on
this phenomenon). The 100MW bleed
resistor effectively between the gate
and source terminals of M1/M2 was
added for a similar reason.
Testing the NTC thermistor
Fig.8 shows the test circuit. We have
a 325V peak sinewave representing the
mains, with the thermistor in between
it and the test load. There’s a simple
half-wave rectifier feeding a 1000µF
high-voltage capacitor with a 100W
bleeder/load resistor. This is intended
to crudely simulate a capacitor-input
switchmode power supply with a load.
Above it, you can see the result of
the simulation, with the voltage across
R2 in red, voltage across C1 in green
and instantaneous dissipation in X1 in
blue. (By the way, to plot dissipation of
a component in Windows, hold down
the ALT key while clicking on that
component. Once you’ve done that, to
display the average power, zoom over
the relevant portion of the waveform
and hold CTRL while clicking on the
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run the simulations very slowly or halt
altogether. This is due to a failure to
converge – see the side panel explaining this problem.
Putting it all together
Fig.9: another test of the NTC thermistor model, this time with a primarily
resistive load of around 15A. It takes around 100ms for the load voltage to rise
close to the full 230VAC with thermistor dissipation initially averaging 600W,
dropping down to 10W in the steady-state condition after around 200ms.
Fig.10: we can now complete our simulation of the SoftStarter. It uses the relay
and NTC thermistor sub-circuits we’ve developed plus a typical load comprising
an EMI suppression capacitor, bridge rectifier, mains filter capacitor and 100W
equivalent resistive load. We can probe the voltages and currents at various
points more easily than with the real circuit, which floats at mains potential.
formula at the top of the plot window.)
As shown, the voltages rise quite
gradually, over the first few mains cycles. If you remove X1 from the circuit,
C1 charges almost instantly, in under
1ms, drawing a peak current of almost
1000A! A real capacitor would have
too much parasitic resistance/inductance to draw quite so much current
but the contrast is still educational.
Note how the thermistor dissipation
drops initially, then rises a little before
finally dropping down to a stable level. That’s because after the thermistor
heats up a little initially and its resistance drops, it allows more current to
flow into C1 which briefly increases its
dissipation before the voltage across X1
siliconchip.com.au
drops, further reducing its dissipation.
Fig.9 shows a variation on this test
circuit, where we have replaced the
capacitor input power supply with
a resistive load shunted with an EMI
suppression capacitor. With a load resistor of 16W, it will draw 14.4A RMS
on a continuous basis (ie, 230VAC ÷
16W). As you can see, in this case,
the thermistor heats up a little more
gradually and as the voltage across R2
approaches the full 230V RMS, dissipation in the thermistor drops from
an initial average of 600W down to
around 10W after about 200ms.
Note that if you are experimenting
with these circuits, you may find that
certain changes will cause SPICE to
Fig.10 shows our now complete
SoftStarter circuit at bottom, based on
what we finished with last month (ie,
incorporating the relay model we developed then) but now also including
our thermistor, X2, plus a test load circuit comprising EMI suppression capacitor C4, bridge rectifier D7-D10, filter capacitor C5 and resistive load R6.
The simulation output at top shows
the mains voltage at V1 (green), voltage
across the load at C5/R6 (cyan), current
through simulated thermistor X2 (blue),
voltage across the relay coil (mauve)
and thermistor dissipation (red).
As you can see, the inrush current is
limited to around 20A, which is pretty
much the same peak current that the
load draws during normal operation.
You can see the thermistor dissipation is very high over the first few
cycles but drops to below 10W after
about 500ms, at which time the relay
coil voltage rises and the thermistor
is shorted out.
Its dissipation then drops to almost
zero; if the relay didn’t close then, its
dissipation would continue to drop,
to a steady-state value of around 4W.
So in other words, the simulation is
working correctly and showing how
the real circuit behaves!
Note that a small amount of current
is still shown flowing through the thermistor even after the relay contacts
close. This is as a result of the non-zero
relay contact resistance we’ve programmed into our model. But because
the product of current and voltage is
so low, dissipation still appears as a
flat line once the relay latches.
Note also that Fig.10 shows the voltage across the relay coil of X1, even
though that part of the circuit is not
connected directly to ground. This
can be achieved by right-clicking in
the plot window and selecting “Add
Trace”, then typing in the expression
V(x)-V(y), where “x” and “y” are nodes
in the circuit.
This is one reason why it’s a good
idea to label nodes in the circuit (as
we have with VOUT) since the automatically generated node names like
“n004” can change if you modify the
circuit.
You also need to figure them out (by
September 2017 83
Simulation slowness, pausing or intermittent failure
SPICE simulations have two distinct phases, the first of which is optional, but normally present. The first phase is where it determines the initial DC operating point. In other words, for every component which has state – primarily capacitors (charge)
and inductors (magnetic field strength) – it needs to determine the steady-state condition* with which to start the simulation.
If you have something like an oscillator in the circuit, it won’t have a steady state, but SPICE will still attempt to determine a reasonable starting point – a condition which a real circuit may find itself in at some point in time, prior to any AC signals being applied.
Various circuit configurations can make this impossible. One thing that often throws SPICE off and prevents it from finding
the initial DC operating point is nodes which have no DC current path to ground. For example, it’s perfectly valid to apply an AC
signal to a pair of series-connected capacitors, with them operating as a capacitive voltage divider.
But unless you have a way for current to flow from the junctions of these capacitors to ground, SPICE will often throw up its
arms in disgust. The usual solution to this problem is to connect a high-value resistors from this junction to ground. It will have
negligible effect on the operation of the circuit but may help SPICE to converge on an initial operating point solution.
If you’ve drawn up a circuit and can’t figure out any way to get SPICE to get past this initial hurdle and start the simulation,
your other option is to get it to skip this step entirely and either start with everything in a default state (capacitors and inductors
discharged etc). Or alternatively, you can specify the initial state of the components yourself.
In fact, you can even adopt a “mix-and-match” approach, providing initial states for some component and letting SPICE figures
the other out. You may need to use trial and error to determine which components need their initial conditions defined before
the software will reliably complete this step.
To set the initial condition of a component, modify its value and add " ic=xx" to the end, where xx is the initial value. For example, a capacitor can have a value of "10uF ic=5V" and an inductor can have a value of "100uH ic=1A". If you also add " uic"
to the end of the simulation command (labelled "skip initial operating point solution" in the LTspice configuration dialog), all
components will start with a value of 0V/0A unless the initial condition is specified.
Note that you can also abort the initial operating point solution, if it gets stuck, by pressing the ESC key on your keyboard.
SPICE will then take whatever its last guess was as to the initial conditions and run the simulation.
SPICE can also get stuck during the simulation, for similar reasons. This is often at the point where a transistor is moving
into or out of conduction, a diode is becoming forward biased and so on. The rapid changes in circuit behaviour at these points
can cause it to move forward in smaller and smaller time steps. It will normally eventually get past that point but it may take a
long time, and it may get stuck again soon afterwards.
There are various techniques you can use to avoid or mitigate this. First, it helps to understand why this happens. The following
course notes contain some useful information on this aspect of SPICE: www3.imperial.ac.uk/pls/portallive/docs/1/7292571.PDF
This document is from the Department of Electrical and Electronic Engineering, Imperial College London. On page 24, it
states “There are convergence problems associated with very high conductance [… and] very high resistance”.
On pages 23 and 24, it shows an example of attempting to iteratively solve a circuit involving a current source, resistor and
diode and shows how, depending on the algorithm used, the software may not be able to converge on the solution.
The following pages discuss the GMIN parameter, one of several you can adjust in LTspice which may help prevent it from getting stuck. This can be changed by going to the “Control Panel” menu option in the “Tools” menu and clicking on the SPICE tab.
We experimented with some of these options and found that changing the “Default Integration Method” from “modified trap”
to “trapezoidal” sometimes caused our simulations to run much more smoothly with a range of different component parameters.
Changing the “Solver” from “Normal” to “Alternate” had an even bigger effect on the simulation’s performance. There were
times where it would absolutely crawl with the Normal solver but ran very fast and reliably with the Alternate solver. So if you
find your simulation getting stuck, it’s well worth trying to change these parameters before resorting to modifying your circuit.
If you do need to modify the circuit, we suggest the following: add high-value resistors across capacitors, or from the ends
of capacitors to ground. Add high-value resistors or low-value capacitors across diodes and/or transistor junctions. For generic
components, try different component models, or try using models of similar parts.
Many of these changes can have negligible impact on the accuracy of your simulation while potentially making SPICE run
much faster and without getting “stuck” as often. For example, in our SoftStarter simulation (shown in Fig.10), we sometimes
get an error message that the initial operating point solution failed, implicating diode D7. While changing the Default Integration
Method helped, another solution we found was to put a low-value capacitor across D7. This has hardly any effect on the results
but seemed to overcome that particular problem. So that’s one example of a way to modify your circuit when SPICE is “playing up”.
* a circuit may have zero, one or many steady-state conditions. These are conditions where the series of simultaneous equations that represent
the circuit's behaviour converge to a fixed set of values. This is important for transient simulations as without a steady-state condition, SPICE
cannot model the behaviour of the circuit.
hovering the mouse over a point in the
circuit and looking at the bottom of the
window) before you can enter the expression, whereas if the circuit nodes
are labelled, the names are obvious.
Conclusion
So what is this simulation good for?
First, it would allow us to more easily
tweak the power supply component
84 Silicon Chip
values, the time constant values which
set the relay delay time and so on. It
also allows us to examine the voltages
and currents applied to each component to verify that they will not experience conditions outside their ratings.
For example, we can examine the
expected inrush current for various different types of load and whether the relay time delay is sufficient to allow the
thermistor to finish its job of limiting
that current before it’s shorted out. We
could also see the effect of disconnecting the load and then re-connecting it
some time later, before the thermistor
has had a chance to fully cool down.
That’s it for this month. In our next
SPICE tutorial, we will look at simulating audio circuits, especially those
which involve op amps.
SC
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Build an Arduino
Data Logger
with GPS
Part 2 by Nicholas Vinen
As promised, here is a follow-up to the Arduino Data Logger article from the
last issue, with more details about how its software operates. We will also take
you through the steps required to add support for new sensors and show
some photos of the completed shield PCB.
PCB
W
hile the bulk of this article details the operation of the critical
Arduino software for the data logger,
we also have some important information on building the shield PCB, shown
in the photos.
Upon building the PCB, we discovered an error in the overlay diagram,
Fig.2, on page 30 of the August 2017
issue. The pins for the DS3231 real
time clock and calendar module were
labelled incorrectly. The revised diagram, shown here, gives the correct
labelling.
The PCBs that we supply from our
Online Shop will have the correct labelling.
Regarding mounting the DS3231
module, our module came fitted with
a 6-pin right-angle header. We straightened this with a pair of pliers and then
soldered a 4-pin straight header at the
opposite end.
This module can then be soldered
directly to the PCB, as shown in the
photos. Make sure to trim the pins so
that they can’t short against anything
on the Arduino board below. The advantage of this approach is that you
don’t need to use any screws or spacers
to retain it on the board.
As for the microSD card module,
we used four M2 machine screws and
nuts to hold it on the board, along
86 Silicon Chip
with short untapped spacers. You
could use Nylon nuts or washers as
spacers. These parts were not listed
in the Parts List last month (see Extra
Parts on page 90).
It needs to be pretty close to the
board if you’re using a socket to make
the electrical connections, as we did,
or else the socket pins will not reach
the pads on the board.
The remaining construction details
were in the article last month. So refer
to that article to complete the shield.
Now let’s move on to the Arduino
software sketch details.
Software description
The SdFat and SPI libraries are used
to read and write data on the microSD
card, which is formatted with either
FAT16 or FAT32. RTClib is used to
control the DS3231 real-time clock
and calendar module. The TinyGPS
library is used to decode data from the
optional GPS unit, although the software serial interface used to receive
data from it has been customised, as
explained below.
We also use the OneWire library to
communicate with a DS18B20 temperature sensor, if present, and the
MsTimer2 library to manipulate hardware Timer2 if we have set up any of
the digital inputs to measure frequency.
We use Timer2 to provide the normally one second gating period to
count pulses on the relevant pin, because Timer2 can be left running in
one of the sleep modes. This mode
uses more power than the normal sleep
mode, so we only use it when the frequency counting feature is active.
We also have some custom routines
to put the ATmega328P microcontroller on the Arduino into sleep mode and
wake it up when required.
The setup() routine is run at power-up time and first sets up the input
and output pins. It then checks that
the real-time clock module is present
and whether it has the current time. If
not, it sets the clock time to be the time
that the sketch was compiled, plus 20
seconds (to allow for the approximate
time required to compile and upload
the sketch). It then stores the new time
in EEPROM.
If the Arduino is reset within one
minute, as determined by comparing the clock time to that stored in
EEPROM to the RTCC, the time is
advanced to the next whole minute.
Thus, if you programmed the chip at
say 11:37:25, and reset it at exactly
11:38:00, the clock would have the
correct time, accurate to the second.
The setup routine then initialises
the microSD card and assuming that’s
siliconchip.com.au
siliconchip.com.au
The finished Arduino Datalogger without the Elecrow charger module, Li-ion
cell and solar panel connected. Compared to building it with the prototyping
shield, it's much neater and easier to solder.
successful, the main loop starts and
runs as long as there is 5V power
available. If either the real-time clock
or microSD card initialisation fails,
LED1 flashes in an endless loop to
alert the user. It flashes at 2Hz for a
real-time clock fault and 4Hz for an
SD card fault.
The main loop
The main loop() function first
checks for the presence of a GPS module, if one has not already been detected. In the absence of a GPS unit,
pin D8 is always high.
If D8 is found to be low, the software
serial port is set up to receive data from
this pin at 9600 baud, with TTL signal
levels. This serial port is then monitored for ten seconds, looking for the
string “$GPRMC,” which is part of the
standard NMEA data stream.
If during those ten seconds this
string is identified, a flag is set in the
software indicating that a GPS module
is present. Otherwise, the serial port is
closed down and the low level on D8
is assumed to be from electrical noise.
If a GPS module is determined to be
present, the unit will then wait for the
programmed period for a position lock
(defaulting to five minutes). If a lock
siliconchip.com.au
occurs during this time, the latitude
and longitude (along with the number
of satellites in view and the current
time) are stored for future reference
and pin D7 is driven low, to switch off
the GPS module and conserve power.
It is only brought high again once the
GPS details need updating, which by
default is once per hour.
If a lock does not occur during this
time, the location data is not updated
but the GPS module will still be powered down for an hour, at which point
it will try again. If the unit had GPS
lock previously, those co-ordinates
will be preserved. Otherwise, they will
be kept blank.
While it is doing all this, the normal data logging tasks are still going on, as we don’t want to lose any
data just because the GPS module
is active.
Data logging
Each time through the loop, the unit
checks the state of D9. If D9 is high (it
is pulled high by default), and the unit
has not received a message on its serial
interface to pause logging, it will then
check whether the configured logging
interval has passed.
If it has, the states of the analog and
digital inputs are queried and stored
in a RAM buffer, along with the data
The revised PCB overlay
diagram from last month.
The difference is that
every connection on the
DS3231 RTC was flipped
horizontally, eg, GND ↔
SCL, VCC ↔ SQW, etc.
September 2017 87
Top and bottom views of the assembled shield board. The right-angle
polarised connector at lower left (on the top view) is for the four analog
inputs plus ground while the digital inputs are on the 5-pin header to its
right. Note the real-time clock module is mounted so the cell is accessible.
from any extra sensors that the logger
is configured to query.
Once this RAM buffer is full, typically after about a minute, the microSD
card is brought out of sleep mode and
the values are converted into humanreadable format and appended to the
log file. While this is happening, LED1
is lit. As a result, is flashes very briefly
about once per minute, to indicate that
logging is occurring.
If pin D9 has been driven low, or a
pause command is received on the serial console, the log file on the microSD
card is closed and the unit will go into
sleep mode to conserve power until it
is told to continue logging.
The next time there’s logged data to
be written to the microSD card, a new
file will be created with the name containing the date and time of the first log
entry and the entries will subsequently
be written to that file.
Once all the logging tasks have
been completed, the software checks
the main USB serial console to see if
any data has been received. If it has, it
compares it against a list of commands
and if a valid command has been received, it processes it. There are four
commands: “stop”, “cont”, “list” and
“dump”. They are terminated with a
newline (enter/return).
“stop” pauses logging and “cont” resumes it; pausing is equivalent to pulling pin D9 low, so when a “stop” command is received, any buffered data is
88 Silicon Chip
written to the microSD card and it can
then be removed. When it’s replaced,
the “cont” command will then cause
the log file to be re-opened (assuming
D9 is not held low).
The “list” and “dump” commands
can only be used when the log file is
closed, so will normally be preceded
by a “stop” command. “list” displays
a list of all the log files on the microSD card over the serial console.
Dump then allows one of them to be
downloaded through the serial console. The log file name to be written
must be sent immediately after the
dump command, for example, “dump
ArduinoLog_2017-06-28_094837.log”.
Sleep mode
When the unit is not doing any logging, handling any serial commands
and the GPS unit is not powered up,
it will go into sleep mode to conserve
power.
We couldn’t find a suitable Arduino
library to perform this sleep function
so we wrote the SleepMilliseconds()
function ourselves. This will put the
chip into sleep mode for a period between 16ms and eight seconds, using the low-power watchdog time to
wake it up.
During this time, the ATmega328P
consumes well under 1mA. However,
other circuitry on the Arduino board
(eg, regulators) brings the total up
to around 8mA. Still, this is a much
lower power consumption than when
it is active and allows for a decent
battery life.
One of the tricks we’ve employed is
that we temporarily disable the Arduino’s hardware UART which provides
the main USB serial port when entering sleep mode, so that we can enable
a Pin Change Interrupt on pin D0, the
RXD pin for that serial port.
This means that the chip will automatically wake up if the state of that
pin changes, which occurs whenever
there’s any serial data being transmitted to the unit. Hence, the unit
can be in low-power sleep mode but
still respond to commands on the
serial port.
We ran into one slight problem with
the Arduino SdFat library which is
that the first time you open a file on
the SD card, the card’s current consumption jumps from under 1mA to
around 15mA and even if you close
the file, it will continue to operate at
the higher power level.
We solved this by closing the file after each write and resetting the SD card
interface, via a call to the sd.begin()
function. We then re-open the file later
and append data as required.
This means its power consumption
is back under 1mA all the time, except
when we are actively writing to it. Apparently this is a well-known and longstanding bug in the Arduino version
of the SdFat library and it’s mystifying
that it has never been fixed.
GPS serial interface
The Arduino Uno only has one hardware serial port which is hooked up to
its USB port (via a second Atmel chip
on the Uno board). We wanted to keep
this for communications with a PC, so
that logged data could be off-loaded
without removing the microSD card
(although in some cases, removing the
card would be easier/faster).
That means that the serial data from
the GPS unit must be received using a
“software serial port”, where the RXD
pin is just a normal digital input (with
internal pull-up enabled) and software
routines count the time between state
changes on that pin to decode the serial data.
The Arduino IDE comes with a popular library called SoftwareSerial to do
just that but we discovered in writing
this software that it has serious limitations. Basically, the problem is that
it’s a “blocking” type library, where the
siliconchip.com.au
CPU is 100% busy during the time that
serial data is being received.
Since a GPS unit sends out quite
a large burst of data each second, of
several hundred bytes, without a huge
RAM buffer, the buffer would always
overflow. That’s because while the
CPU is busy receiving serial data, it
has no time left to actually process it.
There’s another problem with SoftwareSerial which is that it assumes
that if you’re allocating a pin to receive
serial data, you also want to allocate
a second output pin to send serial
data. We don’t need to send any data
to the GPS unit and we don’t have any
spare pins.
We found a library called AltSoftSerial which solves the first problem.
It uses a piece of hardware in the Atmel chip known as an “input compare
unit” which, in combination with a
hardware timer, effectively provides
time stamps indicating when the state
of a pin has changed.
This allows the processor to continue running other code while it waits
for transitions on the serial input pin
and since the library is interruptbased, it provides a software serial
port that works almost as well as the
hardware port (at the low 9600 baud
rate we’re using, anyway).
Its major limitation is that the input compare unit is hooked up to pin
D8, so you must use this as the RXD
pin (and therefore you can only have
a single AltSoftSerial port). Similarly,
it uses “output compare” hardware to
produce the TXD signals in an asynchronous manner, which means the
TXD pin must be on D9.
In a stroke of luck, it just so happened that we had hooked up the GPS
TXD pin to D8 on our prototype, and
its RXD pin to D9, so we could use
AltSoftSerial without having to make
any hardware changes.
However, when we subsequently
decided to add S1 to the design, we
found that AltSoftSerial also forced
you to use the transmit and receive
functions together. So we made a
copy of the library, renamed it ReceiveOnlyAltSoftSerial and deleted the
sections which enable transmission.
That library is provided along with
our sketch.
Adding new sensors
One of the major advantages of this
data logger over our previous projects
is that it’s quite easy to customise.
While we provided it with a wide
range of standard features, we haven’t
tried to account for every possible sensor that you might want to attach. For
example, you may want to log data
from an I2C barometric pressure or
humidity sensor.
Since it’s written using the Arduino
IDE and already has built-in I2C support, you just can download some
example code for the sensors you want
to use, check that the example sketch
works and then integrated it into the
data logger code. This does require
some programming experience but
there’s a lot of information available on
the internet on programming Arduino.
One minor issue to consider is the
amount of free flash memory space.
With all the features enabled in our
code, it uses 96% of the total flash
memory (30,978 bytes out of 32,256
bytes).
However, if you don’t need the
DS18B20 or frequency counter support, that immediately drops to 84%
(27,394 bytes). Disabling serial debugging (by removing the #define
SERIAL_DEBUG line near the top of
the file) drops this further, to 81% or
26,406 bytes.
We realise that modifying the software can seem daunting, so we'll give
a concrete example showing you the
modifications to make to interface a
GY-68 I2C barometric pressure sensor
to the unit (and we will be offering
this sensor in our online shop in case
you want to give it a go; Cat SC4343).
This sensor will be described in
some detail in a future “El Cheapo
Modules” article. It contains a BMP180
sensor and has a 4-pin SIL header with
the pins labelled VIN, GND, SCL and
SDA. Wiring it up to the Arduino is
easy; we just used four male-to-female
jumper leads to connect these pins to
5V, GND, A5 and A4 respectively.
We then downloaded the sample
Arduino code for this module and discovered it uses an I2C address of 0x77.
The sample code contains a number
of helper function to interface with
the sensor.
The first step to integrating this with
our Data Logger code is to remove
the line near the top of the file which
reads “#define DS18B20_INPUT 2”.
We don’t need the DS18B20 temperature sensor features since the GY-68/
BMP180 has an onboard temperature
sensor. This frees up some flash memory, giving us 10% free.
We then copied and pasted the entire GY-68 sample code into the bottom
of the Data Logger sketch but deleted
the setup() and loop() functions (as
these would conflict with those used
by the Data Logger).
The sample code does two things
in its setup() function: sets up the
serial port, then calls the function
“bmp085Calibration”. So our next
step was to add a call to this function
at the bottom of our setup() routine.
The end of the setup() function now
looks like this:
bmp085Calibration();
From the side you can see that due to the depth of the screw head that the
PCB doesn't fit entirely flat relative to the Arduino board. If this is an issue
for you, simply omit the screw in that corner; as it will still have three
others to support it.
siliconchip.com.au
#ifdef SERIAL_DEBUG
Serial.println(F(“SILICON CHIP
Arduino Datalogger ready”));
#endif
September 2017 89
Extra Parts for the Arduino Datalogger
Used for mounting the microSD module to the shield PCB
4 M2 x 10mm machine screws
4 M2 hex nuts
4 short (~4mm) tapped or untapped spacers to suit M2 screws
OR
4 M3 Nylon nuts
OR
8 M2/M3 Nylon washers, 1mm thick
Looking at the loop() function in the
sample code, the following four lines
at the top are responsible for reading
data from the sensor:
// MUST be called first
float temperature =
bmp085GetTemperature
(bmp085ReadUT());
float pressure =
bmp085GetPressure
(bmp085ReadUP());
// “standard atmosphere”
float atm = pressure / 101325;
// Uncompensated calculation
// - in metres
float altitude =
calcAltitude(pressure);
Note that there is a bug in this code;
the third float variable should be set to:
float atm = pressure / 101325.0;
Otherwise, it will round the atmospheric pressure to the nearest bar (ie,
it will pretty much always be 1.0)!
Anyway, having looked at this code,
we need to create some RAM buffers
for storing these values before we can
log them. Towards the top of the Data
Logger code, at the end of the section
labelled “// Other stuff”, we add the
following line to do this:
float BMP180buf
[LOG_RAM_ENTRIES][2];
This gives us two floating point values per log entry to store the pressure
and temperature data. So now, we
modify the end of the function “write_
RAM_log_entry” to look like this:
// in degrees Celcius
BMP180buf[log_ram_filled][0] =
bmp085GetTemperature
(bmp085ReadUT());
// in bar
BMP180buf[log_ram_filled][1] =
bmp085GetPressure
(bmp085ReadUP()) / 101325.0;
++log_ram_filled;
90 Silicon Chip
Now we just need to modify the
“write_buffered_log_entries” functions so that the temperature and
pressure values are written to the
log file.
First, we modify the CSV header,
so that the line which used to look
like this:
if( !file.println(F(“Date,Time,VA0,
VA1,VA2,VA3, D0,D1,D2,D3,
Lat,Lon,NumSats,
SecondsSinceLock”)) )
Now looks like this:
if( !file.println(F(“Date,Time,VA0,
VA1,VA2,VA3, D0,D1,D2,D3,
Temp,Pres,Lat,Lon,NumSats,
SecondsSinceLock”)) )
We also need to modify this section:
#else
static const char
LogEntryTemplate[] PROGMEM
=
“%02d/%02d/%04d,%02d:%02d:
%02d,%d.%02d,%d.%02d,%d.
%02d,%d.%02d,%d,%d,%d,%d”;
#endif
That’s rather hard to understand
but basically, it just defines the format
of each number that’s stored in a log
entry in the CSV file.
We need to add two, both with decimal points, at the end (GPS data is not
included in this line). After adding
these, the new line looks like:
static const char
LogEntryTemplate[] PROGMEM
=
“%02d/%02d/%04d,%02d:%02d:
%02d,%d.%02d,%d.%02d, %d.
%02d,%d.%02d,%d,%d,%d,%d,
%d.%01d,%d.%03d”;
Note that we have set it up to log the
temperature with one decimal place
(%01d) and pressure with three decimal places (%03d).
Next, we need to make sure that the
RAM buffer used to temporarily store
the log lines before writing to the SD
card is large enough, so change this
section:
#ifdef COUNTER_INPUT
char buf[56+38];
#else
char buf[56+30];
#endif
to:
#ifdef COUNTER_INPUT
char buf[72+38];
#else
char buf[72+30];
#endif
Now all that’s left is to add the code
to actually write the temperature and
pressure data to the log file. Just after
the line which reads:
// add any extra logged data here
We insert the following:
,(int)BMP180buf
[log_ram_filled-1][0]
,(int)((int)(BMP180buf
[log_ram_filled-1][0]*10))%10
,(int)BMP180buf
[log_ram_filled-1][1]
,(int)((int)(BMP180buf
[log_ram_filled-1]
[1]*1000))%1000
This is a bit complex because unfortunately, the Arduino sprintf()
function (used for converting numbers into text) does not support floating point numbers. So what we do is
first print the integral portion of each
value, then the digits after the decimal
point; one for temperature and three
for pressure.
Running the Verify/Compile command from the Sketch menu then gives
us the following output at the bottom
of the screen:
Sketch uses 30,608 bytes (94%)
of program storage space.
Maximum is 32,256 bytes.
Global variables use 1,470 bytes
(71%) of dynamic memory,
leaving 578 bytes for local
variables. Maximum is 2,048
bytes.
So all the extra code for the BMP180
pressure/temperature sensor takes just
4% of the flash memory space and
leaves plenty of RAM free, despite the
extra buffering.
Uploading this new code to our
prototype gives the following log output:
siliconchip.com.au
Customising the software
You can simply download the software and then upload it to an Arduino Uno to get started with the data logger. However, since each logging application is different, we went to some effort to make the software easily customisable. The
top of the sketch looks like this:
#define LOG_INTERVAL_SECONDS
#define VRAIL_5
#define A0_DIV_RATIO
#define A1_DIV_RATIO
#define A2_DIV_RATIO
#define A3_DIV_RATIO
//#define DS18B20_INPUT
//#define COUNTER_INPUT
#define COUNTER_AVG_MS
#define LOG_RAM_ENTRIES
#define GPS_TIMEOUT
#define GPS_CHECK_INTERVAL
#define SERIAL_DEBUG
6
5.000
(100.0/47.0)
(100.0/47.0)
(100.0/47.0)
(100.0/47.0)
2
3
1000
6
(60*5)
// 5 minutes
(60*30)
// half an hour
You can change the first line to vary the logging interval, in the range of 1-60 seconds.
The second line should be altered to provide maximum accuracy for the analog inputs. Simply power up the
data logger with your preferred power supply and measure the voltage between the 5V and GND pins. Change the
VRAIL_5 value to this figure and (re-)upload the sketch.
Note that if you’re using the solar option, it’s best to make this measurement while the unit is running off battery power since this will be the normal condition and it’s likely to result in a different measurement than when
USB/solar power is connected, as this will bypass the power supply regulator.
The next four lines, Ax_DIV_RATIO, allow you to change the 100kW/47kW dividers for the four analog inputs
to measure higher voltages. Simply increase the 100kW value or decrease the 47kW value to allow higher voltages
to be measured, then alter the relevant lines in the software to compensate. If you don’t, you will get incorrect
readings. Since the four values are defined separately, you can use different divider values for each analog input.
The next two lines define which of the four digital inputs (#0-3) are used for a DS18B20 temperature sensor and
as a frequency counting input. These features are disabled by default, to save power, so the four inputs operate as
general purpose digital inputs. Remove the two slashes at the start of the line to enable that feature. Leaving these
features disabled will also increase the amount of free flash memory.
Note that if you are using a DS18B20, it must be connected directly to one of pins D2-D5 rather than via a 1kW
resistor (or replace the relevant 1kW resistor with a wire link) and you also need to fit a 4.7kW pull-up resistor from
5V to that pin – see Fig.1 last month. If using the frequency counting feature, the maximum frequency is limited
to roughly 10kHz and readings can be expected to be within a few percent of the actual frequency.
The next line defines the number of log entries to buffer in RAM. A larger value reduces power consumption
since the microSD card only needs to be powered up each time the buffer fills. In the default case, with a 6-second interval and 6-entry buffer, that’s once every 36 seconds. Basically, you probably don’t need to change this,
but you can reduce the value to free up some RAM (to a minimum of one) and increase it if you’re confident that
there’s enough free memory to do so.
The next two lines define how often and for how long the GPS unit is powered up, if it is connected. By default,
the unit will wait for a lock for a maximum of five minutes and it will power up the GPS module once per hour
to get a fresh reading. You can increase the timeout value if your logger will be in a marginal signal area but this
will increase power consumption for those times where it can’t get a lock.
Similarly, you can reduce the check interval to update the GPS co-ordinates more often than once per hour but
this will also come with a power consumption penalty.
If the last line is removed, the unit will not print debugging messages on the serial console, other than log entries
(as they are created). This reduces flash usage, as described in the text, making room for more code if required.
Date,Time,VA0,VA1,VA2,VA3,D0,D1,D2,D3,Temp,Pres,Lat,Lon,NumSats,SecondsSinceLock
29/06/2017,12:57:04,0.00,0.00,0.00,0.00,1,1,1,0,20.8,1.002,33.760280,151.280291,6,25
29/06/2017,12:57:10,0.00,0.00,0.00,0.00,1,1,1,0,20.7,1.002,33.760280,151.280291,6,31
29/06/2017,12:57:16,0.00,0.00,0.00,0.00,1,1,1,0,20.7,1.002,33.760280,151.280291,6,37
29/06/2017,12:57:22,0.00,0.00,0.00,0.00,1,1,1,0,20.6,1.003,33.760280,151.280291,6,43
29/06/2017,12:57:28,0.00,0.00,0.00,0.00,1,1,1,0,20.7,1.003,33.760280,151.280291,6,49
29/06/2017,12:57:34,0.00,0.00,0.00,0.00,1,1,1,0,20.7,1.004,33.760280,151.280291,6,55
29/06/2017,12:57:40,0.00,0.00,0.00,0.00,1,1,1,0,20.8,1.004,33.760280,151.280291,6,61
siliconchip.com.au
So those log entries show that the
new sensor is working, giving us an
indoor temperature reading of just
over 20°C and a pressure of just over
1 bar. This modified sketch, titled
Arduino_Data_Logger_Barometer.
ino, is supplied in the download
package.
SC
September 2017 91
Logging data to the ’net
using Arduino
This circuit and software show how
you can easily log data to the cloud
from a remote location, using an
ESP8266-based Arduino module.
By Bera Somnath
ThingSpeak.com is a website supporting open source software on the
“Internet of Things”. It’s basically a repository for remotely logged data that
you can access to download your sensor data at any time. This circuit and
software show how you can log data to
it at a remote location easily, using an
ESP8266-based Arduino-type module
and retrieve it over the internet later.
The ESP8266 is a chip which combines a powerful ARM processor with
a WiFi transceiver and antenna. We’re
using a WeMos D1 R2 which is compatible with the Arduino IDE but instead
of an Atmel ATmega processor, it uses
the ESP8266. It’s a low-cost device
that’s readily available and contains
everything you need to communicate
over WiFi.
The parts required for this sample
project can be acquired for under $20
and the result is a battery-powered device which measures its local temperature and humidity and then uploads
them periodically to ThingSpeak.com
You can view the logged results at any
time using your PC.
Setting up an account
Before using ThingSpeak you need
to sign up for an account and “open a
channel” for your logging device. To
do this, you need a working email address. Once registered, you can create
as many channels as you need. Simply
go to https://ThingSpeak.com and follow the instructions to register and set
up a channel.
Each channel has a channel ID,
a “write” API key and a “read” API
key. Note these down as we will need
them later.
Each channel can contain up to eight
streams of data. You can then assign
names to these streams. Our example
92 Silicon Chip
will log temperature and humidity
from a DHT-22 sensor, so name the first
two “temperature” and “humidity”.
Configuring the WeMos board
Fig.1 shows how we connect the
DHT22 sensor to the WeMos board,
along with a lithium rechargeable battery to power it and a small OLED display so we can see the current status.
If you were to position one or more of
these modules remotely, having gotten
them working, you wouldn’t need to
connect the display.
Communication with the DHT22 is
over a single-wire bus and this data
pin is connected to digital I/O pin
D5 of the WeMos module. The OLED
display is driven via an I2C serial bus
and this is wired to the hardware SCL
(clock) and SDA (data) pins, D1 and
D2, of the WeMos board. Both modules run off the same 3.3V supply as
the WeMos module.
Not only does the WeMos ESP8266
board have onboard WiFi, saving you
the hassle of connecting a shield for
this task, as noted earlier, its processor
is faster and it also has more memory.
We got ours from AliExpress for less
than $5.
Having installed the latest version
of the Arduino IDE on your computer
(if you didn’t have it already), you will
need to enable support for ESP8266based boards. Open up preferences
in the IDE and under “Arduino Board
Manager URLs”, enter:
http://arduino.esp8266.com/stable/
package_esp8266com_index.json
Hit OK, then go to Tools → Boards
→ Board Manager, type in “esp8266”
in the search box, click on the entry
which appears below and then click
on the “Install” button. This will result
in around 160MB of compilers and associated files being downloaded and
installed on your computer.
You can now go to the Tools → Board
menu and select the “WeMos D1 R2 &
mini” entry from the drop-down list.
You will then need to install three
The data logger was built using a small breadboard for the extra parts with
the Li-ion battery sitting underneath the WeMos board. Otherwise, most
connections were made using flying leads.
siliconchip.com.au
Arduino libraries: DHT, OneWire and
thingspeak-arduino. All three are supplied in the download package from
the Silicon Chip website, which also
includes the sketch itself.
Then install these libraries using the
Sketch → Include Library → Add .ZIP
Library option, if you didn’t have them
already. You will then need to open
up the sketch and modify it so that it
can connect to your WiFi network and
your ThingSpeak channel.
Change the ssid[] and pass[] strings
to suit your WiFi network and the myChannelNumber and myWriteAPIKey
strings to match those you noted earlier when setting up your ThingSpeak
account. You can then compile/verify
the sketch and it’s ready to be uploaded
to the WeMos board.
Having wired up the circuit as
shown, with the battery disconnected, plug the WeMos board into your
PC via USB, ensure the Arduino IDE
is configured to use the correct port
and then upload the sketch. It should
spring into life straight away.
Once working, you can add more
sensors later, which can be logged to
the six spare streams in your channel.
The software
The code is broadly divided into a
few parts. The first few lines include
the relevant headers, then create instances of the WiFi, DHT, OLED and
ThingSpeak.com objects. The setup
function initialises these objects by
calling the begin() method then inside
the main loop, it retrieves the temperature and humidity from the sensor and
then transfers the data to ThingSpeak.
com at thirty-second intervals.
The entire code is less than 70 lines,
including the comments. If you eliminate the OLED-related lines, fewer
than 30 remain.
If you look at the code, you will see
the following lines:
ThingSpeak.writeField(
myChannelNumber, 1, h,
myWriteAPIKey); delay(15000);
// ThingSpeak will only accept
updates every 15 seconds.
ThingSpeak.writeField(
myChannelNumber, 2, t,
myWriteAPIKey); delay(15000);
// ThingSpeak will only accept
updates every 15 seconds.
Fig.1: block diagram showing the connections required to and from the WeMos
module. The OLED module isn’t required for it to run, and is used more as a
convenience during set-up and debugging.
tion calls add a pause of fifteen seconds
between each transmission.
Once you declare a channel “public”, it will have a URL which is accessible to all. Just by clicking that URL,
anybody can view the channel. Otherwise, for a private channel, you have
to log on to see that channel’s output.
Power Consumption
While active, the unit draws around
80mA but most of this is the WiFi
chipset. To reduce overall power con-
sumption, the WiFi interface is put to
sleep when not needed, reducing idle
power consumption to 22mA, giving
an average of around 30mA. If the optional OLED display is used, that adds
another 40mA.
Without the OLED display, the
device can run for hours on a small
LiFePO4 cell.
We recommend you use this type
of rechargeable cell since its normal
voltage range is close to the 3.3V that
SC
the WeMos board requires.
An example shot showing what kind
of data you can expect to see when the
software is up and running.
These are responsible for uploading
the sensor data to your ThingSpeak.
com channel. The intervening funcsiliconchip.com.au
September 2017 93
Using Cheap Asian Electronic Modules Part 9: by Jim Rowe
The AD9850 DDS Module
In the April issue, we covered the AD9833 Direct Digital Synthesiser
(DDS) chip. This time, we’re looking at modules based on its big
brother, the AD9850. Typically combined with a 125MHz crystal
oscillator, it can be programmed to produce sinewaves to beyond
40MHz, possibly accompanied by a square or pulse waveform. It is
again controlled via an SPI serial interface.
W
e won’t explain how a DDS chip
works again as we covered that
quite thoroughly in the article mentioned above, in the April 2017 issue.
There are a couple of modules using
the AD9850 chip in conjunction with
a 125MHz oscillator, with the one
shown in the photos probably the most
common. The other module is very
similar in most respects, apart from
having a different PCB layout.
In the module shown, the fact
that the AD9850 is coupled with a
125MHz crystal oscillator means that
it can be programmed to produce any
output frequency from 0.0291Hz to
over 62MHz in 0.0291Hz increments
(more about the practical frequency
limits later). This means it has a frequency range about five times that of
the AD9833 with a resolution about
3.4 times finer (0.0291Hz compared
with 0.1Hz).
Although the AD9850 doesn’t provide the same choice of output waveforms as the AD9833, it does offer the
basic sine waveform plus a derived
rectangular waveform with bipolar
outputs and an adjustable duty cycle.
This allows it to produce anything
from narrow positive pulses through
to a square wave to narrow negative
pulses.
The AD9850 chip itself is a little
larger than the very tiny AD9833,
but is still quite small. It comes in a
28-pin SSOP package, operates from
either 3.3 or 5V and is described as
low power – dissipating just 380mW
when running with a 125MHz master
clock from 5V, or only 155mW when
operating from a 3.3V supply with a
110MHz master clock.
94 Silicon Chip
The AD9850-based module shown
in the photos, which measures only
44.5 x 26mm and includes a 125MHz
crystal oscillator, is currently being offered on eBay and AliExpress for prices ranging from A$9.80 to A$22.50, in
many cases with postage included.
Inside the AD9850
The block diagram of Fig.1 shows
what’s inside that compact 28-pin
SSOP package. The main sections
involved in basic DDS operation are
those shown with a pale yellow fill.
The high speed comparator at lower
right is used for deriving the rectangular/square output waveform, as we’ll
see shortly.
Down at lower left is the 40-bit input
register where data and instructions
are loaded into the chip from almost
any micro. With the AD9850, this can
be done in two ways; in serial fashion
via an SPI (Serial Peripheral Interface)
The AD9850 module shown at approximately twice actual size.
siliconchip.com.au
bus like the AD9833, or by parallel
loading via an 8-bit data bus.
Since the AD9850 needs a 40-bit
word rather than two 14-bit words, this
means that programming it gets a little
more complicated than the AD9833.
With serial loading via the SPI bus,
all 40 bits must be sent in sequence,
while with parallel loading they must
be sent as a sequence of five bytes (8bit words). In both cases, they must be
sent to the chip in a particular order
(LSB first) and with the 32-bit frequency word sent before the 8-bit control/
phase word.
Returning to Fig.1, just above the
input register is the frequency/phase
data register, also of 40 bits. This stores
the data used to program the DDS in
terms of output frequency and phase
modulation (if any).
Once the data has been loaded into
the input register either serially or as
five bytes, it is transferred into the
frequency/phase register with a single
positive-going pulse to the Frequency
Update (FQ_UD) pin.
The high speed DDS “heart” of the
AD9850 is shown at upper left in Fig.1,
with its 125MHz master clock input
labelled “Ref Clock Input”. Then to
the right of the DDS block is the very
fast 10-bit DAC (digital to analog converter), used to provide the AD9850’s
main sinewave output. Note that the
use of a 10-bit DAC gives the device
a sinewave amplitude resolution of
1024 levels.
The complete module
Now turn your attention to Fig.2,
which shows the complete circuit for
the 44.5 x 26mm module shown in
the photos. It has quite a few components, comprising the AD9850 DDS
chip (IC1) and its equally small (6.5
x 4.5mm) 125MHz crystal oscillator,
a red power LED, seven SMD resistors, 14 SMD capacitors, three SMD
inductors and a small trimpot.
10-way SIL connectors CON1 and
CON2 provide all the signal and power
connections to the module. Most of
the pins of CON1 are used for the 8-bit
parallel data input (apart from pin 1
for +5V power and pin 10 for ground),
while the pins of CON2 are used for
the SPI serial interface and the analog
outputs.
Note that pin 25 of IC1 is both D7,
the most significant bit of the parallel
input (via pin 9 of CON1) and also the
serial data (SDA) line of the SPI intersiliconchip.com.au
face (pin 4 of CON2).
As shown on Fig.1, the AD9850’s
DAC has bipolar outputs and these
emerge via pins 21 and 20, as shown
in Fig.2. But only one of these is actually used within the module – the
positive output from pin 21. The signal from this output passes through
a low-pass filter formed by the three
small inductors and their accompanying low-value capacitors, to remove
as much of the DAC noise as possible
before the output signal passes to pin
10 of CON2.
The negative DAC output from pin
20 is simply terminated in a 100W load
and fed directly to pin 9 of CON2,
without any filtering. So if you want
to use this output, it will need external filtering.
One more thing to note regarding
the AD9850’s DAC is that its full-scale
output current is set by the value of
the resistor connected between pin
12 (DAC RSET) and ground. With the
3.9kW resistor supplied in the module, the full-scale output current is
10mA, which with the loading of approximately 100W gives a DAC output
close to 1V peak-to-peak. This should
be suitable for the majority of applications.
As well as going to pin 10 of CON2,
the filtered positive DAC output is also
connected to the positive input of the
AD9850’s high speed comparator (pin
16), via a 1kW resistor. The negative
input of the comparator (pin 15) is fed
with an adjustable DC voltage from
the 10kW trimpot, the ends of which
This photo of the underside of the
AD9850 DDS module shows the pin
header connections that can be used
with a Micromite or Arduino.
are connected to the +5V power rail
and ground.
The trimpot thus provides a simple
way to adjust the duty cycle of the rectangular output waveforms derived
from the filtered positive DAC output
by the action of the comparator. The
rectangular outputs emerge from pins
14 and 13, and are taken directly to
pins 7 and 8 of CON2.
Fig.1: internal block diagram of the AD9850 IC. This is somewhat simpler than
the AD9833 featured previously as it has no facility to generate a triangle wave
nor a square wave. However, the internal high-speed comparator at lower right
can be used to generate a fixed or variable duty cycle square wave derived from
the sinewave output and a DC reference voltage.
September 2017 95
From left to right: 10kHz, 100kHz, 1MHz, 10MHz waveform outputs from the AD9850 DDS module. The 25MHz and 40
MHz output graphs are shown overleaf.
Note that the comparator outputs
are both bipolar and symmetrical, ie,
they are always mirror images of each
other, regardless of the duty cycle setting set by the 10kW trimpot.
Practical limitations
As with the AD9833, the main limitation of this module regards the maximum frequency that it can produce.
In theory this is equal to the Nyquist
frequency, or half the sampling clock
frequency; in this case, 125MHz ÷ 2
or 62.5MHz.
But you need to bear in mind that
because of the way a DDS works, the
“sinewave” that it produces at this frequency will have very high distortion.
If you want to get a reasonably smooth
sinewave output, this will only be possible at frequencies below about 20%
of the clock frequency, or in this case,
a maximum of about 25MHz.
If you can tolerate a moderate
amount of distortion, it should be
possible to get nominal sinewaves at
frequencies up to about 40-50MHz.
That’s why the module pictured is
usually advertised as being capable
of delivering sinewaves up to “40MHz
and above”.
Programming it
Although the AD9850 is capable of
being programmed by a parallel loading sequence of five bytes, we’re going to concentrate on the SPI interface
since it involves only five wires between the micro and the module, rather
than the 11 wires needed for parallel
loading; with most micro-based projects, it’s easy to run out of free pins.
Fig.2: circuit diagram for the AD9850-based DDS module. Besides the DDS IC and 125MHz crystal oscillator used to
derive its output frequency, the main point of interest is the 7th order low-pass elliptic filter formed by three SMD
inductors and a few small ceramic capacitors. This has a corner frequency close to 100MHz and a rapid fall-off, to
reject the 125MHz+ switching artefacts from the DAC while leaving the generated signal largely untouched.
96 Silicon Chip
siliconchip.com.au
While the AD9850 doesn’t provide a direct way to produce a triangle or square wave, a fixed or variable duty cycle square
wave can be derived from a generated sinewave plus a DC reference voltage using the internal comparator.
We have summarised the basic
coding for the frequency, control and
phase registers graphically in Fig.3.
The 40 bits making up the serial word
are shown in a line along the top of
the diagram, with the 32 frequency
programming bits (red tint) on the left,
followed by the three control bits and
the five phase programming bits (blue
tint) on the right.
The entire 40 bits must be sent to
the AD9850 “LSB first”, ie, B0, B1, B2,
B3 and so on, right up to B39. When
all 40 bits have been shifted into the
AD9850’s data input register, a short
positive pulse is applied to the chip’s
FQ_UD/SS pin (pin 3 of CON2 in
Fig.2), to load the data into the frequency/phase data register.
If you decide to use parallel loading instead of serial loading, the main
difference is that you have to present
bits B0-B7 to pins 2-9 of CON1 first,
followed by a pulse to the W_CLK pin
(pin 2 of CON2). Then you repeat this
with bits B8-B15, B16-B23, B24-31 and
finally B32-39.
Only after all five bytes have been
loaded do you then need to apply a short
positive pulse to the FQ_UD/SS to load
it all into the frequency/phase register.
The formula to determine the DDS
output frequency from the 32-bit frequency word is shown at bottom left
in Fig.3. With a 125MHz clock and a
32 bit frequency word, the AD9850
has a minimum output frequency of
0.02910383Hz and this is also the
minimum frequency increment. So
the output frequency Fout = ΔPhase ×
0.02910383. Or if you prefer, ΔPhase =
Fout ÷ 0.02910383.
For most purposes, you won’t really
have to worry about the final eight bits
of that 40-bit programming word, because as you can see bits B32, B33 and
B34 should be set to zero for normal
operation, while bits B35-B39 should
also be set to zero if you don’t want to
perform phase modulation.
So now we just need to connect the
module up to our microcontroller.
Note that we’re only going to do that
using the SPI serial interface.
Driving it from an Arduino
There isn’t much to it, as shown in
Fig.4. Most of the connections can be
made via the 6-pin ICSP header. These
connections are quite consistent over
just about all Arduino variants, including the Uno, Leonardo and Nano, the
Freetronics Eleven and LeoStick, and
the Duinotech Classic or Nano.
The only connection that’s not available via the ICSP header is the one
for SS/CS/FQ_UD, which needs to be
connected to the IO10/SS pin of an
Arduino Uno, Freetronics Eleven or
Duinotech Classic as shown.
With other Arduino variants, you
should be able to find the corresponding pin without too much trouble and
even if you can’t, the pin reference can
be changed in your software sketch
to match the pin you do elect to use.
One thing to bear in mind when
you’re writing your own sketch to
program the AD9850 module is the
requirement for the 40-bit programming word to be sent LSB first, instead
of the usual MSB first.
And because the serial data on the
SDATA/MOSI line is clocked into the
chip on the rising edges of the SCLK
pulses and SCLK must idle low, this
means you need to set the SPI Settings
parameters like this:
SPISettings(5000000, LSBFIRST,
SPI_MODE0)
(where that first parameter is the serial clock frequency). Also, since the
Fig.3: format for loading frequency, phase and control data into the AD9850. 40 bits of data are shifted into the IC,
least significant bit (LSB) first, with the first 32 bits setting the frequency, the next three bits controlling the powerdown (sleep) mode and the final five bits setting the phase.
siliconchip.com.au
September 2017 97
You can see that once the frequency exceeds ~25MHz, a fair amount of distortion is introduced into the output.
FQ_UD input of the AD9850 is active
high, this line should be programmed
to idle in the low state and only go high
for loading the data into the AD9850’s
frequency/phase register.
If this sounds confusing, please refer
to the example Arduino sketch I have
written; more about this shortly.
Driving it from a Micromite
It’s also quite easy to drive the module from a Micromite, using the connections shown in Fig.5. By connecting the MOSI, SCK and SS/FQ_UD
lines to Micromite pins 3, 25 and 22
as shown, MMBasic’s built-in SPI protocol commands will have no trouble
in communicating with the module.
Again, there is just one small
complication, brought about by the
AD9850’s need to have the data sent
to it LSB-first.
As MMBasic’s SPI commands only
have provision for MSB-first data
transmission, your program needs to
reverse the bit order before it’s sent
to the DDS.
You’ll see one way of doing this in
my example program for the Micromite, discussed below.
Note that if you’re using the Micromite LCD BackPack, because the LCD
touchscreen also communicates with
the Micromite via its SPI port, your
program needs to open the SPI port immediately before it sends commands or
data to the module and then close the
port again immediately afterwards to
prevent any SPI conflicts. This is also
illustrated in my example MMBasic
program.
Programming examples
The sample program for Arduino is
called “sketch_for_testing_AD9850_
DDS_module.ino”. This simple program initialises the AD9850, programs
it to generate a 100kHz sinewave, then
informs you of the current frequency
via the Serial Monitor utility built into
the Arduino IDE.
Fig.4: as with many of the modules we’ve examined in this series of articles, connecting the AD9850 DDS module to an
Arduino is quite simple. All you have to do is connect the 5V, GND and SPI signals to the ICSP header on the Arduino,
leaving just the slave select (SS) pin which normally goes to I/O pin 10.
98 Silicon Chip
siliconchip.com.au
At the same time, it gives you the
opportunity to type a new frequency
into the Serial Monitor and if you respond by typing in a new frequency
and clicking on the Send button, it
will load the new frequency into the
AD9850 and repeat the process.
It’s pretty straightforward, but it
should demonstrate the basics of controlling the AD9850 DDS module from
an Arduino.
The other program is written for
the Micromite LCD BackPack and is
called “Simple AD9850 sig gen.bas”.
This one is a little more complicated,
partly because of the need to control
the program’s operation via the LCD
touchscreen and partly because of the
need to reverse the bit order of the 40
bits of data sent to the AD9850 because
of its LSB-first requirement.
It again lets you control the AD9833’s
output frequency, in this case by using buttons and a virtual keypad on
the BackPack’s touchscreen. It’s quite
easy to drive and again, should show
you how the AD9850 can be controlled
via a Micromite.
Both of these programs are available
from the Silicon Chip website (www.
siliconchip.com.au).
SC
siliconchip.com.au
Fig.5: again, wiring up this module to a Micromite is pretty straightforward.
Check the instructions for your Micromite to determine the MOSI and SCK
pins; as shown here, for the 28-pin Micromite and LCD BackPack, these go
to pins 3 and 25. That just leaves 5V, GND and the slave select pin, which in
this case we’ve wired to pin 22.
September 2017 99
Vintage Radio
By Ian Batty
The 3-transistor
Philips MT4 Swingalong
The Philips MT4 is
quite an unusual
set and not only
for its minuscule
transistor count. It
is styled as a mantel radio but being
battery-operated
and quite compact, it can easily
double as a portable. Perhaps its most interesting aspect is
that it is a reflex superheterodyne circuit which means that one
section handles both RF and audio signals.
I seem to be getting a reputation as
an enthusiast for interesting and unusual radios. This set was offered to me
for review by a fellow member of the
Historical Radio Society of Australia
(HRSA), Ron Soutter.
It has to be the most minimal set
I’ve looked at so far. Forget 7-transistor sets such as the Stromberg-Carlson
78T11 (Silicon Chip, July 2015, www.
siliconchip.com.au/Article/8710) or
the Philips 198 (June 2015, www.
siliconchip.com.au/Article/8612) or
the many 6-transistor sets I’ve looked
at. And let’s set aside Astor’s 5-transistor M5 and the 4-transistor GE 2105
that, despite having only four transistors, could certainly hold its own.
The Philips MT4 Swingalong uses
just three transistors! And surprisingly,
it works pretty well. Add in its price
100 Silicon Chip
of around $410 in today’s money (actually £14.10s.6d in 1965) compared
to a 7-transistor set at some $560 and
I could imagine the Swingalong walking off the shelves.
First impressions of the MT4
I’m beginning to think I really have
been too serious with my emphasis
on performance measurements. With
just three transistors, the MT4 is able
to compete with five, six and 7-transistor sets for ordinary listening in
the suburbs.
It may also work OK in the country
but I’ve moved down the Peninsula
to Rosebud. That said, I am still some
75km from the transmitter; not much
closer than the previous 95km or so.
I’m getting good reception in the
kitchen and even from some of the
more remote stations such as 3WV in
Horsham, broadcasting on 594kHz,
are just detectable out of doors. Close
examination of the dial shows city
stations in all states but a smaller roll
call of regionals of the day. Perhaps
it’s a de facto admission of the MT4’s
modest sensitivity. We’ll find out how
good it is later.
We’re familiar with the “sinking
ship” school of engineering by now,
as in “get rid of anything which is
not absolutely necessary”. But how is
anyone going to get any kind of performance with only three transistors?
There’s only one way to do it and the
Philips MT4 resurrects an idea from
the valve days: reflexing. The idea is
simple; use one (or more) amplifying
stages simultaneously at two widelydiffering frequencies.
siliconchip.com.au
Maybe the inspiration behind the nickname “Swingalong” came from a Frank
Sinatra song or perhaps a Canadian music TV show of the name. But no
matter the source, the name was on the rear of the MT4’s plastic case.
The idea became public over 100
years ago with the 1914 awarding of
US patent US1087892 to Schloemilch
and von Bronk. Note that this is still
a superheterodyne set, with a self-oscillating converter stage feeding an IF
(intermediate frequency) transformer
and then a stage which handles both
the modulated 455kHz intermediate
frequency and the demodulated audio signal.
Reflexing has been popular at various times. Early sets, with valves costing as much as a week’s wages, had to
offer useful performance at a price that
listeners could afford. Reflexed stages
cut cost but they need careful design,
and the “minimum volume” problem
bedevilled valve designs for years.
The effect is caused by signal rectification at the grid of the reflexed IF amplifier in addition to the demodulator
diode. The grid-rectified signal commonly acts in anti-phase to the audio
coming back from the demodulator.
This gives the counter-intuitive effect that, since the two audio signals
are in opposition; turning the volume
control to zero (i) eliminates the audio
from the demodulator, but (ii) still allows any grid-rectified signal to be
amplified. Typically, it’s not until the
control is advanced “a little” from zero
that complete cancellation – and thus
zero volume – occurs.
Some valve radios (such as Astor’s
Aladdin FG, reviewed in August 2016)
did use reflexing and seemed to have
eliminated the problem.
But how about reflexing in transistor radios? This is the first such set
I’ve come across, though I have seen
a few circuit drawings also using resiliconchip.com.au
flexing. The design itself is pretty simple. Converter TR1, an alloy-diffused
PNP germanium OC169/AF117, uses
conventional combination biasing and
collector-emitter feedback.
This design allows signal injection
into the base, simplifying fault-finding
and alignment. While converters using collector-base feedback work just
fine, it’s common to find that injecting
a tests signal to the base stops the local
oscillator dead.
The converter stage first feeds the
first IF transformer and then the oscillator coil. This is the reverse of the
usual arrangement, but it seems to
work just as well. By the way, as was
the usual practice with early transistor
radios which mostly used PNP germanium transistors, the chassis is positive, not negative. This aspect can be
confusing when you are working your
way through the circuit.
The ferrite aerial rod is a full-length
type, so I expected fairly good signal
pickup. Usually, there’s about a 10:1
ratio, meaning that a field strength of,
say, 500µV/m gives about 50µV signal
at the converter base.
The 2-section tuning gang is a cutplate design. Don’t let the identical
shape of the moving plates in both
sections fool you, as it’s the stationary plates that differ in shape, to give
good tracking between the oscillator
(C3) and aerial tuning (C1) without
the use of a padder capacitor. First IF
transformer L6/7-L8 uses the familiar
tuned, tapped primary and untuned,
untapped secondary.
Reflexed second stage
It’s the circuit around TR2, another
OC169/AF117, that is unusual. First,
volume control R5 attenuates the IF
signal from the first IFT’s L8 secondary as it is turned down. We’ve seen
this approach with the Astor Aladdin
FG, where the reflexed second IF stage
also had the volume control in the IF
signal path.
This approach should eliminate the
minimum-volume effect and it’s notable that Langford Smith (writing in
Radiotron Designer’s Handbook, 4th
edition) shows the volume control in
the audio path between the demodulator and the grid of the reflexed stage
(it’s a contrast to this set and the FG).
Langford Smith’s design would permit
grid rectification and thus accentuate
the minimum volume effect.
Setting the volume control’s IF attenuation aside, TR2 works as expected. Bias is supplied through a
high-value base resistor (R4, 120kW)
and is balanced by the AGC voltage
fed back from demodulator diode D1
via the 8.2kW resistor, R6. There’s one
wrinkle: TR2’s 33W emitter resistor
has no bypass capacitor, so emitter
degeneration slightly reduces the gain
of the stage.
TR2’s collector feeds the second
IFT’s primary, L9/10, which form a
tuned, tapped winding. Untapped,
untuned secondary L11 feeds IF signals to demodulator D1, a germanium
OA71. D1 feeds AGC voltage and the
demodulated audio back to the base
of TR2. Since R6 would attenuate the
audio markedly, it’s shunted for audio signals by the 220nF capacitor C9.
A close-up of the dial shows that it
had station markings for all of the
Australian states.
September 2017 101
Fig.1: the circuit of the Philips MT4 is quite unusual in that the second stage involving transistor TR2 is reflexed. This
means that it amplifies the 455kHz intermediate frequency as well as the recovered audio from diode D1. This approach
enabled good gain with only a limited transistor count.
Now, TR2 is set up as an audio amplifier (even though it also amplifies
the IF signal). First, volume control R5
will have little effect on audio gain (in
theory), as it’s shorted (for audio) by
the 1st IFT’s low-resistance L8 secondary; more on this later.
So TR2 gets the demodulated audio
on its base and the amplified audio
signal appears at its collector. Its
audio load is the 1kW resistor, R8.
Any IF signal appearing across R8
is shunted by 10nF capacitor C11
and the audio signal is fed via 10µF
capacitor C12 to the base of output
transistor TR3, an alloyed-junction
OC74.
TR3 is a conventional Class-A stage,
drawing a constant 13mA of collector
current. This is a lot more than a comparable Class-B push-pull stage with
no signal, and is why the set uses the
large 276P battery.
It’s around 51 x 63 x 80mm. The
original battery (with a capacity of
1500mAh) would give some 100-plus
hours of playing time; modern equivalents would approach 500 hours.
With a supply voltage of 9V, TR3 dissipates about 115mW. Theory implies
that the maximum output power could
be around 50mW, so can its Class-A
stage do much better than previous
review sets? We will see.
TR3 drives the primary of output
transformer L12-L13, which in turn
drives the 3W speaker. Finally, there’s
negative audio feedback from the
speaker to the base of the IF/audio
amplifier, TR2, via 180kW resistor R13.
102 Silicon Chip
Alloy-diffused transistors
As described in my article on the
Grundig Taschen Transistor Boy (December 2016, www.siliconchip.com.
au/Article/10485), Philips began
transistor production with the second generation of junction transistor
technology – alloyed junctions. While
these could reliably produce the trusty
OC44/45 RF/IF transistors, an operating frequency of some 15MHz was
about the limit.
The problem – as it has been since
Bardeen and Brattain’s first examples
– was to get the active base region as
thin as possible. Alloying, relying as
it does on two mutually-dissolving
materials (a bit like lead and tin in
solder) could not produce base layers
fine enough for very high-frequency
operation.
The third generation of transistors
combined established alloying techniques with the newer principle of
diffusion at near-melting temperatures. Diffusion of a gas, or a metal
vapour, can be made to progress into a
substrate more slowly and with much
greater control.
Construction began by working just
one side of the transistor die. The bottom side would become the collector
(let’s say P-type) and the N-type base
This diagram shows the steps to
produce analloy-diffused transistors.
layer would be diffused from the top
down into the collector. So far, we
would just have a very good diode.
But now, placing a P-type dot onto
the base surface and using alloying,
the emitter could be formed on top of
the base layer, giving the familiar PNP
“sandwich” construction. Alloy-diffused OC169/170/171 transistors were
used in the front ends of FM tuners,
and the 175MHz AF118 was used as
a video amplifier.
Diffused-alloy transistor construction is a bit of a mix-and-match, but (i)
it gets away from the messy “two-sided” manufacturing of purely-alloyed
devices and allows greater automation,
and (ii) the combination of diffusion
and alloying finally produced transistors such as the AF186, able to work
to over 800MHz.
Clean-up and alignment
I received the set in good condition.
Apart from a cabinet clean and a contact spray for the noisy volume pot, it
was ready for the test bench and the
photo session.
Some restorers prefer to leave sets
“as is”, unless the performance is obviously lacking. But every set I’ve reviewed so far has benefited from a basic alignment. Original factory settings
may have been a bit less than optimal
and it’s normal for the alignment to
drift over many decades.
This set responded to local oscillator adjustment at the bottom end, with
sensitivity coming up some 2~3 times.
The IFTs came out spot on.
siliconchip.com.au
The Philips MT4 was equipped with a full-size ferrite rod antenna which ensured good signal pickup. The PCB on
the left was quite compact given the relative complexity of the circuit. The large space on the right accommodated the
Eveready 276P battery which gave somewhat more than 100 hours of life.
The audio injection of 20mV at
TR2’s base may seem high. As usual,
I’ve relied on my generator’s output
meter rather than the actual injection
voltage, as readers may not have audio
millivoltmeters to hand that would
allow measurement of actual audio
levels during testing. I did check the
circuit voltages, and found around
7mV at TR2’s base and 35mV at TR3’s
base. That’s more in line with the signal levels in other sets.
I found the antenna and oscillator
trimmers, on the “inside” end of the
gang and hidden behind the ferrite
rod bracket, very difficult to access.
I’d have (i) spun the gang around 180º
or (ii) used a gang with trimmers on
the other end.
How good is it?
It’s certainly not in the same league
as the earlier Philips 198; almost nothing is. But it’s a creditable performer
given its simplicity. As described below, maximum output is under 20mW,
so all testing was done at 10mW output.
Sensitivity (10mW output) is
1.6mV/m at 600kHz, 1mV/m at
1400kHz, and it achieves these figures
with better than 20dB signal-to-noise
ratio. These figures reflect the lower
RF/IF gain caused by a single IF stage
not amplifying converter noise as
siliconchip.com.au
much as a two-stage IF channel does.
The AGC is rudimentary; output increased by 6dB for an input rise of only
15dB, after which output fell rapidly
as the converter overloaded.
IF bandwidth is ±1.3kHz at 3dB
down. Testing it at -60dB was impractical, however, it did show a -30dB
bandwidth of some ±12kHz; again
confirming its simplified IF channel
configuration.
Audio response from the volume
control to speaker is about 240Hz to
8kHz with a 2dB peak around 1kHz.
It’s another set that could have used
some top cut. From aerial to speaker
it’s 200Hz to 1.9kHz. Distortion at
10mW is creditably low at 2.5%, but
it rises rapidly, reaching 10% and clipping at around 15mW output.
The volume control does have most
effect on the IF signal, as full rotation
of the pot only reduced the audio gain
by some -3dB. It’s essentially an IF
attenuator rather than an audio one.
With a collector current of some
13mA, the output stage only manages some 15mW out while drawing
around 115mW from the battery, so
the output stage efficiency is only
around 15%. It’s another example of
real-world output stages failing to approach Class A’s theoretical maximum
of 50% efficiency.
Against this, the converter’s best
sensitivity of some 180µV, for an air
field of only 1mV/m, shows efficient
coupling from the antenna rod to the
converter base.
How good is it? Like the GE T2105,
it’s a good performer in just about
every setting. Having described the
GE T2105 as cheap and cheerful, I’m
going to tag the MT4 similarly – budget designs can work and quite well.
Whoever designed this set did some
pretty clever engineering, combining
adequate performance with minimum
complexity.
Would I buy one?
This set will go back to its generous
owner but I’d like to have an example.
It’s a good performer and a reminder
of how much performance a fine engineering team can get out of simple
circuitry. And yes, one showed up at
the HRSA’s Radio Market in June at a
great price. Not a member?
Go to www.hrsa.asn.au and take up
the invitation.
Further reading
My special thanks to Ron Soutter of
the HRSA for the loan of his set and
the original circuit diagram, which I
have redrawn (Fig.1).
You’ll also find the MT4 on Ernst
Erb’s Radiomuseum: www.radiomuseum.org/r/philipsaus_mt_4.html SC
September 2017 103
SILICON
CHIP
.com.au/shop
ONLINESHOP
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Or a pre-programmed micro? Or some other hard-to-get “bit”? The chances are they are available direct from the SILICON CHIP ONLINESHOP.
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PRE-PROGRAMMED MICROS
Price for any of these micros is just $15.00 each + $10 p&p per order#
As a service to readers, SILICON CHIP ONLINESHOP stocks microcontrollers and microprocessors used in new projects (from 2012 on) and
some selected older projects – pre-programmed and ready to fly!
Some micros from copyrighted and/or contributed projects may not be available.
PIC12F675-I/P
PIC16F1455-I/P
PIC16F1507-I/P
PIC16F88-E/P
PIC16F88-I/P
PIC16LF88-I/P
PIC16LF88-I/SO
PIC16LF1709-I/SO
PIC16F877A-I/P
PIC16F2550-I/SP
UHF Remote Switch (Jan09), Ultrasonic Cleaner (Aug10),
Ultrasonic Anti-fouling (Sep10), Cricket/Frog (Jun12), Do Not Disturb (May13)
IR-to-UHF Converter (Jul13), UHF-to-IR Converter (Jul13)
PC Birdies *2 chips – $15 pair* (Aug13), Driveway Monitor Receiver (July15)
Hotel Safe Alarm (Jun16), 50A Battery Charger Controller (Nov16)
Microbridge (May17)
Wideband Oxygen Sensor (Jun-Jul12)
Hi Energy Ignition (Nov/Dec12), Speedo Corrector (Sept13),
Auto Headlight Controller (Oct13), 10A 230V Motor Speed Controller (Feb14)
Automotive Sensor Modifier (Dec16)
Projector Speed (Apr11), Vox (Jun11), Ultrasonic Water Tank Level (Sep11)
Quizzical (Oct11), Ultra LD Preamp (Nov11), 10-Channel Remote Control
Receiver (Jun13), Revised 10-Channel Remote Control Receiver (Jul13)
Nicad/NiMH Burp Charger (Mar14), Remote Mains Timer (Nov14)
Driveway Monitor Transmitter (July15), Fingerprint Scanner (Nov15)
MPPT Lighting Charge Controller (Feb16), 50/60Hz Turntable Driver (May16)
Cyclic Pump Timer (Sep16), 60V 40A DC Motor Speed Controller (Jan17)
Pool Lap Counter (Mar17), Rapidbrake (Jul17)
Garbage Reminder (Jan13), Bellbird (Dec13), GPS Analog Clock Driver (Feb17)
LED Ladybird (Apr13)
Battery Cell Balancer (Mar16)
6-Digit GPS Clock (May-Jun09), Lab Digital Pot (Jul10), Semtest (Feb-May12)
Batt Capacity Meter (Jun09), Intelligent Fan Controller (Jul10)
PIC18F4550-I/P
GPS Car Computer (Jan10), GPS Boat Computer (Oct10)
PIC32MX795F512H-80I/PT Maximite (Mar11), miniMaximite (Nov11), Colour Maximite (Sept/Oct12)
Touchscreen Audio Recorder (Jun/Jul 14)
PIC32MX170F256B-50I/SP Micromite Mk2 (Jan15) – also includes FREE 47F tantalum capacitor
Micromite LCD BackPack [either version] (Feb16), GPS Boat Computer (Apr16)
Micromite Super Clock (Jul16), Touchscreen Voltage/Current Ref (Oct-Dec16)
Micromite LCD BackPack V2 (May17), Deluxe eFuse (Aug17)
Micromite DDS for IF Alignment (Sept17)
PIC32MX170F256B-I/SP
Low Frequency Distortion Analyser (Apr15)
PIC32MX170F256D-501P/T 44-pin Micromite Mk2 (Now with Mk2 Firmware at no extra cost)
PIC32MX250F128B-I/SP
GPS Tracker (Nov13), Micromite ASCII Video Terminal (Jul14)
PIC32MX470F512H-I/PT
Stereo Audio Delay/DSP (Nov13), Stereo Echo/Reverb (Feb 14)
Digital Effects Unit (Oct14)
PIC32MX470F512H-120/PT Micromite PLUS Explore 64 (Aug 16), Micromite Plus LCD BackPack (Nov16)
PIC32MX470F512L-120/PT Micromite PLUS Explore 100 (Sep-Oct16)
dsPIC33FJ128GP802-I/SP Digital Audio Signal Generator (Mar-May10), Digital Lighting Controller
(Oct-Dec10), SportSync (May11), Digital Audio Delay (Dec11)
Quizzical (Oct11), Ultra-LD Preamp (Nov11), LED Musicolor (Nov12)
dsPIC33FJ64MC802-E/P
Induction Motor Speed Controller (revised) (Aug13)
dsPIC33FJ128GP306-I/PT CLASSiC DAC (Feb-May 13)
ATTiny861
Thermometer/Thermostat (Mar10), Rudder Position Indicator (Jul11)
ATTiny2313
Remote-Controlled Timer (Aug10)
When ordering, be sure to nominate BOTH the micro required AND the project for which it must be programmed.
SPECIALISED COMPONENTS, HARD-TO-GET BITS, ETC
NEW THIS MONTH:
3-WAY ADJUSTABLE ACTIVE CROSSOVER
(SEPT 17)
- set of laser-cut black acrylic case pieces $10.00
LOGGING DATA TO THE ‘NET USING ARDUINO
(SEPT 17)
- WeMos D1 R2 board $12.50
DELUXE EFUSE PARTS
(AUG 17)
IPP80P03P4L04 P-channel mosfets $4.00 ec
BUK7909-75AIE 75V 120A N-channel SenseFet $7.50 ec
LT1490ACN8 dual op amp $7.50 ec
P&P – $10 Per order#
POOL LAP COUNTER
(MAR 17)
two 70mm 7-segment high brightness blue displays plus logic-level Mosfet $17.50
laser-cut blue tinted lid, 152 x 90 x 3mm $7.50
STATIONMASTER
(MAR 17)
DRV8871 IC, SMD 1µF capacitor and 100kW potentiometer with detent $12.50
ULTRA LOW VOLTAGE LED FLASHER
(FEB 17)
kit including PCB and all SMD parts, LDR and blue LED
$12.50
(JUL 17)
Geeetech Arduino MP3 shield $20.00
SC200 AMPLIFIER MODULE
(JAN 17)
hard-to-get parts: Q8-Q16, D2-D4, 150pF/250V capacitor and five SMD resistors
$35.00
ARDUINO LC METER
60V 40A DC MOTOR SPEED CONTROLLER
$35.00
ARDUINO MUSIC PLAYER/RECORDER
(JUN 17)
1nF 1% MKP capacitor, 5mm lead spacing
MAX7219 LED DISPLAY MODULES
8x8 LED matrix module with DIP MAX7219
8x8 LED matrix module with SMD MAX7219
8-digit 7-segment red display module with SMD MAX7219
(JUN 17)
$2.50
$5.00
$5.00
$7.50
MICROBRIDGE
(MAY 17)
PCB plus all on-board parts including programmed microcontroller
(SMD ceramics for 10µF) $20.00
(JAN 17)
hard-to-get parts: IC2, Q1, Q2 and D1
COMPUTER INTERFACE MODULES
(JAN 17)
TOUCHSCREEN VOLTAGE/CURRENT REFERENCE
MICROMITE LCD BACKPACK KIT (programmed to suit) PLUS UB1 Lid
LASER-CUT MATTE BLACK LID (to suit UB1 Jiffy Box)
(DEC 16)
CP2102 USB-UART bridge
microSD card adaptor
$5.00
$2.50
MICROMITE LCD BACKPACK V2 – COMPLETE KIT
EFUSE
PASSIVE LINE TO PHONO INPUT CONVERTER - ALL SMD PARTS
(NOV 16)
$5.00
MICROMITE PLUS EXPLORE 100 *COMPLETE KIT (no LCD panel)* (SEP 16) $69.90
(MAY 17)
includes PCB, programmed micro, touchscreen LCD, laser-cut UB3 lid, mounting hardware,
SMD Mosfets for PWM backlight control and all other on-board parts $70.00
(APR 17)
two NIS5512 ICs plus one SUP53P06 $22.50
DDS MODULES
(APR 17)
AD9833 DDS module (with gain control) (for Micromite DDS) $25.00
AD9833 DDS module (no gain control) (El Cheapo Modules, Part 6) $15.00
SHORT FORM KIT with main PCB plus onboard parts (not including BackPack
module, jiffy box, power supply or wires/cables)
$70.00
$10.00
$99.00
(includes PCB, programmed micro and the hard-to-get bits including female headers, USB and microSD
sockets, crystal, etc but does not include the LCD panel)
100dB STEREO AUDIO LEVEL/VU METER
All SMD parts except programmed micro and LEDs (both available separately)
(JUN 16)
$20.00
THESE ARE ONLY THE MOST RECENT MICROS AND SPECIALISED COMPONENTS. FOR THE FULL LIST, SEE www.siliconchip.com.au/shop
*All items subect to availability. Prices valid for month of magazine issue only. All prices in Australian dollars and included GST where applicable. # P&P prices are within Australia. O’seas? Please email for a quote
09/17
PRINTED CIRCUIT BOARDS
NOTE: The listings below are for the PCB only – not a full kit. If you want a kit, contact the kit suppliers advertising in this issue.
For more unusual projects where kits are not available, some have specialised components available – see the list opposite.
NOTE: Not all PCBs are shown here due to space limits but the SILICON CHIP ONLINESHOP has boards going back to 2001 and beyond.
For a complete list of available PCBs, back issues, etc, go to siliconchip.com.au/shop Prices are PCBs only, NOT COMPLETE KITS!
PRINTED CIRCUIT BOARD TO SUIT PROJECT:
PUBLISHED:
PCB CODE:
Price:
DCC REVERSE LOOP CONTROLLER
OCT 2012
09110121 $10.00
CLASSIC-D CLASS D AMPLIFIER MODULE
NOV 2012
01108121 $30.00
CLASSIC-D 2 CHANNEL SPEAKER PROTECTOR
NOV 2012
01108122 $10.00
HIGH ENERGY ELECTRONIC IGNITION SYSTEM
DEC 2012
05110121 $10.00
1.5kW INDUCTION MOTOR SPEED CONTROLLER (NEW V2 PCB)DEC 2012 10105122 $35.00
THE CHAMPION PREAMP and 7W AUDIO AMP (one PCB) JAN 2013
01109121/2 $10.00
GARBAGE/RECYCLING BIN REMINDER
JAN 2013
19111121 $10.00
2.5GHz DIGITAL FREQUENCY METER – MAIN BOARD
JAN 2013
04111121 $35.00
2.5GHz DIGITAL FREQUENCY METER – DISPLAY BOARD
JAN 2013
04111122 $15.00
2.5GHz DIGITAL FREQUENCY METER – FRONT PANEL
JAN 2013
04111123 $45.00
SEISMOGRAPH MK2
FEB 2013
21102131 $20.00
MOBILE PHONE RING EXTENDER
FEB 2013
12110121 $10.00
GPS 1PPS TIMEBASE
FEB 2013
04103131 $10.00
LED TORCH DRIVER
MAR 2013
16102131
$5.00
CLASSiC DAC MAIN PCB
APR 2013
01102131 $40.00
CLASSiC DAC FRONT & REAR PANEL PCBs
APR 2013
01102132/3 $30.00
GPS USB TIMEBASE
APR 2013
04104131 $15.00
LED LADYBIRD
APR 2013
08103131
$5.00
CLASSiC-D 12V to ±35V DC/DC CONVERTER
MAY 2013
11104131 $15.00
DO NOT DISTURB
MAY 2013
12104131 $10.00
LF/HF UP-CONVERTER
JUN 2013
07106131 $10.00
10-CHANNEL REMOTE CONTROL RECEIVER
JUN 2013
15106131 $15.00
IR-TO-455MHZ UHF TRANSCEIVER
JUN 2013
15106132
$7.50
“LUMP IN COAX” PORTABLE MIXER
JUN 2013
01106131 $15.00
L’IL PULSER MKII TRAIN CONTROLLER
JULY 2013
09107131 $15.00
L’IL PULSER MKII FRONT & REAR PANELS
JULY 2013
09107132/3 $20.00/set
REVISED 10 CHANNEL REMOTE CONTROL RECEIVER
JULY 2013
15106133 $15.00
INFRARED TO UHF CONVERTER
JULY 2013
15107131
$5.00
UHF TO INFRARED CONVERTER
JULY 2013
15107132 $10.00
IPOD CHARGER
AUG 2013
14108131
$5.00
PC BIRDIES
AUG 2013
08104131 $10.00
RF DETECTOR PROBE FOR DMMs
AUG 2013
04107131 $10.00
BATTERY LIFESAVER
SEPT 2013
11108131
$5.00
SPEEDO CORRECTOR
SEPT 2013
05109131 $10.00
SiDRADIO (INTEGRATED SDR) Main PCB
OCT 2013
06109131 $35.00
SiDRADIO (INTEGRATED SDR) Front & Rear Panels
OCT 2013
06109132/3 $25.00/pr
TINY TIM AMPLIFIER (same PCB as Headphone Amp [Sept11])OCT 2013
01309111
$20.00
AUTO CAR HEADLIGHT CONTROLLER
OCT 2013
03111131
$10.00
GPS TRACKER
NOV 2013
05112131
$15.00
STEREO AUDIO DELAY/DSP
NOV 2013
01110131
$15.00
BELLBIRD
DEC 2013
08112131
$10.00
PORTAPAL-D MAIN BOARDS
DEC 2013
01111131-3
$35.00/set
(for CLASSiC-D Amp board and CLASSiC-D DC/DC Converter board refer above [Nov 2012/May 2013])
LED Party Strobe (also suits Hot Wire Cutter [Dec 2010])
JAN 2014
16101141
$7.50
Bass Extender Mk2
JAN 2014
01112131
$15.00
Li’l Pulser Mk2 Revised
JAN 2014
09107134
$15.00
10A 230VAC MOTOR SPEED CONTROLLER
FEB 2014
10102141
$12.50
NICAD/NIMH BURP CHARGER
MAR 2014
14103141
$15.00
RUBIDIUM FREQ. STANDARD BREAKOUT BOARD
APR 2014
04105141
$10.00
USB/RS232C ADAPTOR
APR 2014
07103141
$5.00
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MAY 2014
10104141
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MAY 2014
16105141
$10.00
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MAY 2014
18104141
$20.00
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JUN 2014
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JUL 2014
01105141
$12.50
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JUL 2014
99106141
$10.00
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JUL 2014
24107141
$7.50
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JUL 2014
04105141a/b $15.00
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AUG 2014
21108141
$15.00
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AUG 2014
24108141
$5.00
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SEP 2014
23108141
$15.00
OPTO-THEREMIN PROXIMITY SENSOR BOARD
SEP 2014
23108142
$5.00
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SEP 2014
04107141/2 $10/SET
MINI-D AMPLIFIER
SEP 2014
01110141
$5.00
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OCT 2014
05109141
$7.50
DIRECT INJECTION (D-I) BOX
OCT 2014
23109141
$5.00
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OCT 2014
01110131
$15.00
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NOV 2014
18112141
$10.00
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NOV 2014
19112141
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NOV 2014
19112142
$15.00
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NOV 2014
01109141
$5.00
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DEC 2014
04112141
$5.00
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DEC 2014
05112141
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DEC 2014
01111141
$50.00
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DEC 2014
01111144
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DEC 2014
01111142/3 $30/set
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JAN 2015
- $25.00
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JAN 2015
04108141
$10.00
SPARK ENERGY METER MAIN BOARD
FEB/MAR 2015
05101151
$10.00
SPARK ENERGY ZENER BOARD
FEB/MAR 2015
05101152
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FEB/MAR 2015
05101153
$5.00
APPLIANCE INSULATION TESTER
APR 2015
04103151
$10.00
PRINTED CIRCUIT BOARD TO SUIT PROJECT:
PUBLISHED:
APPLIANCE INSULATION TESTER FRONT PANEL
LOW-FREQUENCY DISTORTION ANALYSER
APPLIANCE EARTH LEAKAGE TESTER PCBs (2)
APPLIANCE EARTH LEAKAGE TESTER LID/PANEL
BALANCED INPUT ATTENUATOR MAIN PCB
BALANCED INPUT ATTENUATOR FRONT & REAR PANELS
4-OUTPUT UNIVERSAL ADJUSTABLE REGULATOR
SIGNAL INJECTOR & TRACER
PASSIVE RF PROBE
SIGNAL INJECTOR & TRACER SHIELD
BAD VIBES INFRASOUND SNOOPER
CHAMPION + PRE-CHAMPION
DRIVEWAY MONITOR TRANSMITTER PCB
DRIVEWAY MONITOR RECEIVER PCB
MINI USB SWITCHMODE REGULATOR
VOLTAGE/RESISTANCE/CURRENT REFERENCE
LED PARTY STROBE MK2
ULTRA-LD MK4 200W AMPLIFIER MODULE
9-CHANNEL REMOTE CONTROL RECEIVER
MINI USB SWITCHMODE REGULATOR MK2
2-WAY PASSIVE LOUDSPEAKER CROSSOVER
ULTRA LD AMPLIFIER POWER SUPPLY
ARDUINO USB ELECTROCARDIOGRAPH
FINGERPRINT SCANNER – SET OF TWO PCBS
LOUDSPEAKER PROTECTOR
LED CLOCK
SPEECH TIMER
TURNTABLE STROBE
CALIBRATED TURNTABLE STROBOSCOPE ETCHED DISC
VALVE STEREO PREAMPLIFIER – PCB
VALVE STEREO PREAMPLIFIER – CASE PARTS
QUICKBRAKE BRAKE LIGHT SPEEDUP
SOLAR MPPT CHARGER & LIGHTING CONTROLLER
MICROMITE LCD BACKPACK, 2.4-INCH VERSION
MICROMITE LCD BACKPACK, 2.8-INCH VERSION
BATTERY CELL BALANCER
DELTA THROTTLE TIMER
MICROWAVE LEAKAGE DETECTOR
FRIDGE/FREEZER ALARM
ARDUINO MULTIFUNCTION MEASUREMENT
PRECISION 50/60HZ TURNTABLE DRIVER
RASPBERRY PI TEMP SENSOR EXPANSION
100DB STEREO AUDIO LEVEL/VU METER
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BROWNOUT PROTECTOR MK2
8-DIGIT FREQUENCY METER
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MICROMITE PLUS EXPLORE 64
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AUTOMOTIVE FAULT DETECTOR
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MICROPOWER LED FLASHER
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50A BATTERY CHARGER CONTROLLER
PASSIVE LINE TO PHONO INPUT CONVERTER
MICROMITE PLUS LCD BACKPACK
AUTOMOTIVE SENSOR MODIFIER
TOUCHSCREEN VOLTAGE/CURRENT REFERENCE
SC200 AMPLIFIER MODULE
60V 40A DC MOTOR SPEED CON. CONTROL BOARD
60V 40A DC MOTOR SPEED CON. MOSFET BOARD
GPS SYNCHRONISED ANALOG CLOCK
ULTRA LOW VOLTAGE LED FLASHER
POOL LAP COUNTER
STATIONMASTER TRAIN CONTROLLER
EFUSE
SPRING REVERB
6GHZ+ 1000:1 PRESCALER
MICROBRIDGE
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10-OCTAVE STEREO GRAPHIC EQUALISER PCB
10-OCTAVE STEREO GRAPHIC EQUALISER FRONT PANEL
10-OCTAVE STEREO GRAPHIC EQUALISER CASE PIECES
RAPIDBRAKE
DELUXE EFUSE
DELUXE EFUSE UB1 LID
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APR 2015
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$10.00
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$15.00
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$15.00
MAY 2015
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$20.00
MAY 2015
18105151
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15105151 $10.00
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01107151 $15.00
SEP 2015
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NOV 2015
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DEC 2015
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JAN 2016
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JAN 2017
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FEB 2017
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SEPT 2017
SEPT 2017
PCB CODE:
Price:
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01108172/3 $20.00/pair
LOOKING FOR TECHNICAL BOOKS? YOU’LL FIND THE COMPLETE LISTING OF ALL BOOKS AVAILABLE IN THE SILKS & DVDs” PAGES AT SILICONCHIP.COM.AU/SHOP
PRODUCT SHOWCASE
Freeview Plus TV upgrade
Freeview Australia, a consortium
of free-to-air TV stations, has delivered the new Freeview Plus service
to more than 2.2 million Freeview
Plus-enabled TVs across Australia.
Freeview Plus is designed to make
content discovery easier than ever before, offering a simplified user experience, additional features and a fresh
look and feel.
Freeview Plus is a hybrid digital
television service that provides access to catch-up free-to-air programming on TVs and led the world when
it launched in 2014, winning local
and international accolades for its
ground-breaking technology and user
interface.
There are currently around 2.2 million TV receivers in Australia that are
Freeview Plus-enabled with an 85%
Smartphone
Temperature Datalogger
connection rate.
Key to the upgrade has been the implementation of world’s best practice
interface design which now features
image-based browsing and the introduction of the My TV function.
My TV presents the viewer with image-based carousels including personalised recommendations and viewers’
favourites along with live TV, catch up
and genre-based browsing.
Other Freeview Plus upgrade features include an easy-to-use guide
with backwards navigation to catch-up
content and a simplified Mini Guide
for quick program discovery.
For more information, visit www.
freeview.com.au or view the how-to
video at siliconchip.com.au/l/aaem
New record for LONGi 60-cell Solar Module: 325.6W
LONGi Solar received a test report showing its latest 60 cell Hi-MO1
module achieved a power output of 325.6W under standard testing
conditions (STC) with the conversion efficiency reaching 19.91%.
The module incorporates monocrystalline PERC cells based on
mass production technology with a 21.9% conversion efficiency. The
test was completed at the
Contact:
TUV Rheinland Shanghai
LERRI Solar Technology Co Ltd
Lab with the open-circuit
201, Building 8 Sandhill Plaza, Lane 2290, Zuvoltage and short-circuit chongzhi Rd, Pudong, Shanghai, China
current reaching 40.79V and Tel: (0011) 86 021 6104 7322
10.160A respectively.
Website: http://en.longi-solar.com
Rail-to-rail op amp with inbuilt EMI protection
EMI – electromagnetic interference – is the
bane of engineers and circuit designers
everywhere.
Among a
host of problems, EMI
causes DC errors, increased current
consumption and unwanted tones.
Now Microchip have introduced the
MCP6411, a single, general purpose
op amp offering integrated EMI protection and rail-to-rail input/output
over the 1.7 to 5.5V operating range.
This amplifier has a typical GBWP of
1 MHz, with typical quiescent current
of 50µA. The MCP6411 is available in
SC-70 and SOT-23 packages.
106 Silicon Chip
Integrated EMI protection, when
used with proper circuit/PCB design
techniques, eliminates external components that increase system cost, design complexity and footprint.
Many applications could benefit
from integrated EMI protection, including medical instrumentation, automotive electronics, data acquisition
equipment, battery powered portable
systems, sensor amplification and
conditioning and analog active filters.
You can find the MCP6411 data
sheet at siliconchip.com.au/l/aael
Contact:
Microchip Technology Inc
Unit 32, 41 Rawson St, Epping NSW 2121
Tel: (02)9868 6733 Fax: (02) 9868 6755
Website: www.microchipdirect.com
The new TagTemp-S,
from Novus Automation, is a cost-effective data logger recommended for use in
warehouse and
transportation
applications.
It is an IP65
rated sealed
unit with a
temperature
range of -30 to 60°C and can operate for
2 years at a 5-minute acquisition interval.
It can store up to 4020 readings.
The stored data is transferred through
a smartphone equipped with an embedded NFC interface or by an NFC interface
connected to a computer through a USB
port (both not included).
The LogChart-NFC smartphone app
allows the user to configure the logger and
view and graph the temperature history.
The NOVUS Cloud Portal is offered as an
optional service to TagTemp-NFC users.
The LogChart-NFC Android app can be
configured to send out temperature recordings read from TagTemp-NFC devices
straight to
the internet portal.
Once
stored on
NOVUS
Cloud,
records
can be
checked
from any
internet
browser.
Prices
start at
$59.00
+GST
each.
Contact:
Ocean Controls
PO Box 2191, Seaford BC, VIC 3198
Tel: (03) 9782 5882 Fax: (03) 9782 5517
Website: www.oceancontrols.com.au
siliconchip.com.au
ASK SILICON CHIP
Got a technical problem? Can’t understand a piece of jargon or some technical principle? Drop us a line
and we’ll answer your question. Send your email to silicon<at>siliconchip.com.au
Designing and winding
toroidal inductors
My question is regarding a project
in the March 2004 edition of Silicon
Chip titled “3V to 9V DC/DC Converter” (www.siliconchip.com.au/
Article/3421). I understand how boost
converters work and what the coil (inductor) does. What I want to know is
how calculate the inductance value
of the coil.
In the “Winding the Inductor” section, the article states: “The inductor is
hand-wound on a 14.8mm powdered
iron toroid. You’ll need about 700mm
of 0.63mm enamelled copper wire for
the job. In total, 30 turns are required to
achieve the 47µH inductance value.”
In this project, the toroidal core was
powdered iron with the dimensions
15mm x 8mm x 6.5mm and the wire
is enamelled copper of 0.63mm diameter, with 30 turns. How did you calculate that this would give 47µH? What
difference would a ferrite core make? I
hope you can help me because I want
to be able to design my own boost and
buck converters. (J. D., via email)
• Each core has an “Al” value; for the
15 x 8 x 6.5mm compressed powderediron core, it depends on the exact
type used. For a Neosid type number
17-732-22, the Al value given is 47
whereas for the Jaycar LO-1242 it is 34.
To determine the number of turns
of wire around the core required for a
given inductance value, you divide the
Al value into the inductance required
in mH, then take the square root and
multiply by 1000. Note that 47µH is
equal to 0.047mH.
So for the Neosid core, you can calculate the number of turns as 1000 ×
√0.047mH ÷ Al = 32. For the Jaycar
LO-1242 it is 37.
Each core also has a Joule rating
while allows you to calculate the
saturation current. In the case of the
Neosid core, the rating is is 0.54mJ.
The peak current at which saturation
occurs is the square root of the Joule
rating, divided by the inductance in
millihenries (mH); √0.54 ÷ 0.047 = 3.39
so that inductor could handle 3.39A
peak before saturation.
Note that saturation is progressive;
by the time the current had reached
3.39A, the effective inductance would
already be lower and it would drop
rapidly as the current increased.
The required wire diameter is usually based on 5A/mm2. The 0.63mm
diameter wire has a cross sectional
area (πr2) of 0.312mm2 and so is suited
for up to 1.55A RMS.
You can find more information on
these formulas at the Neosid website:
www.neosid.com.au/tech-info.html
Note that ferrite cores have a much
higher permeability (and higher Al)
and therefore saturate at lower currents. They also tend to have significantly lower eddy current losses, so
ferrite inductors are normally larger
Alternative Majestic/Senator tweeter with titanium diaphragm
I was wondering whether you
considered the Celestion CDX11720 compression driver (titanium
diaphragm) for the Majestic speaker
system before settling on the CDX11730 (PETP diaphragm), and if so,
why you chose the 1730 over the
1720.
The 1720 has a wider frequency
range (perhaps a little too wide to be
used for the available horns) and is
available at a similar price.
I have purchased the Celestion
No-bell horns and want a compression driver to use with them, but I am
not using them in a Majestic design.
I am trying to decide which driver
to buy, CDX1-1720 or CDX1-1730,
hence my question.
Any information you can give regarding why you chose the CDX11730 would not only be very interesting in itself, but might also help
me make a decision which one to
siliconchip.com.au
go for. Many thanks. (P. T., Casula,
NSW)
• Allan Linton-Smith replies: According to the official Celestion
brochure (websites can differ), the
CDX1-1730 handles more power
(75W RMS, AES standard as opposed to 50W RMS for the 1720). The
CDX1-1730 is also more efficient, at
110dB/W <at> 1m, as opposed to the
1720 at 107dB/W <at> 1m.
The CDX1-1730 seems to have a
flatter response on paper but there is
not much in it. The CDX1-1720 can
tolerate slightly lower frequencies.
All we know is that the CDX1-1730
together with the “No-bell” horn is
well regarded by everyone at Silicon Chip and has been our tweeter
of choice for three projects.
For the Majestic, we were aiming
for 300W maximum power handling
and the CDX1-1730 was a better
choice because we could attenuate
it more heavily, so it could be virtually bullet-proof against big power
transients.
Nevertheless, the CDX1-1720 may
be a good alternative for most systems which don’t require huge power handling. We haven’t tried the
1720 but it should be OK matched
up to the No-bell horn. Perhaps price
will determine your choice!
In the opinion of Silicon Chip
staff, tweeters with metallic diaphragms can sound overly bright. On
the other hand, Mackie advocate metallic tweeters as they do not “break
up” as badly as other types.
The CDX1-1720 could be used in
our designs but the extra capacitor
we put in the crossover to boost the
high frequencies often may not be
needed. It may be necessary to do
some re-balancing of the crossover components to avoid an overall
shrill sound.
September 2017 107
but more efficient than those with
powdered iron cores.
The design process requires careful
selection of the core size and material
based on current, core saturation,
inductance and switching frequency.
Solar Lighting System
LDR threshold control
I have just completed the Solar
Powered Lighting System project from
the May and June 2010 issues (www.
siliconchip.com.au/Series/9).
While it works well, I need more
control over the LDR threshold. The
normal ambient light level at that location at night is not quite low enough
to turn the system on. Can I change
the value of the 100kW resistor in series with the 500kW trimpot to remedy
this? (N. S., Bongaree, Qld)
• The 500kW trimpot (VR5) and series
100kW resistor should provide more
than enough adjustment range if the
LDR is to specification. You could use
a 10kW resistor instead of the 100kW
resistor that is in series with VR5, if
the voltage across the LDR does not
rise above 2.5V in low light conditions.
Ultrasonic Anti-fouling
Mk.1 blowing fuse
I purchased an Ultrasonic Antifouling Kit from Jaycar, catalog code
KC5498, based on your project from
the September and November 2010
issues (www.siliconchip.com.au/
Series/12).
I have assembled the kit and the
fuse keeps blowing whenever I try to
power it up. I have learnt that other
people have had the same problem.
I have contacted Jaycar for advice on
how to rectify the problem and they
have told me to contact you. (T. T.,
Whale Beach, NSW)
• Although some other constructors
have had similar problems where the
fuse blows, this has been due to a range
of causes rather than any one cause.
Assuming you have only used the
parts as supplied in the kit, try these
following steps.
Firstly, make sure the electrolytic
capacitors are oriented with the correct
polarity. Secondly, check the soldering
for dry joints and for shorts between
adjacent component connections.
Also check for correct placement of
all components.
108 Silicon Chip
Arduino-based 230VAC speed controller wanted
I purchased Jaycar’s KC5478 kit
for the 230VAC 10A Full-Wave Motor Speed Controller published in
your May 2009 issue (see: www.
siliconchip.com.au/Article/1434).
I bought this with plans to interface the kit with an Arduino microcontroller to vary the motor speed.
However, upon opening the kit,
I read in the instructions that the
whole circuit “floats at 230VAC”.
Is it possible to interface the kit
with an Arduino? Please advise if
you can suggest a mains motor speed
controller that can be used with a
microcontroller adjusting the reference speed. (T. K., via email)
• That speed controller project is
now obsolete, having been superseded by our improved design in the
Adjust VR1 for 5V between TP1 and
TP0 before inserting the fuse and IC2.
Make sure IC2 is inserted with the correct polarity.
If you are sure the kit is constructed
correctly, a slow blow 3A fuse could
be used. This may prevent the fuse
blowing should the large 4700µF electrolytic capacitor require a higher than
normal charging current when first
powered up.
Trouble-shooting failed
Ultrasonic Anti-fouling
I purchased the Jaycar Ultrasonic
Anti-fouling kit (KC5498), based on
the project in the September and November 2010 issues, for my 31-foot
yacht (www.siliconchip.com.au/
Series/12). I’m an electrical engineer
so the assembly was straightforward.
It had been working on my yacht but
yesterday while out sailing, the fuse
blew. When I replaced the fuse, the
LED did not come on to signify the
unit is working. I checked the voltage
both sides of the replacement fuse and
got 12V DC.
Are there other checks I can perform
on the unit with my multimeter? While
it was working, I was very impressed
with the unit. (I. W., Ireland)
• Perhaps there is an open-circuit
connection to the PCB for the fuse clip
on the output side. This might explain
why the LED does not light.
Check that the supply at TP1 is at
February & March 2014 issues. See:
www.siliconchip.com.au/Series/
195
However, neither project has
provision for interfacing to an external microcontroller, Arduino or
otherwise.
That would require something
like optical isolation to render it safe.
The improved 2014 design does use
a PIC16F88 micro, programmed in
assembly language.
To make it compatible with Arduino or the Micromite, it would need an
extensive re-design.
If we do publish another speed
controller with similar specifications, we would certainly make it
compatible with Maximite, Micromite and probably Arduino.
5V. Check pin 1 and pin 4 of IC2 are at
5V and that pin 8 is at 0V. Also there
should be a DC voltage reading at the
gate of each Mosfet as they are driven
by IC2.
The voltage would be around 2V but
this may vary. If voltage is 0V or floating (ie, can be pulled up to 5V with a
100kW resistor to the 5V supply), then
there is a problem with IC2.
Other than that, there may be an
open-circuit connection on the transformer primary windings or Q1 and
Q2 may have failed and are not conducting when the gate is driven high
(to 5V).
Check continuity of the 12V supply
after the fuse up to the transformer terminals on the PCB. 12V should also
be present at the drains of Mosfets
Q1 and Q2.
Check that the 20MHz crystal is oscillating. A voltage reading should be
found at pin 3 of IC2 at about 2-3VDC
when checked with a multimeter.
Using Battery Lifesaver
with 7-cell Li-ion battery
I have an application for the Battery Lifesaver (September 2013; www.
siliconchip.com.au/Article/4360)
which uses a “7S” LiPo battery, ie,
29.4V fully charged, 25.9V nominal
and 21-25.2V discharged.
Since the battery voltage is pretty
much at the upper limit of the Mosfet
maximum drain-source rating, do you
siliconchip.com.au
Induction Motor Speed Controller troubleshooting
I emailed you about six months
ago while I was trying to sort out
an initial problem with the 1.5kW
Induction Motor Speed Controller (April & May 2012; www.
siliconchip.com.au/Series/25). I’ve
lost those emails due to a software
problem but continue my quest to get
this equipment operational.
To recap, I was not getting the PIC
program to run when 3.3V power
was applied. I had no LED activity
and no signal was present at pin 15
of the PIC.
There was, however, a hint of
activity on the PIC outputs to the
optocouplers.
I obtained a new unprogrammed
PIC, a PICkit 3 and Microchip
programming software and went
through the learning process until
I had my PIC programmed with the
relevant HEX file from the Silicon
Chip website. But alas, still no proper
operation.
I then breadboarded the PIC and
its surrounding circuitry and had
some success. The Start LED flashes
for a while in pool pump mode and
the frequency of the waveform at pin
15 changes as expected.
have any recommendations as to the
suitability of the Battery Saver to cope
as published; ie, should I upgrade any
of the components?
Inrush current is about 20A and
normal current drain is around 6A.
Thank you for any advice. (J. R. N.,
Widgee, Qld)
• The original LifeSaver design
should be OK in this application.
Li-ion charger cut-off is usually very
accurate so it’s unlikely the battery
voltage will ever exceed 30V and Mosfet drain/source ratings are usually at
least several volts below the actual
avalanche breakdown voltage.
If you wanted to, you could substitute a 40V Mosfet but it would need
to be a similar type with a very low
on-resistance. We don’t think that is
necessary.
The only thing possibly amiss at
this stage is that there are drive signals to the optocouplers at pins 22,
24 and 26 but pin 25 is constantly
low. Is this normal or should there
also be activity at pin 25? Once I get
past this hurdle, I’ll be able to try
and sort out what is wrong on the
main PCB.
The only things different on my
breadboard are a leaded tantalum
capacitor at pin 20 (instead of an
unreadable surface mount capacitor on the main PCB) and I’ve used
a 10kW resistor at pin 1 (MCLR) as
per the PIC datasheet instead of
47kW as specified in the article. (M.
H., Moonee Beach, NSW)
• We have all your previous emails
and our replies. Pin 25 only goes
high to shut down the outputs of
the device if a fault is detected so
the constant low voltage is normal.
M. H., subsequently got back to us,
having solved the issue: “Up until
the other day I had been following
the testing instructions which said to
feed 3.3V into the circuit via CON4.”
“I had tried this with a couple of
different linear power supplies with
the same result.”
(www.siliconchip.com.au/Article/
10751) is good but what if you really
want to run on battery as the original device was intended rather than
mains?
How about a design that is battery
powered (eg, Li-ion/NiMH?) and gives
the same output voltages of 1.5V and
90V? I have a set that used a large 1.5V
bell battery for the filaments and two
45V dry batteries in series for the plate
voltage. 45V batteries are very expensive. (R. P., Auckland, NZ)
• It could be done but we would need
a switchmode booster circuit to go
from 11.4V (standard three-cell lithium-ion battery) to 90V and probably
a second switchmode (buck) circuit to
provide the 1.5A output.
It would need quite a lot of EMI suppression to avoid causing interference
with the radio.
Rechargeable valve radio
Upgrading an ETI 480
battery supply wanted
The “Battery Valve Radio Power amplifier
Supply” in the August 2017 issue
siliconchip.com.au
Back in February 1977, I built the
“By chance, I decided to check the
operation of the onboard 3.3V regulator by feeding about 7V to REG1.”
“Lo and behold, the PIC sprang
into life and worked as it should. I
then removed the 7V supply and fed
3.3V into pin 2 of the ICSP connector instead. Once again, it worked
properly. So the problem is the 10W
resistor between pin 1 of CON4 and
the Vdd pin (pin 13) of IC3.”
“Also, during my extensive
checks of voltages and continuity
before sorting out the problem, I
found that the connections shown in
the circuit diagram between pins 17
and 18 and the DIP switches labelled
‘EXT’ and ‘O/S’ are transposed. My
PCB is the updated version (supplied in a Jaycar kit).”
M. H., is correct, the instructions
to feed 3.3V into CON4 are erroneous
since the voltage drop across the 10W
series resistor could be high enough to
prevent proper operation and will result in an unregulated supply for IC1.
During testing, 3.3V power should
be fed in via the ICSP header instead.
We will publish errata on this, and
the incorrect labelling of the DIP
switches in the circuit diagram.
ETI 50W stereo amplifier which used
two of the ETI 480 amplifier modules
along with preamp and tone control
boards.
It still works fine and I am looking
to revamp the unit to use as a stereo
fold-back amp at a local hall.
I am thinking of adding the extra
transistors to the power amplifier modules to convert them into the 100W versions as well as removing the preamp
and tone boards and adding a LED VU
meter and speaker protection modules.
However, the original 28V-0-28V
transformers are no longer available;
this is the same one that was used for
your SC480 design from January &
February 2003 (www.siliconchip.com.
au/Series/109).
Altronics have a 300VA 30V-0-30V
toroidal transformer with 12V and
15V auxiliary windings. I could use
the auxiliary windings to run cooling fans as the area the unit works in
gets warm.
But will the 100W version of the ETI
480 (or your SC480) handle the higher
September 2017 109
Touchscreen DDS Signal Generator signal clips at 100%
I have built the Touchscreen DDS
Signal Generator as described on
page 68 of the April 2017 issue of
Silicon Chip (www.siliconchip.com.
au/Article/10616).
I purchased nearly all of the components from the Silicon Chip Online Shop. The construction was
straightforward and the initial testing went well.
However, I noticed that the sinewave output would start to be
clipped on the positive cycle once
the level was raised above 90%.
The amount of signal clipping increased as the level approached the
100% value.
I checked it on two different oscilloscopes just to make sure there
was not some obscure problem on
the first oscilloscope used. The second oscilloscope that was used happened to be the Banggood DSO138
LCD Scope, as described on page
53 of the April 2017 issue of Silicon Chip. Both oscilloscopes show
the signal clipping of the sinewave
above the 90% level.
It also appears that the square
voltage? I realise I have to change to
something like a 35A bridge rectifier
and increase the filter caps to say, a
total of 10000µF.
We don’t intend on running the amplifier flat-chat as so many people seem
to think is a requirement for running
power amps in an audio or PA system.
(A. B., Davoren Park, SA)
• A 30V-0-30V transformer is probably just a little too high and not worth
the risk of blowing output transistors.
In any case, both the ETI480 and the
SC480 are obsolete.
Why not build our recently described SC200? It is much more rugged, with far more power output, easy
to build and it will run with a 30V or
40V per side transformer.
Li’l Pulser overload
buzzer only beeps
I have built the Li’l Pulser Mk2 model
railway controller (from the July 2013
issue, updated in the January 2014 issue; www.siliconchip.com.au/Series/
178) and it appears to work OK.
But if I short-circuit the track, all
110 Silicon Chip
wave produced by the Touchscreen
DDS Signal Generator is over-driven
because both oscilloscopes show the
horizontal line portion of the positive and negative cycle on a slope
instead of being horizontal.
Unfortunately, the square wave
level is fixed at 100% so it cannot
be decreased making it impossible to
check if the square wave looks correct at a lower level setting.
There does not appear to be any
way of eliminating these two problems by adjustment. It is worth noting that the triangle waveform is perfect even at the 100% level setting.
Has this problem been encountered by anyone else and is there a
solution? (D. B., Wellington, New
Zealand)
• We asked Geoff Graham to comment and his response is as follows.
The output waveform is clipping
because the gain of the amplifier in
the module is too high and the output is being limited by the power
supply voltage. We tested a number
of modules and set the maximum
gain based on these tests but you
I get is one short beep from the siren
instead of a continuous sound. Is that
correct? (R. H., Campbelltown, NSW)
• Yes, the overload buzzer should
sound briefly. That’s because when a
short is detected, the buzzer sounds
and supply to the track is switched
off.
With supply off, the overload is
removed and so the buzzer goes off.
The supply is restored after a short
period and the buzzer sounds again
if an overload is still present.
Automatic Audio Gain
Control circuit wanted
I am after a copy of a Silicon Chip
magazine that contains the circuit
and building instructions for an Audio Automatic Gain Control unit. I
need to connect it to the speaker or
line output of a QRP transceiver. Can
you please help me? (E. T., Hornsby
Heights, NSW)
• We published an Automatic Level
(Volume) Control in the March 1996
issue and Compressors (which operate similarly) in the March 1999, June
may have a module with even more
gain or perhaps a lower power supply voltage.
In the BASIC program (SigGenerator.bas), the gain is set at line number
495 (“Local Integer x = (Level/100)
* 211”). You can adjust the number
211 to suit your module. Try a lower
value (say 190) and adjust it as necessary so that you do not get clipping
at the maximum output.
To edit the BASIC program, you
will need to connect a USB/Serial
converter to the console, stop the
program using CTRL-C and run the
EDIT command. See the Micromite
User Manual for details.
The sloping top and bottom of
the square wave output is probably
because you are using AC coupling
on your oscilloscope’s input.
The Touchscreen DDS Signal Generator’s output is also AC coupled,
however, the large value used for the
output capacitor will ensure that this
effect is only seen at low frequencies. It would be worth checking
that the value of this capacitor is
correct (470µF).
2000 and January 2012 issues. See the
links below.
The Compressors boost low levels
and reduce high levels for a more constant sound level but with some degree
of volume variation. The Automatic
Level Control maintains a constant
volume. The settings can be changed
to suit your purposes.
The Automatic Level Control from
March 1996 is available as a printed
back issue while the others can be
viewed online or a printed back-issue
purchased.
We suggest you build the January
2012 design as it’s the most up-to-date
with two kits available (Jaycar KC5507
and Altronics K5526) and we can also
supply the PCB and panels from our
Online Shop.
• January 2012 “A Stereo Audio Compressor” www.siliconchip.com.au/
Article/809
• June 2000, “CD Compressor for Cars
or the Home” www.siliconchip.
com.au/Article/4328
• March 1999, “Easy-to-Build Audio
Compressor” www.siliconchip.
com.au/Article/4608
SC
siliconchip.com.au
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on 0425 122 415 or email bigal
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WARNING!
SILICON CHIP magazine regularly describes projects which employ a mains power supply or produce high voltage. All such
projects should be considered dangerous or even lethal if not used safely.
Readers are warned that high voltage wiring should be carried out according to the instructions in the articles. When working
on these projects use extreme care to ensure that you do not accidentally come into contact with mains AC voltages or high
voltage DC. If you are not confident about working with projects employing mains voltages or other high voltages, you are
advised not to attempt work on them. Silicon Chip Publications Pty Ltd disclaims any liability for damages should anyone be
killed or injured while working on a project or circuit described in any issue of SILICON CHIP magazine.
Devices or circuits described in SILICON CHIP may be covered by patents. SILICON CHIP disclaims any liability for the
infringement of such patents by the manufacturing or selling of any such equipment. SILICON CHIP also disclaims any liability
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siliconchip.com.au
September 2017 111
Next Month in Silicon Chip
Silicon Chip’s 30th Anniversary
Advertising Index
Silicon Chip was first published in November 1987 so next month’s issue is
our 360th issue! The anniversary issue will include an article on how to make
the best use of our website.
Altronics...................CATALOG,85
Deluxe Touchscreen eFuse, Part Three
Dave Thompson...................... 111
Control Devices Group.............. 45
Unfortunately, this article has been delayed due to space contraints. This third
and final article explains how to assemble the unit into the case, calibrating it
and using it. It will also include some information on how the software works.
Digi-Key Electronics.................... 3
5-inch touchscreen Micromite 6GHz+ frequency counter
element14................................. 42
Our new frequency counter is compact and easy to use. It has two inputs which
together cover a frequency range from below 10Hz to above 6GHz.
El Cheapo Modules, part 10: GPS modules
We describe two common GPS modules, their features and how to interface them
to an Arduino or Micromite.
Note: these features are prepared or are in preparation for publication and
barring unforeseen circumstances, will be in the next issue.
The October 2017 issue is due on sale in newsagents by Thursday, September
28th. Expect postal delivery of subscription copies in Australia between September 28th and October 13th.
Notes & Errata
Arduino Stereo Audio Playback and Recording Shield, July 2017: theSC
circuit diagram (Fig.2 on pages 74 and 75) shows LED2 connected to SCK but
the text says it is connected to the CS line. The diagram is correct.
12V DC Cycling Pump Timer, Circuit Notebook, July 2017: a 10µF capacitor
needs to be connected between pin 7 of IC1 and ground in order for IC1 to
operate in pump timer mode.
New Marine Ultrasonic Anti-Fouling Unit, May & June 2017: ETD29 3C85
ferrite cores may no longer be available since they have been discontinued by
FerroxCube. ETD29 3C90 ferrite cores are suitable substitutes.
Induction Motor Speed Controller, April-May 2012, December 2012 &
August 2013: contrary to the instructions on page 74 of the May 2012 issue,
do not feed 3.3V into CON4 to test the unit without using the mains supply.
Instead, feed 3.3V into pin 2 of the ICSP header while making the ground
connection to pin 3 of that same connector. This supply can be provided by a
PICkit 3 programmer set up to supply power to the chip being programmed.
Also, in the circuit diagram (Fig.5 on pages 22 and 23 of the April 2012 issue),
the connections to the EXT and O/S DIP switches are shown reversed; EXT
should go to pin 18 (RB8) and O/S to pin 17 (RB9).
Building the RapidBrake, August 2017: in the calibration instructions on
page 85, the first sentence under “Step 1” is incorrect. It should read: “If the
jumper at JP1 is set for the Y-axis, go to step 2. If the jumper is set for the Xaxis, as before, ...”
Electronex................................. 52
Emona Instruments................. IBC
Freetronics................................ 15
H K Wentworth/Electrolube....... 46
Hare & Forbes....................... OBC
Icom Pty Ltd.............................. 14
Jaycar............................ IFC,53-60
KCS Trade................................. 13
Keith Rippon Kit Assembly...... 111
Keysight..................................... 50
LD Electronics......................... 111
LEDsales................................. 111
Master Instruments..................... 9
Mastercut Technologies............. 43
Mektronics................................. 47
Microchip Technology............. 5,29
Mouser Electronics...................... 7
Oatley Electronics..................... 35
Ocean Controls........................... 8
Pakronics................................... 10
PCB Cart................................... 11
Qualieco Circuits Pty Ltd........... 51
Rohde & Schwarz...................... 49
ROLEC OKW............................ 48
Sesame Electronics................ 111
Circuit Ideas Wanted
SC Online Shop...............104-105
Got an interesting original circuit that you have cleverly devised? We need
it and will pay good money to feature it in the Circuit Notebook pages. We
can pay you by electronic funds transfer, cheque (what are they?) or direct
to your PayPal account. Or you can use the funds to purchase anything from
the SILICON CHIP on-line shop, including PCBs and components, back issues,
subscriptions or whatever. Email your circuit and descriptive text to editor<at>
siliconchip.com.au
Silicon Chip Binders................. 39
112 Silicon Chip
Silicon Chip Wallchart.............. 99
Tronixlabs................................ 111
Vintage Radio Repairs............ 111
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