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Items relevant to "Multi-use Frequency Switch":
Items relevant to "LTspice Simulation: Analysing/Optimising Audio Circuits":
Articles in this series:
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Contents
Vol.31, No.5; May 2018
SILICON
CHIP
www.siliconchip.com.au
Features & Reviews
14 Drone Air Taxis – Autonomous, Pilotless and Soon!
Already trialling in several countries, you’ll soon be able to call up a pilotless
drone taxi from your smartphone. Fares are projected to be not much more
than street taxis but there will be no traffic hang-ups! – by David Maddison
24 Tiny capsule measures, radios your gut gas data
Medical specialists need to know what gases are in your gut – but they are
loathe to operate. Now researchers in Australia have come up with a capsule
that measures gases and radios the info in real time – by Ross Tester
43 LTspice Simulation: Analysing/Optimising Audio Circuits
Continuing our occasional tutorial series to help you understand the very
versatile LTspice simulation software. It’s still available (free!) from new owners,
Analog Devices – by Nicholas Vinen
82 El Cheapo Modules 16: 35-4400MHz frequency generator
Based on the ADF4351 PLL, this <$30 module can produce a signal from
35MHz to 4.4GHz with crystal accuracy. It can even be used as a sweep
generator – by Jim Rowe
Constructional Projects
28 800W (+) Uninterruptible Power Supply (UPS)
One of our most exciting projects ever: a build-it-yourself UPS which we believe
isn’t as good as commercial models . . . it’s much better! And if you need even
more grunt, this design allows it – by Duraid Madina and Tim Blythman
36 Multi-use Frequency Switch
Some Drone “Taxis” are still
figments of their proponents’
imagination – but some are
already in testing phase – Page 14
Tiny capsules
pass through
the gut, reading
and sending gas
data as they go
– Page 24
Suffer from blackouts in your office
or home? You need a UPS to ensure
you don’t lose
valuable data.
It’s also the
answer to
maintaining
power after a
disaster – Page 28
If you need something controlled when it exceeds a certain frequency – up or
down – this superb circuit will do it. Anything that produces a frequency (or can
have a sensor fitted) can be switched – by John Clarke
57 USB Port Protector – just in case!
We thought we’d fried a laptop when something managed to drop onto the
exposed USB port components. We were lucky – but made up this low cost,
mini PCB to guard against “oopses” in the future! – by Nicholas Vinen
70 12V Battery Balancer
12V batteries in series need careful attention to charging if you’re expecting a
long life. This little balancer does it automatically for you and you can even use
them in parallel for extra power handling – by Nicholas Vinen
Your Favourite Columns
63 Serviceman’s Log
I reckon servicemen are cursed – by Dave Thompson
76 Circuit Notebook
(1) 20V, 2.5A adjustable power supply with current limiting
(2) A personal “speedometer” for joggers
(3) Sunset switch to discourage possums and other night visitors!
(4) Adjustable audio low-pass filter
90 Vintage Radio
Zenith Royal 500 “Owl Eye” AM Radio – by Dr Hugo Holden
Everything Else!
2 Editorial Viewpoint
Feedback
88 Product Showcase
94 SILICON CHIP Online Shop
4 Mailbag – Your
siliconchip.com.au
96
103
104
104
Ask SILICON CHIP
Market Centre
Advertising Index
Notes and Errata
Switch just about any
device if its output
frequency goes above
or below limits which
you set – Page 36.
USB ports can
be fried if
you’re not
careful
(we know!!!).
Be safe with this low-cost
USB Port Protector – Page 57
You can’t simply
charge 12V
batteries in
series as you
would a single
battery – you
need a battery
balancer to ensure
they don’t get out of
balance – Page 70
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SILIC
CHIP
www.siliconchip.com.au
Publisher
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Editor
Nicholas Vinen
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John Clarke, B.E.(Elec.)
Technical Staff
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2
Silicon Chip
Editorial Viewpoint
Trusting our lives to computers
In the January editorial, I raised concerns about the
digital security of autonomous vehicles. While two fatal
accidents relating to (semi-)autonomous vehicles have
been in the news lately, both appear to be due to failures in the sensors or software. One resulted in Uber
suspending North American autonomous vehicle testing for an indeterminate period.
Consider that in the last 12 months, around 1250 people were killed in road accidents in Australia. Let’s imagine that by making every vehicle on our roads autonomous, we could halve
that, to 625 deaths per year (without any negative effects).
This seems like it would be a good thing. But will the general public
accept software errors killing two people every day in Australia alone? Most
of these people will not have done anything wrong and there may be nobody
to “blame” in most of these incidents. Based on the reaction to the aforementioned deaths, I don’t think it would go down well at all.
And then consider the future posed by the article on flying passenger drones
in this issue. This brings us the possibility of fatal crashes involving not just
drone passengers but also (from time to time) some hapless people on the
ground, too. They could be minding their own business when, with no warning, a drone falls on them.
Yes, flying is very safe these days but commercial aviation is heavily regulated and the aircraft are well-maintained. They still crash occasionally.
And while there are a huge number of planes in the air at any given time,
there would have to be many more small drones to have a significant impact on
transportation. They’d have to come crashing down to earth from time to time.
So the question is this: will the general public get used to the idea of computer errors or hardware failures being responsible for so many deaths?
A different approach to project construction
On another topic, we have the first part of a very practical major project in
this issue, namely, the lithium-battery-based Uninterruptible Power Supply.
This is an unusual project for us because while it’s quite a large and complex
design, there’s little soldering involved.
It’s mostly built from off-the-shelf building blocks that are wired together. It
does have a custom control PCB, the details of which will be presented next
month but even this is based on pre-built Arduino and relay driver modules.
When you look at the UPS box, mostly what you see are the large batteries
and the impressive sinewave inverter.
The fascinating aspect of this project is that you could take essentially the
same design and scale it down to a tiny backup supply for a few LED lights.
Or you could scale it up to a huge device that would keep a household running for days without mains power. The design principles used would be
basically the same.
So we had some “spirited” discussions about just how best to present it
in the magazine. Is it just a UPS or is it something much more than that? We
wound up mentioning some of the many other possibilities in the article. But
there are lots of aspects of this design to be explored.
We’ll finish describing this UPS design – which has quite a few different
uses – over the next couple of issues. But we intend to revisit the concept in
the future, to flesh it out. For example, we may add solar panels to keep the
batteries charged when the grid fails. And we might increase the size of the
battery bank and inverter power. This would greatly expand its possible uses.
In the meantime, some readers may see what we’ve done and decide to expand
the design on their own. There’s certainly nothing to stop you from doing that.
Nicholas Vinen
Celebrating 30 Years
siliconchip.com.au
siliconchip.com.au
Celebrating 30 Years
May 2018 3
MAILBAG – your feedback
Letters and emails should contain complete name, address and daytime phone number. Letters
to the Editor are submitted on the condition that Silicon Chip Publications Pty Ltd may edit and
has the right to reproduce in electronic form and communicate these letters. This also applies to
submissions to “Ask SILICON CHIP”, “Circuit Notebook” and “Serviceman”.
Information from ACMA
about LED interference
It was with some interest I read a
letter during the night on TV channel
interference by D. McC. in the April
2018 issue of Silicon Chip. Your response was a bit surprising.
ACMA recognises LED lights as a
cause of interference (siliconchip.
com.au/link/aajp). This information
was provided to me by an employee
of ACMA who was investigating TV
interference at my premises and adjoining addresses.
Our problems developed a few years
ago and have increased over that time.
There seems to be a number of factors
involved including solar panel inverters and radiation from power lines
(which is worsening).
We need someone with the right
equipment to visit our area after hours
(ACMA have difficulty with staff beyond business hours!) to make observations when interference actually
occurs.
We also have a radio reception problem on the AM band at 873kHz, causing increased background noise.
Geoff Lloyd,
Hornsby Heights, NSW.
Response: it definitely is plausible
that poorly designed LED switchmode drivers could cause significant
interference but we're unsure why it
would affect just one TV channel frequency. Perhaps the affected stations
are at an odd harmonic of the switching frequency.
Grid-feed inverters and power-line
based networking certainly are contributing to a much higher level of RF
background noise and can swamp AM
reception in some areas.
Game Boy mystery solved
In the Ask Silicon Chip section
of the February 2018 issue, B. M. of
Kiama Downs asked about a watering
system project based on a Game Boy.
The article appeared in Electronics
Australia, June 2000, on page 41.
John Heffernan,
via email.
4
Silicon Chip
More range for the nRF24L01+
Digital Radio Modules
I read Jim Rowe’s interesting article
in the January 2018 edition regarding
working with the nRF24L01+ digital
radio modules. I purchased a couple
from the Silicon Chip Online Shop and
yesterday, updated the firmware on a
couple of LCD BackPacks I previously
built for other uses and programmed
them with your “checkout” program.
It worked straight out of the box but
I found a few ways to tweak the hardware and software to achieve better
range and performance.
Firstly, I think the recommended
10µF bypass capacitor should be considered mandatory! Without these, I
was getting a range of not much more
than 1.5m and even then, it was a
little erratic in one direction. After
fitting 10µF MLCC capacitors, range
went up to about 7-8m but no more,
without lots of time-outs (1 in 4). Also,
it was still a little asymmetric.
I downloaded the Nordic IC product
specifications and also went back to
the September 2016 Circuit Notebook
article and noticed they both used a
lower data rate and a higher power
setting.
I tried your code with RegData(5)
set to &H2626 (for 250kb/s, and 0dBm)
LED interference
can affect some TV channels
I also had the same problem D.
McC. had (Ask Silicon Chip, April
2018, page 89).
The family living across the street
from us had a tree in their front yard
all decked out in LED lights. When
the lights were turned on, channel
10 would disappear and channel 7
would pixellate.
The family concerned are a rather
prickly bunch and weren't going to
have a bar of it. I managed to talk
the husband into coming over for
a demonstration while his wife at
home turned the lights off and on.
Sure enough, the reception fault
Celebrating 30 Years
and RegData(3) set to &H2453 (to set
ARD to 1500µs, to suit the slower
speed). I must admit that I haven’t a
clue what the first bytes in each RegData value relate to – I was concerned
they might involve the CRC – maybe
you can shed some light on this.
Anyway, this worked, and the range
was at least doubled – to 16m+ going from a room downstairs, through
a couple of doorways, upstairs, and
around a corner – so not really “lineof-sight”.
With the increased power setting
(0dBm) and lower data rate (250kb/s)
and the devices fitted with 10µF MLCC
bypass capacitors, I got reliable communications at 200m with line-of-sight
(I had one unit set up on a bin near the
road). It’s possible that this set-up is
capable of more range but I ran out of
road and was starting to get amongst
trees in our local park.
Finally, I don’t understand why
you’re reversing the byte order of the
payload before transmission and then
reversing them again on reception,
before output. I deleted both the byte
reversal process when assembling the
followed the light operation. The
light installer wouldn't believe it!
A week later, the installation crew
arrived with boxes of lamps sourced
from China.
They changed all the lamps and
we had no more problems. I could
not get any information from the installers on the lamps and the prickly
neighbour was not all that forthcoming with information either.
Looking from the side fence, I
could see that they had a glass outer
envelope, were supposedly LEDs
and glowed with a slight orange tint.
I hope that helps.
Fred Thorpe,
Narrabeen, NSW.
siliconchip.com.au
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6
Silicon Chip
data to transmit (PrepmsTime), and removed the “RestByteOrder” subroutine. This didn’t make any difference
to the operation of the units.
Ian Thompson,
Duncraig, WA.
Jim Rowe replies: it sounds like the
changes to the RegData values are
worthwhile. Note that 0dBm is only
1mW, so this higher power setting is
still perfectly legal. I implemented
the data byte reversal because the
nRF24L01 datasheet implied that it
was required but you have apparently
found that it isn’t.
How to reach audiophile nirvana
I read your response to the query regarding directionality in audio cables
on page 91 of the April 2018 issue.
You left out some important details.
It's a little-known fact that the
"break-in period" can be reduced significantly by hanging the cables up by
one end. Furthermore, directionality
can be improved by stroking the cables by hand while they hang. Firmly
stroking each cable, from bottom to
top, for about an hour each day over
a month, will virtually eliminate any
need for further "break-in".
Phil Denniss,
Darlinghurst, NSW.
Computer security seems like a joke
Your remark in the February 2018
Editorial Viewpoint that “Unless you
become a hermit and live in a cave in
the mountains, I’m not sure that you
can ever be completely safe from these
flaws” seems to be on the money. In
just the last few months, the following has occurred:
1. WPA2 WiFi encryption has been
shown to be flawed and vulnerable.
2. Equifax (a credit rating agency) in
the USA has been hacked and the
personal details (social security
numbers, accounts etc) of 150 million US citizens have been stolen.
I recently found out that Equifax
operates in Australia too.
3. Spectre & Meltdown were discovered (the topic of your editorial).
These are reputedly launched
through JavaScript on web pages.
These apparently also put “the
cloud” in jeopardy.
4. Recently, it was reported that all
that is needed now for ID theft is
someone’s Driver’s License number. Enough other personal details
are available (eg, through Social
Celebrating 30 Years
Media) to then enable the theft.
Recently, telcos and electricity
suppliers have been asking for License numbers.
5. The Russian government allegedly
had a backdoor into Kaspersky anti-virus software which they used
to get their hands on secret information from the NSA. This is scary
as anti-virus software requires privileges and access to core parts of the
computer. In the past, there were
strong rumours of Microsoft providing backdoors for the NSA etc.
6. It was revealed that the Australian
Electoral Commission is using archaic systems and software. DOS
was mentioned as still being in use.
Regarding your recommendation of
“patching”, this concept is in itself not
secure and creates vulnerabilities. The
business models of Apple and Microsoft exacerbate this. Remember you
don’t own the OS, you are a renter and
the landlord has another key. A recent
example is Apple purposely and surreptitiously interfering with (ie, reducing) the iPhone’s speed.
Now I wouldn’t suggest one becomes a hermit but because hardware is now so cheap, I suggest that
you should have two systems, one airgapped (the one holding private information) and one connected to the
‘net for browsing. Regularly wipe and
re-install the OS on the internet-connected computer. This is much easier
with Linux.
The “Data Breach Mandatory Notification” legislation came into effect
on the 22nd of February. Though it is
(at the moment) limited to companies
with $3 million turnover and above, it
should be a wake-up call to everyone.
J. Williams,
Elanora, Qld.
Comment: while it’s true that patching
your operating system can introduce
bugs, including security vulnerabilities
and backdoors, unpatched systems
are even more vulnerable. A computer
connected to the internet that hasn’t
been updated in a year or more and
that isn’t behind a comprehensive firewall is almost certainly to have been
already compromised.
Image on monochrome TV
is not a moiré pattern
On page 81 of the March 2018 issue,
in the article on the Analog TV A/V
Modulator, I noticed the caption for the
right-hand image of the test pattern on
siliconchip.com.au
a B&W set says that the screen features
"moiré pattern[s]" due to the interaction of the screen and camera. But you
can see that this patterning only occurs
in the parts of the picture which have
colour (ie, in the colour bars).
This is due to the 4.433MHz PAL colour modulation sidebands modulating
the CRT beam on the TV set. There is
no (or little) patterning in the black,
white or grey areas of the picture.
This could be eliminated by adding
an LC trap circuit in series with the
video signal line, tuned to 4.433MHz.
A switch could be added to switch it
out for use with colour sets. It could
be added to the pin 11 input of IC6.
Alternatively, it's possible to fine-tune
the TV slightly so it is less noticeable.
As usual, it was an excellent magazine; I would not miss it. You have
some very clever and innovative designers.
Rod Humphris (ex RMIT),
Ferntree Gully, Vic.
Faulty premises Earth connections
are still a menace
The Publisher's Letter in the August
2014 issue of Silicon Chip warned of
the dangers of faulty Earth connections
and the possibility of electrocution
during the removal and replacement
of water meters.
I was sufficiently concerned that
I bought a clamp meter to check the
current in the incoming water pipe of
our house. I was relieved to find that
any current was below the threshold
of measurement.
In The Australian, 7th March, 2018,
there is an account of a child who
is in a critical condition in hospital
after receiving a severe shock from
a garden tap. It seems likely that a
faulty Neutral/Earth connection was
responsible.
It would seem prudent to have house
Earth connections checked every
few years since they can be degraded
by corrosion, with fatal consequences.
James Goding,
Princes Hill, Vic.
Leo Simpson responds: This issue
raises its head again, in the most tragic circumstances! I agree entirely that
Neutral and Earth connections to all
properties should be checked a matter of routine by the supply authorities
and if anomalies are found, they should
be fully investigated and rectified, no
matter how many properties may be
affected in any one instance.
siliconchip.com.au
In fact, it probably should be a requirement that any property being
sold or leased should have a test certificate to state that the wiring is safe,
just as most states have a requirement
that a home swimming pool must be
fully compliant with fencing and other
regulations
I was certainly not happy that the
anomaly I discovered at my home (as
detailed in the August 2014 issue) was
not fully investigated and remedied.
Changing the colour of Earth wires
is not permitted
The comments by Thomas Siegmeth
on page 6 of the March 2018 issue
regarding the misuse of green or green/
yellow wire for non-Earth wiring in
a mains-powered device are correct.
However, the comment about sleeving
the green/yellow conductor to solve
this is not correct.
The last paragraph of AS/NZS 3000
clause 3.8.2 prohibits the use of sleeving to use a green/yellow wire as an
Active or Neutral conductor.
Geoff Coppa,
Alstonville, NSW.
Response: we agree that this is not
acceptable since it would be possible
for the sleeving to fall off, or someone
might cut it off and then forget.
Some ideas for future seismographs
I received my April edition of SiliChip yesterday and was particularly interested to read your 3-Axis
Arduino Seismograph article. I have a
particular interest in seismology and
appreciate your point when you say
that there are few standard seismic
data formats that support multi-channel recording.
One that does is the PSN format
developed by a polymath electronicssoftware Californian gentleman named
Larry Cochrane.
Larry and his clever equipment have
been the backbone of serious amateur
seismology for the last couple of decades but sadly Larry is soon retiring
and many amateurs worldwide are
now scratching their heads and pondering life post-Larry. Larry and his
hardware and software are available
at his website: http://psn.quake.net
Using Larry's equipment I operate
a little seismic observatory at Coonabarabran, NSW, data from which is
posted at: www.map.id.au/seismic
Any earthquake big enough to make
the news is likely to show up here. You
con
Celebrating 30 Years
May 2018 7
may be interested to note that I have
recorded the last three North Korean
nuclear tests, including the latest one
which wasn't far from being a Chinacabinet rattler. The details are at: www.
map.id.au/seismic/epso_events_nk_
nuclear_tests.html
On my property, I operate a threeelement seismic array, where the sensors are at the vertices of an equilateral
triangle measuring 200 metres per
side.
This gives me the ability to unilaterally compute the bearing to a particular
earthquake/blast/event. I wish to make
a similar array but with the triangle
measuring around 4km per side.
My small seismic array is hardwired with buried cables but a large
array will require RF links of some sort
and I have been pondering my options.
Reading your article, another possibility occurred to me. If the Arduino
logger could incorporate precision
GPS timing as well, one could potentially create a powerful tool for seismic
monitoring (eg, for mining and engineering structures) and the creation of
large seismic arrays.
Generally speaking, professional
seismograph equipment costs a fortune,
so making a seismic array by deploying many autonomous precision-timed
loggers is not an option.
But if your Arduino could timestamp data to an absolute precision
of say 10 milliseconds or better, then
that would be potentially really useful
to me. It also means you don't have to
fiddle with setting RTCs and dealing
with their time drift.
So would you consider a future design improvement/upgrade to incorporate GPS timing as well? I'm not
sure if this is really possible, but if so
it would be most interesting.
Incidentally, I think your use of
WAV for this application is clever.
WAV data will be generally a lot more
compact than standard seismic formats, and it is then also trivial to "listen" to earthquakes. Listening to spedup seismograph data was quite a hobby
at one time, and I own a 33rpm vinyl
record made in the 1960s which contains exactly that.
Anyway, it was a great article and
clever to think of using WAV to solve
the compact-multi-channel problem.
Michael Andre Phillips,
Coonabarabran, NSW.
Nicholas responds: Thanks for your
feedback. It certainly would be possible
8
Silicon Chip
to use a GPS module for timing; we considered it but thought it unnecessary. If
you want to synchronise multiple geographically-distributed seismographs
then it makes a lot of sense and we will
certainly incorporate such a feature in
any future seismograph.
We did find and consider the PSN
file format when designing our seismograph but it has a major problem
in that it does not store the data for
multiple orientations or sensors in
an interleaved fashion like the WAV
file format. Rather, multi-sensor files
are simply multiple single-sensor files
"glued" together.
That makes it almost impossible
to generate them on-the-fly. You have
to record to multiple individual files
and then combine them when they are
complete. Whereas with a .wav file
with multiple channels, we can simply
append new data on the end and then
update the header periodically and no
post-processing is needed.
How accurate are GPS speed readings
on an incline?
I was intrigued by Leo Simpson's
assessment of the Navman Driveduo
in the February issue of Silicon Chip.
I use a GPS in my 1969 vehicle which
has its speedometer hidden in a black
hole in the dashboard and of course it
measures in miles per hour.
So I use a GPS unit as a speedometer, to give me some peace of mind
on speed-related matters. It reads my
speed to within 1km/h. Or does it?
As an engineer, I am always interested in how and why things work and
I have some questions about GPS. For
instance, it would appear to me that it
measures speed in the horizontal plane
only, my reason for this summation is
that the location is based on the intersection of the signals from satellites in
orbit at my location on the Earth’s surface; this can be shown as a vertical line
emanating from the centre of the Earth.
The different locations over a set
time will give the speed of travel between these two points on the Earth’s
surface. One assumes here that one is
travelling on a level surface.
But what happens when one is
travelling on a steep gradient? Does
the GPS speed reading drop as it only
takes into account movement in a
plane that's tangential to a spheroid
representing the Earth?
I believe there are some models of
GPS which include an altimeter. It is
Celebrating 30 Years
possible that these models may well
give an accurate speed reading on
steep inclines but without this function, how does the two-dimensional
GPS operate on slopes? I know that
there is some variation on gradients
as my speedometer tells me so.
John Hardisty,
Burnie, Tas.
Response: as far as we know, all GPS
receivers track altitude as well as
latitude and longitude, regardless of
whether the altitude is displayed. So
it should be possible for a GPS unit to
give an accurate speed reading even on
a steep incline. This does require the
correct calculation to be used, which
takes into account changes in altitude;
we assume most units will do this but
who knows.
GPS speed readings are likely to
be most accurate when travelling "on
the flat" but they are always behind
the eight-ball in adjusting to changes
in speed. This is due to the averaging
required to hide slight inaccuracies in
GPS position readings.
As you might expect, GPS accuracy
is also poorer in hilly country or in
"canyon-like" city streets with lots of
high-rise buildings.
The OBD setup is generally quicker
to respond and is probably more accurate but tyre wear (and long-term
changes in wheel diameter) would
also affect accuracy; not that OBD is
any good to you in a 1969 vehicle! The
only truly accurate speed measurement system would involve a RADAR
or LIDAR setup.
Updated GPS-based Frequency
Reference wanted
Regarding your September 2011
update of the popular GPS-based Frequency Reference project, I note that
like most GPS-based frequency references, it has a fixed output frequency
of 10MHz. While this is a common
frequency used by test equipment, I
have seen some devices which use a
reference frequency which cannot easily be derived from 10MHz.
For example, the Philips PM5193
function generator needs a reference
frequency of 8.589934592MHz so I
would like to see a GPS-based Frequency Reference design which provides reference frequencies other than
10MHz.
One possible way to achieve this is
to use a DDS IC such as the AD9956
with a 48-bit (or longer) frequency
siliconchip.com.au
word (with a frequency multiplier IC
for the reference oscillator) to generate
frequencies with the smallest possible
error. This error should be calculated
and displayed by the unit.
Bryce Cherry,
Rockhampton, Qld.
Response: we are working on a new
GPS-based Frequency Reference design and have taken your suggestion into account. It will have a fixed
10/20/40MHz (selectable) output and
multiple configurable outputs which
are derived from the main reference
clock using programmable PLLs. These
low-jitter outputs should be programmable from 0.1-167MHz in steps of
around 10kHz.
Another faulty motor run capacitor
The letter from Ian Thompson on
page 8 of the March 2018 issue was
very helpful. I live in a rural area
without reticulated water and so
water to the house is supplied from
underground tanks via a pump. Given
that the area is rural and reasonably
heavily wooded, we get our fair share
of blackouts.
To cope with this, we have a 2.4kVA
inverter-generator which I plug into an
appropriate socket at the main switchboard. This has worked successfully
for eight years. Recently, during a
blackout, the pump tripped the overload protection on the generator. That
had never happened before. So like
Leo Simpson, I assumed that it was
bearings in the pump or motor.
I dismantled the pump and found
no problems with the pump or motor
bearings. I checked the pump controller and found no problem there either.
The points in the controller had some
small amount of carbon on them but
not more than I would expect from
eight years of use.
The power was back on so I reassembled the pump and it worked normally. During the next blackout, the
pump was able to run off the generator but it seemed to be loading it more
than usual.
Having read the aforementioned
letter in the March 2018 issue, I realised that I had not checked the run
capacitor. I thought that if the capacitor failed, the motor would simply not
run. Two days later we had a blackout and the pump tripped the generator again. So I removed the capacitor
and measured its capacitance. It was
marked as 20μF but measured 11.6μF.
10
Silicon Chip
I purchased a 20μF motor capacitor
from Jaycar which measured 19.9μF.
I fitted it and re-connected the pump.
The blackout was still in effect so I
switched it on under generator power and it ran perfectly. It now runs
more quietly with the new capacitor
but I don’t understand why. Thanks
for the tip.
Peter Chalmers,
Clear Mountain, Qld.
Navman and DTV antenna
Your article on the Navman GPS
satnav is very much welcome. I am an
enthusiast for this “Real Time” Traffic
Information System, yet I am often
criticised for using one. For example,
“you don’t know your way home”...
and then I say, “why does it take you
so long to get home, were you stuck
in a traffic jam?”
Anyway, I was most impressed with
the article but I use the TomTom 520
with voice commands, where the RTT
(Real Time Traffic) information is received via Bluetooth from my phone
and is displayed down a panel on the
right-hand side of the TomTom screen.
I get an icon on my phone and the
TomTom showing a “Two Car” symbol which indicates that I am sharing
traffic information with fellow users.
This, in turn, helps TomTom developers improve mapping quality and
provide regular map updates, eg, for
speed cameras and road changes. But
regardless of the brand of the unit, the
article was wonderful reading. The
whole magazine is great. I also liked
Leo’s Digital TV antenna project.
Peter Casey,
West Pennant Hills, NSW.
Response: Google Maps also shares
traffic data with other users, which is
a great feature and a good reason to
prefer using a phone for navigation –
but you do need a reasonable amount
of data on your plan.
Smartphone app makes project
hard to justify
Most days I drive a section of road,
taking my kids to school, which has
100km/h point-to-point average speed
cameras. I have been imagining about
a device on the dashboard with two
buttons, one marked 100km/h and the
other 110km/h, these being the only
two speeds I have encountered average speed cameras at.
Pressing the appropriate button at
the start of the policed zone would
Celebrating 30 Years
cause the device to (via GPS) start to
track your average speed and would
warn you via an LED or alarm sound
if this exceeded the maximum you
had chosen. Pressing the button again
at the end of the policed zone would
turn off the monitoring.
Additionally, it could learn the location of the speed zone and will automatically monitor the area in the
future. The March 2018 editorial
prompted me to submit this as there
probably is a bad app for this already!
Love your magazine; keep up the good
work.
Alan Williams,
Adelaide, SA.
Comment: as you have implied, there
are already a number of smartphone
apps for average speed cameras and
while we aren’t sure if they do exactly
what you have suggested, it does seem
like they would be useful to ensure you
don’t run afoul of an average speed
camera. On that basis, we probably
can’t justify a custom-designed device
for this purpose.
Another option would be to fit cruise
control to your car (or use it if you
already have it). In many cases, except
when you’re travelling down a steep
hill, it will hold your vehicle very close
to the set speed. This is especially true
if you have an automatic transmission
which is able to change down for engine braking (or you could do it yourself with a manual transmission).
An easier method for assembling
RTL-SDR kit
Jim Rowe was absolutely right when
he said, in the November 2017 issue,
that assembling those RTL-SDR kits
was difficult.
I bought one of those kits and assembled all but the connection from
the toroid T1 to the RTL2832U chip.
It then sat for months while I pondered how to do it. I ended up soldering two dressmaker's brass pins to a
piece of Veroboard as pictured to the
upper right, then bent the pins so that
when the Veroboard was on top of the
RTL2832U IC, the pins would apply
pressure to pins 4 and 5 and make an
electrical connection.
I have been using the kit now for several months without any problems. I
don't see why this should be any less
reliable than, say, a socketed IC.
I used 22 SWG tinned copper wires
soldered to the Veroboard and to the
main PCB for support in two places
siliconchip.com.au
Shown at right are two
brass pins soldered to a
piece of veroboard.
Below it is the board
attached to the Banggood
SDR kit in a way that the
brass pins from the board
apply pressure to pins 4
& 5 of the RTL2832U IC,
so that it makes electrical
contact.
with a third wire soldered to the frame
and bent so that the pins were aligned
with and able to apply sufficient pressure to the pins of the RTL2832U chip.
The very thin wires from toroid T1
were soldered to the Veroboard tracks
to complete the circuit.
Regarding the software, you can in-
stall Airspy's SDR# for Windows as
described in Jim's November review.
However, the Windows software for
SDR are something of an ordeal to install, so instead, I installed a recent
version of gqrx (version 2.11, from
http://gqrx.dk) on Linux Mint (version
18.3) to get this SDR-RTL kit fully operational very quickly.
Note that for HF reception, gqrx
needs to use the parameters as shown
in the adjacent screen grab. I am very
pleased with the result, although a
wideband HF preamp is worth adding
for receiving marginal signals.
R. Matthews,
Adelaide, SA.
Confusion over slowing of
GPS clock pulses
Thank you for published the Analog
Clock-based 1pps signal source in the
Circuit Notebook section of the May
2017 issue, as I requested.
I finally got around to assembling
it. Initially, everything worked as expected. The startup LED did its thing
and a 40ms pulse got fed into my digitally-controlled analog clock, which
ran as expected.
I let it run on the bench for some
siliconchip.com.au
Celebrating 30 Years
hours but when I next checked the
time on it, my clock was very slow;
losing one hour in six. So something
was quite wrong.
Stopping the board and restarting it
caused it to perform as expected. I then
attached a CRO probe to monitor the
1pps output. It timed at exactly 1Hz,
so I let it run like that.
Checking after one hour and a bit, I
noticed the clock started losing time
again and the CRO pulse was now
0.5Hz, exactly half the expected rate.
I have no idea what is going on in
that PIC chip. However, I observed
there is a 1pps pulse available at the
white GPS connector wire for a short
time when the GPS had locked onto
its satellites. So I decided to use that
instead.
I simply removed Q2 and shorted
the collector-emitter pins to turn on
the GPS permanently. There now was
a nice 1pps pulse available but at only
3.3V peak-to-peak. A 4050 buffer (all 6
gates in parallel) boosted that to a 5V
pulse and with that my clocks keep
running right on time.
There was perhaps a misunderstanding at my initial request as low
power consumption is not an issue
May 2018 11
with my two clocks, both using 1970s
technology. A 5V/2A plug pack easily
provides the almost 5W of power requirement. So the extra drain of the
permanently on GPS is no problem.
If you think running the GPS powered like I do might do long-term damage to the PIC chip please let me know
but I doubt it.
Klaus Sussenbach,
Doubleview, WA.
Response: this is because the GPS
Analog Clock board drives the clock
mechanism with one pulse per second, but the pulses alternate in polarity between positive and negative, as
required by the clock motor. We realise now that the software would need
to be modified to produce a positive
pulse each time.
The reason it starts out at 1Hz is that
this is the unit “quick stepping” the
hands around to the correct time (it assumes they start out set at 12 o’clock).
A modified version of the firmware is
available for download on our website
under May 2017. This produces positive pulses only at 1Hz with no quick
stepping, to suit clocks like yours.
Praise for Super Clock and feedback
on Altimeter
I built the Micromite Super Clock
about a year ago and I must say it’s
been one of the best projects I’ve ever
made. I have been a keen clock collector for many years and I greatly appreciate the accuracy of the clock.
I used the DS3231 RTC as the timebase with a view to changing to the
GPS if the lack of accuracy warranted
it. During the past eight months, the
clock has lost less than 1.5 seconds
after I adjusted the basic accuracy with
the Micromite software.
I used www.timeanddate.com/
worldclock/timezone/utc as my time
reference and it’s interesting to notice
the occasional difference with phone
and TV time.
As a result of the incredible performance, I’ve given up on the GPS timebase because it would no doubt be a
problem supplying the GPS module
with a good signal at all times inside
the house.
I recently constructed the Micromite
Altimeter which works satisfactorily
except for the Humidity sensor which
reads quite low against two weather
stations. At the moment, the Micromite reads 23% against 37%. The sensor responds to my finger or breath and
12
Silicon Chip
rises to 100% very quickly and returns
in similar time. I think a sensor change
may be in order.
The temperature reading looks good
but I can’t determine whether you take
this reading off the BMP180 barometer sensor or the DHT22 humidity/
temp sensor.
I don’t fly and I built the altimeter
to use for bushwalking, car trips etc
where it’s interesting to follow the terrain. This is not the first altimeter I’ve
built. About 10 years ago I built a PICbased unit from an article in EPE magazine. This suited my purpose better
than the Micromite because you could
set the altitude directly into it from contour maps or start from home with the
known altitude set.
The Micromite is more suited to aviators in its present configuration and I
wonder whether you could modify the
software along the lines of the “QNH”
mod you recently included so that a
base altitude can be entered in. I feel
such a modification would greatly
increase the appeal of the unit for us
non-aviators.
Finally, I would like to suggest that
you dispense with the large “TOUCH
TO CHANGE” area on the screen and
use a touch screen function similar to
the Super Clock. The area of the present screen is somewhat wasted by
the TOUCH button especially as it’s
so bright and detracts from the overall readability of the screen.
I have modified my unit to use just
one case rather than the two as presented. The sensors are fitted into a
cut-down smaller plastic box on the
back of the main case. The little box is
ventilated with a number of holes and
the lid screws for the small box now
retain the sensor housing to the main
case. The heating problem is no longer
an issue and in addition when walking
as the unit is only on for short periods.
Bob Temple,
Churchill, Vic.
Response: note that your local microclimate can vary considerably from
that of nearby weather stations (Bureau
of Meteorology or your own). Just as
your local temperature can vary by several degrees compared to other nearby
sites, humidity can vary considerably
too and depends on your proximity to
bodies of water, vegetation, being in a
valley and so on.
Faulty LCD screen for BackPack
Firstly, congratulations on achieving
Celebrating 30 Years
30 years. Thirty years of producing a
truly quality product reflects passion
and commitment. You have, I believe,
contributed, in a big way, to the education of many of today’s electronics
engineers; by firstly kindling their interest in the subject and then by showing them where a career in the industry might lead.
I believe you have contributed, both
directly and indirectly, to the advancement of humanity. Also many have
become materially better off through
your endeavours. For me, I am still
being thoroughly entertained each
month. I am not a whiz so I get a big
thrill from making things from recycled parts and getting them going with
PICAXE and now Micromite.
On that topic, I built the Micromite
Plus LCD BackPack V2 in May 2017
but ran into problems running the GUI
CALIBRATE command. The following
is an example of what happens when I
try to calibrate the touchscreen:
> gui calibrate
Warning: Inaccurate calibration
> gui calibrate
Warning: Inaccurate calibration
(calibration could complete
twice)
> gui calibrate
Error: Touch hardware failure
> gui calibrate
Done. No errors (calibration
successful)
> gui test touch (however test
touch failed three times)
> gui calibrate (tried to re-calibrate)
Error: Touch hardware failure
...and so on.
After installing the replacement programmed Micromite chip you so kindly
sent me, I became very despondent as
the touchscreen still didn’t respond
correctly. It still had intermittent failures so I put the project aside.
I was then greatly heartened to find
others with very similar problems, as
per “BackPack problems may be due
to bad LCD connections” in Mailbag,
December 2017, so I dusted off my
BackPack and started “hiking” again.
I checked my construction again and
finding no faults, reconnected the LCD,
fired it up and guess what, it works. I
was so excited I went and hugged my
darling wife!
Problem is, I don’t know exactly
what fixed it. The only difference is
that when I reassembled the LCD to the
BackPack, I left out the four small Nysiliconchip.com.au
lon washers. This would have brought
the two boards closer by about 0.5mm
and also allowed the male and female
headers to further engage, maybe creating a better connection.
Now the “calibration” and “gui test
lcdpanel” commands execute OK.
However, there are missing pixels on
my screen. If I colour in the entire
screen there appears a grid of vertical
and horizontal lines where the pixels
do not respond to touch. Has anyone
else reported this fault? Are we dealing with a dud batch of LCD boards?
Stephen Somogyi,
Barrington, NSW.
Response: it does sound like your original problem was due to intermittent
bad connections on the LCD header.
Yours is the first report we’ve had of
missing pixels/rows/columns on the
LCD screen.
We have had a few people complain that the touch controller doesn’t
work and we replaced the screens in
those instances, and a couple of other
screens that were totally dead.
A few were also replaced because they were damaged in transit
(cracked). Overall they do not appear
to be too unreliable but the defect rate
is still higher than we would like. We
will send you a replacement screen as
yours seems to be faulty.
Using relays to switch 3-phase mains
I found the Lath-E-Boy Controller project in the January issue
(siliconchip.com.au/Article/10933)
interesting. But I have a comment regarding the text in the breakout box
on page 43, titled “Using it with a
3-phase motor”.
It says that RLY3 will need to be a
four-pole type to allow it to switch
all three phases. That's fair enough
but it will need to be a relay specifically designed for switching threephase mains.
That's because there's nominally
400V DC between phases (415V DC
for 240VAC). The relay will need sufficient internal dielectric strength and
physical separation between contacts
to handle this.
I built a relay box some years ago
using 250VAC-rated Omron relays
and switching three-phase mains, it
generated a loud bang and welded all
contacts together upon first operation!
I'd be inclined to err on the safe side
and use a 250VAC-rated relay (eg, the
Jaycar model suggested for singlephase use) to drive a 415V four-pole
contactor. A contactor with a 12V coil
would remove the requirement for an
extra relay. Cheers and keep up the
good work.
Kit Scally,
Canberra, ACT.
WRESAT article enjoyed
Thank you for continuing the great
tradition of in-depth science-technology articles. Catching up on my wet
weather reading with the covers on in
Adelaide, and after the recent publicity of the WRESAT launch anniversary
and interviews on the ABC, I greatly
enjoyed reading the WRESAT article
in the October 2017 issue.
It took me back to my visit to the
Woomera museum in winter 2008
and staying in the Redstone block at
the ELDO. I found the other resources
page very useful.
I started reading electronics magazines (and constructing projects) at the
age of 13 while the last moon landings
were being made. The only launch I
have ever attended was the Woomera
weather balloon. Keep up the good
work and congratulations on the 30th
anniversary.
Roger Curtain,
Williamstown, Vic.
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Celebrating 30 Years
May 2018 13
Fancy a quick aerial taxi ride to the airport . . . or perhaps to a fancy
restaurant? That dream may become a reality sooner than you think.
Some very large companies, including Airbus, Bell Helicopter, Boeing,
Daimler, Intel, Toyota and Uber, as well as many smaller ones, are
involved in the development of aerial drone taxis. And some are
planning to have that taxi service available as early as 2020!
Kitty Hawk’s “CORA” – now flying in
trials in New Zealand (see panel page 23).
Courtesy www.kittyhawk.com
A
By Dr David Maddison
lmost two years ago (August 2016) we looked at
Personal Flight Vehicles and their future (www.
siliconchip.com.au/Article/10035). In that time,
some have disappeared completely, some are still in planning and some are actually in production.
But most of those featured were not intended for commuter use, nor did many have the option of operating autonomously.
So we thought it opportune to look at the subject again,
with particular emphasis on aircraft intended for public
passenger use.
Based on quadcopters
These vehicle are primarily based on the familiar quadcopter or other multi-rotor
formats used for hobbyist and
professional photographic
“drones” or more correctly,
unmanned aerial vehicles.
Quadcopters (four rotors)
or other multi-rotor aircraft
such as hexacopters (six) or
octocopters (eight) are an
attractive and potentially
cheaper option than helicopters for commuter use, for a
couple of reasons.
They are mechanically
much simpler, as their blades
14
Silicon Chip
are usually fixed pitch (rather than variable pitch) and they
have a potentially smaller landing footprint than helicopters of the same passenger capacity. They also usually use
electric motors for propulsion, which are easier to maintain than internal combustion motors.
Some of the first attempts at vertical flight in the early
years used multi-rotor craft similar to quadcopters but they
were mechanically complex and very difficult, if not impossible, to effectively control.
The advent of high speed computers, three-axis accelerometers and solid state gyroscopes now enable these
aircraft to be controlled with
simple commands, eg, speed,
yaw, pitch and roll that are
One major problem yet to be fully solved with electric aircraft translated into complex comand passenger drones in particular is the length of time required mands to control the aircraft.
to recharge their batteries. Most passenger drones will be used
In this article we will surlike taxis and therefore will have a large number of relatively short vey some of the large number
trips with battery recharging required after each trip.
of passenger drones now unAs an example, a trip of ten minutes might require a few hours der development.
to recharge the batteries. This will adversely affect the economNote that while many comics of operation and one solution may be a hybrid system with panies have passenger drones
a liquid-fuelled generator to recharge the batteries in flight or a in development, relatively
replaceable battery pack system.
few have flown prototypes
Uber has partnered with ChargePoint (www.chargepoint. and many will inevitably fail
com), a company that makes electric vehicle infrastructure, such to survive.
as charging stations, to develop a standardised rapid charging
Some of the illustrations
connector that will fit any electric VTOL vehicle that uses its shown are artist’s impresUber Elevate Vertiports (see below). The system is planned to sions; very few actually show
be ready by 2020.
the aircraft in flight.
Battery Charging
Celebrating 30 Years
siliconchip.com.au
Uber vision for the future
showing various flight paths of
Uber Air vehicles around a city.
Airbus CityAirbus
Airbus Pop.Up
The CityAirbus by Airbus (www.airbus.com) is designed
for an air taxi role and will carry up to four passengers.
Initially there will be a pilot but the aircraft will operate
autonomously once regulations permit.
Eight propellers and motors are used and in each ducted fan nacelle there are two motors and two fixed pitch
propellers.
The motors are Siemens SP200Ds with an output of
100kW each. There are four battery packs with a combined capacity of 110kWh, with a total power delivery of
up to 560kW.
The aircraft can cruise at 120km/h with an endurance
of 15 minutes. So it has a range of up to 30km. Unmanned
flights are expected to start at the end of this year.
This is a demonstration concept only and not intended to
be built. It is a joint exercise between Airbus engineers and
automotive engineers at the Italian design company Italdesign. The concept has either an automotive “undercarriage”
or a quadcopter “over-carriage” attached to a common passenger module. The module can also be carried by other
modes of transport such as rail.
A video “Pop.Up” may be viewed at siliconchip.com.
au/link/aajf
siliconchip.com.au
Celebrating 30 Years
May 2018 15
Airbus Vahana
AirSpaceX
AirSpaceX (http://airspacex.com) [not related to Elon
Musk’s SpaceX] is developing the MOBi 2025 which carries a range of modules for different purposes such as passengers or freight.
It will have a range of 115km and a cruise speed of 241kph.
It will operate either autonomously or with a pilot.
A TEDx talk about eVTOL flight by Jon Rimanelli, founder
of AirSpaceX: “Traffic is taking over our lives. The solution
is to look up. | Jon Rimanelli | TEDxDetroit” siliconchip.
com.au/link/aajh
Airbus Vahana prototype first test flight which occurred
on January 31, 2018 in Oregon, USA. Another flight
occurred the next day.
A3 by Airbus (www.airbus-sv.com) is the advanced projects and partnerships division of Airbus in Silicon Valley,
California. The single-seat Vahana has eight motors and
propellers on two tiltable wings. The wings rotate for vertical take-off and rotate again for forward flight. It is 6.2m
wide, 5.7m long, 2.8m high and has a maximum take-off
weight of 745kg.
Its cruise speed is 175km/h and each motor is rated at
45kW. The Vahana is equipped with a ballistic parachute
as a safety measure. Video: “Airbus Vahana Flying Taxi”
siliconchip.com.au/link/aajg
Artists impression of the Vahana when fully developed.
AirSpaceX MOBi 2025. It has a range of modules for
different purposes such as passengers or cargo or
specialised modules for other purposes such as military
surveillance.
Another concept by AirSpaceX is the MOBi One. This
electric passenger drone will have a range of 104km, cruise
at 240km/h with a maximum speed of 400km/h, a passenger capacity of 2-4 and be capable of piloted or autonomous
operation. It will be 10m long, 12m wide and 3m tall. Production is expected to start in 2020.
See video: “Mobi-One: AirSpaceX’s autonomous,
electric air taxi lands in Detroit”
siliconchip.com.au/link/aaji
AirSpaceX
MOBi One concept.
Multi-rotor flight mechanics
In a conventional winged aircraft, variations in roll, pitch and yaw
are made with aerodynamic control surfaces but in a multi-rotor
aircraft (which usually lack control surfaces), these variations are
effected by altering the rotational speed of one or more propellers.
In a quadcopter, one pair of propellers rotate in one direction
and the other pair in the opposite direction.
This is to counteract the tendency of the aircraft to rotate in
the opposite direction to the propellers, as would be the case if
they all rotated in one direction. In helicopters, this tendency is
counteracted by the tail rotor, or more rarely by a contra-rotating
pair of main blades.
When the speed of all propellers is increased, the vehicle goes
up; conversely when the propeller speed is decreased the vehicle descends.
16
Silicon Chip
To make a quadcopter in an “x configuration” roll or pitch pairs
of propellers corresponding to the desired direction are sped up.
For example, to pitch forward, the speed of the two rear propellers is increased or to roll to the right the two left side propellers
are sped up.
Pairs of propellers are matched in speed to prevent the quadcopter rotating due to torque reaction. If the quadcopter is to be
deliberately rotated about its yaw axis, opposite pairs of propellers are slowed or sped up (compared to the other pair) which removes the balance against the torque reaction and the quadcopter
will rotate about its yaw axis.
In multi-copters with more than four sets of propellers such as
hexacopters and octocopters control of the vehicle is similar but
with more groups of propellers being controlled.
Celebrating 30 Years
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Aurora eVTOL
Safety and Regulations
Concept of Aurora eVTOL in production form.
Aurora Flight Sciences (www.aurora.aero/evtol), owned
by Boeing, is developing the eVTOL passenger drone. It is
an electric design with eight propellers for vertical lift plus
a wing with a pusher propeller for horizontal cruise. It will
carry two passengers including pilot or cargo.
Operational testing is anticipated to start in 2020 in Dallas-Fort Worth, USA and Dubai, UAE.
Uber has partnered with Aurora to be the manufacturer
of one of the drones it intends to use for its Uber Air service. Video: “Aurora Flight Sciences’ Electric VTOL Aircraft” siliconchip.com.au/link/aajj
Subscale demonstrator of Aurora eVTOL aircraft in a test
flight. During the this test flight there was a successful
transition from vertical to forward flight.
Image credit: Karen Dillon, Aurora Flight Sciences.
Bartini Flying Car
The Russian Bartini.
The electric Bartini Flying Car by Bartini in Skolkovo,
Russia (https://bartini.aero) will be offered either as a two
or four-seat model and uses ducted fans for vertical take-off,
after which the fan pods are rotated for horizontal flight. It
uses variable pitch propellers.
siliconchip.com.au
In contrast to helicopters, multi-rotor aircraft cannot auto-rotate to enable a relatively safe landing in the event of an engine
failure – providing there is somewhere safe to land!
And unlike almost any other aircraft, most proposed “passenger” drone designs are unable to glide any distance (if at all) in
the event of loss of power.
So additional levels of redundancy for critical aircraft systems
such as twin motors coupled to twin propellers, partitioned power
sources (ie, all batteries normally contribute to flight but if one
bank fails remaining ones can supply power to all motors), redundant flight control systems and even a ballistic parachute
may be needed.
A ballistic parachute can be ejected from, then open and save
the aircraft at a relatively low altitude; they are becoming more
common on light aircraft now.
Regulations
As there are (as yet) few or no regulations allowing for the flight
of autonomous passenger drones in most jurisdictions, one way
these drones may be introduced is to fly them with pilots first,
until regulations can be established for autonomous operations.
This assumes that the vehicles can gain appropriate airworthiness certification, given their radical differences compared to
existing certified aircraft types.
In April 2017, A3 by Airbus (a division of Airbus Industries)
in partnership with the Association for Unmanned Vehicle Systems International (AUVSI) [www.auvsi.org] called for industry
co-operation in developing standards for “urban air mobility”.
At a workshop held at the Airbus Experience Center in Washington, DC, which included participants from the US Federal
Aviation Administration (FAA), the two key regulatory areas considered were certification of autonomous passenger aircraft and
air traffic management of such aircraft.
Currently there is no clear pathway to certification of autonomous passenger aircraft, including airworthiness standards for
Vertical Take-off and Landing (VTOL), electric propulsion, fly-bywire systems, software and sense-and-avoid systems.
Such a pathway for certification needs to be developed.
In terms of air traffic management, such aircraft need to be
managed in point-to-point autonomous operations in an environment that also includes
manned aircraft. Rules
would also be required
that allow for Beyond Visual Line of Sight (BVLOS)
operations and operation
over people.
A ballistic parachute
(such as that seen
here on a small
unmanned drone)
could save an aircraft
that has run out
of battery charge
or has a motor or
control failure.
Such parachutes are
already used on many
manned light aircraft.
Image courtesy Mars
Parachutes.
Celebrating 30 Years
May 2018 17
It is designed to be able to use hydrogen fuel cells when
suitable models are available which will dramatically extend its range. The cost is expected to be a relatively low:
US$100,000 to $120,000. The company plans to demonstrate flight of a two-seat model later this year (2018) and a
possible four-seat model in 2020. Tests will be conducted
in Dubai, Singapore or Sydney. Funding for this project is
via the Blockchain.aero consortium.
This aircraft has unusually detailed specifications published for it, such as: width 4.5m, length 5.2m, height 1.7m,
range 150km or up to 550km with hydrogen fuel cells, payload 400kg, take-off weight 1100kg, lift to drag ratio 4 to
5, propeller loading 146kg/square metre, battery weight
320kg, battery density 200Wh/kg with the possibility of
up to 700Wh/kg with hydrogen fuel cells.
Battery capacity is 64kWh with the possibility of up to
224kWh with hydrogen fuel cells, power output 30kW, eight
thrusters each rated at 40kW, maximum altitude 3000ft,
cruising speed 300km/h, energy used for flight 51kWh,
energy used for one minute of hover 5.3kWh, energy used
for 30 minutes of cruise 45.9kWh, energy reserve 13kWh,
energy used per 1km of flight at cruise 0.30kWh, energy
used per minute of cruise 1.5kWh.
A video (computer generated) of this vehicle can be seen
at “Bartini Vision 2020 - Bartini Aerotaxi Is Man’s Wheels
In the Air for Blockchain community” siliconchip.com.
au/link/aajk
Bell Air Taxi
Carter CarterCopter
Electric Air Taxi
Carter Aviation Technologies in Texas, USA (www.cartercopters.com) are developing an electric helicopter based
around their highly efficient “slowed rotor” technology.
They are also working in collaboration with Uber to develop a four-passenger drone that can cruise at 280km/h.
It has a rear-mounted rotor that provides an anti-torque
force for the main rotor up to a speed of 160km/h. Then
the main rotor is disengaged from the engine and the antitorque rotor turns to become a thruster and thus the aircraft operates like an autogyro.
The main rotor is 10.4m in diameter and the rear rotor is
3.0m. The maximum payload is 363kg. The empty weight
of the vehicle is 1451kg. The range of the vehicle is from
about 180km to 256km depending on payload and speed.
For detailed technical analysis of the design decisions
made for this aircraft, see: siliconchip.com.au/link/aajm
Cormorant and CityHawk
Bell Air Taxi concept.
Bell Helicopter company (www.bellhelicopter.com) is
also working with Uber to develop an air taxi but is a concept only at this stage. See: siliconchip.com.au/link/aajl
Taxi, sir? Rendition of the CityHawk on the streets of
Manhattan
Passenger space in the Bell Air Taxi concept.
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Silicon Chip
The Cormorant is being developed by Israeli firm Urban
Aeronautics (www.urbanaero.com as part of their “Fancraft” series of VTOL vehicles, without external propellers
and with internal ducted fans powered by a single gas turbine engine. The autonomous military aircraft is designed
to take a 500kg payload of cargo or battlefield casualties.
This payload limit imposed by the international Missile
Celebrating 30 Years
siliconchip.com.au
DeLorean Aerospace DR-7
Artist’s conception of CityHawk flying over an urban area.
Note the large internal counter-rotating ducted fans and
associated vanes which are steerable.
Technology Control Regime which also applies to military drones. See the video at: “Cormorant UAV (formerly
AirMule) Pattern Flight Over Terrain (short)” siliconchip.
com.au/link/aajn
In April 2017 it was decided to design a vehicle based on
the Cormorant for civilian use as an air taxi for four people
as well as for emergency medical transport use. This vehicle is called the CityHawk. It will use a gas turbine engine
at first but will later may be converted to compressed hydrogen at 10,000psi, or battery power.
As of November 2017 the Cormorant was fitted with a
Safran Arriel 2S2 735kW gas turbine engine. The plan with
the CityHawk is to relocate the engine from the centre to
the side to enable a passenger compartment to be installed
there and to add an additional engine on the other side for
redundancy in the event of one engine failure. A ballistic
parachute will be fitted.
Some specifications for the CityHawk are as follows:
empty weight 1170kg, maximum take-off weight 1930kg,
maximum speed 270km/h, range with four people 150km
plus 20 minute reserve, range with pilot only 360km with
20 minute reserve.
Video: “CityHawk: the flying car you’ve been waiting for”
https://youtu.be/A1TPviF8YqU
DeLorean Aerospace (www.deloreanaerospace.com) is
developing the patented DR-7 which has two tiltable ducted fans which are horizontal for take-off and are rotated for
forward flight, with lift being generated by wings.
Ehang 184
Ehang, based in China, is developing the single-passenger Ehang 184 drone. It is reported to be very close to
market, assuming regulatory permission is granted. It is a
four arm, eight motor, eight propeller aircraft that weighs
260kg, has a cruise speed of 100km/h, a flight duration of
25 minutes and can carry a payload of 100kg. Recharging
takes one hour. There have now been numerous manned
flights of this drone (see below).
Note that in the company’s own promotional video there
is an eight arm, sixteen propeller two passenger model that
is also designated an Ehang 184 but there is no mention of
this on the company website at www.ehang.com
See the video at: “EHANG 184 AAV Manned Flight Tests”
https://youtu.be/Mr1V-r2YxME This has been widely broadcast in recent news bulletins.
Flexcraft
Flexcraft Consortium (http://flexcraft.pt/en) of Portugal
is designing a nine-person plus pilot hybrid electric aircraft. It has two fans in its wings for vertical take-off and a
separate motor for forward flight. Quoted range is 926km,
with a fuel capacity of 532 litres. Different passenger and
cargo modules can be attached.
Look mum, no hands! One of the few drones already flying: the two-seat model of the Ehang 184 in a manned flight test.
siliconchip.com.au
Celebrating 30 Years
May 2018 19
US$59,000) but their latest project is to make a patented
five seat “flying taxi” passenger drone “Formula” which
they say they’ll place into commercial service sometime
this year.
It uses a linear crank-less “free-piston” petrol engine to
drive a turbine to produce electric power for propulsion.
It has 48 vertical thrusters at four corners plus four horizontal thrusters and foldable wings that can be deployed
for forward flight. The company quotes a remarkably affordable US$97,000 for this aircraft. Its range is quoted as
450km with a speed of 320km/h. Video: “Formula Project
by Hoversurf” https://youtu.be/sxoG3eT6WJ8
The Portugese “Flexcraft” hybrid electric VTOL.
I.F.O. Jetcapsule
HopFlyt
I.F.O. above a city street. Landing gear folds down to form
legs. The capsule is lowered for entry and exit.
HopFlyt’s eight-engine, four-person “Venturi”.
Founded in December 2016, HopFlyt of Maryland,
USA (https://hopflyt.com) are developing the four-person
Venturi. It has its propellers mounted in venturi channels within tiltable canard wings to give improved efficiency and longer range. It has eight wing channels containing the motors and contra-rotating propellers. Some
specifications: weight 815kg, wingspan 8m, length 7m.
Video of test of 1/7th scale model: “HopFlyt Hover Test”
https://youtu.be/oc_hUL0v-3s
HoverSurf Formula
HoverSurf (www.hoversurf.com), a Russian company
with offices in Virginia, USA, are currently making or about
to make a quadcopter format “hoverbike” (priced from
HoverSurf’s Taxi R-1
20
Silicon Chip
The I.F.O. or Identified Flying Object is a proposed design by Pierpaolo Lazzarini (www.lazzarinidesign.net) for
Italian company Jet Capsule. To be powered by eight electric motors, it has an estimated speed of 200km/h with a
claimed duration of around an hour. Video: “I.F.O. The
Identified Flying Object” https://youtu.be/3ysmPDwVZFI
Jetpack Aviation
Jetpack Aviation (www.jetpackaviation.com) of California,
USA was first mentioned in the August 2016 SILICON CHIP
article on Personal Flight Vehicles for their personal Jetpack.
Their unnamed multi-rotor aircraft is in very early stages of development but is expected to have 12 motors and
propellers mounted on six arms. It will carry one person.
Jetpack Aviation’s concept for a passenger drone.
Celebrating 30 Years
siliconchip.com.au
Jetpack are looking at extending flight times beyond
the 20 minutes it would have with batteries by the use of
a small generator, possibly based on a small gas turbine
engine. Two arms will fold so that it can fit in a domestic
garage. There will be a number of safety features such as
a ballistic parachute and an energy absorbing structure.
See video at “Jetpack company developing new electric
VTOL flying car” https://youtu.be/Bfo_iOjsbvc
For an interview with one of the inventors, Australian
David Mayman, see https://newatlas.com/david-maymanvtol-flying-car-jpa-interview/47700/
Joby Aviation
It is envisaged that a passenger will
request a Lilium Jet directly from
their smartphone.
The 36 electric jets work much like
turbofan motors in a conventional jet aircraft but the compressor fan at the front
is turned by an electric motor rather than
a gas turbine. The wing assemblies are
rotated for vertical take-off.
There is a ballistic parachute for
safety and multiple redundancy in
the engines and other flight systems.
Video: “The Lilium Jet – The world’s first
all-electric VTOL jet” https://youtu.be/
ohig71bwRUE
Passenger Drone
California-based Joby Aviation (www.jobyaviation.com)
is developing an electric S2 two-passenger aircraft which
has 16 propellers – 12 for vertical lift, which fold back for
forward flight and four mounted on the rear of the wings
for forward propulsion. This company has received US$100
million in backing from Toyota and Intel.
The aircraft is powered by lithium nickel cobalt manganese oxide batteries and will be capable of flying
at 320km/h. The cost of the aircraft is expected to be
US$200,000. Video: “30-sec TECH: the amazing Joby S2
tilting VTOL multi-rotor” https://youtu.be/AYhs4OFEgDw
Lilium
The German Lilium Jet drone (https://lilium.com) is a
unique five-seat electric jet with a large 300km range and
a 300km/h top speed. The first manned flight is envisaged
to be in 2019 and it is expected consumer flights will start
in 2025. The price for a typical airport to city centre flight
such as from JFK Airport to Manhattan is anticipated to be
less than a typical road taxi.
siliconchip.com.au
Passenger Drone operating autonomously – without
pilot or passenger.
Passenger Drone (http://passengerdrone.com) is a California-based company developing a two seat autonomous
passenger drone, about the size of a small car. It can also
be flown manually if desired and has eight motor positions
with sixteen motors and sixteen propellers.
When operated in autonomous mode the aircraft is monitored and guided via the company’s “Ground Control and
Monitoring Center” using the 4G mobile telephone network.
Some specifications of this vehicle are as follows: empty
weight including batteries 240kg; maximum take-off weight
360kg, maximum payload 120kg; maximum thrust 560kg;
maximum speed 60-70km/h; flight time 20-25 minutes
(without range extender); dimensions 4.2m x 2.3m x 1.8m.
No details on the range extender option have been released but it is assumed to be a small petrol or jet fuelpowered generator to recharge the batteries.
A corporate promotional video can be seen at “Passenger
Drone - The most advanced Manned Autonomous VTOL
in the World !!!” https://youtu.be/IStmyk3R3Hc
Also see “Passenger Drone First Manned Flight” https://
youtu.be/V3pi4HfQ0Gc Videos of the avionics system display can be seen at “PassengerDrone Avionics Demo Video
1” https://youtu.be/L43JZ3_CgAI; “PassengerDrone Avionics Demo Video 2” https://youtu.be/o4sZIWZFYKc and
“PassengerDrone Avionics Demo Video 3” https://youtu.
be/OvHhK-8LkQA
Celebrating 30 Years
May 2018 21
Sky-Hopper
Terrafugia TF-X
Sky-Hopper
proof of
flight concept.
Sky-Hopper (http://tinagebel.wixsite.com/sky-hopper) is
a Dutch company in an early start-up phase and currently only have a proof-of-flight concept. Their stated goal is
to “develop an eco-friendly electric aircraft that is as safe,
reliable, affordable and easy to use as a mainstream car”.
The skeletal prototype has 16 motors and several flight controllers and it will be developed as autonomous vehicle.
Video: “Sky-Hopper, first manned flight of electric multicopter” https://youtu.be/Omv_WdryGRc
Volocopter
SureFly
The Workhorse Surefly (http://workhorse.com), based
in Ohio, USA, is a drone under development that will offer both an autonomous mode and piloted mode. It has a
petrol-powered generator based upon an automotive engine as well as batteries that drive eight motors at four locations with eight propellors. It seats two including the
pilot and has a kerb weight of 500kg and a maximum takeoff weight of 682kg.
The 4-cylinder 2-litre engine drives two 100kW generators, which also keep the batteries charged. They comprise
a twin pack each of 7.5kWh which will enable a 5-minute
flight time in the event of an engine or generator failure;
otherwise the engine and generator will power the eight
3-phase AC motors.
The top speed is about 113km/h with a service ceiling
of 4000ft and an estimated range of 113km (70 miles). It
has a ballistic parachute as well as redundancy in other
critical systems.
Videos: Static ground test, “Workhorse Surefly CES 2018
Test” https://youtu.be/8gIBujk7cAE; “SureFly Octocopter Behold The Future” https://youtu.be/hr8vksAI3jI
The Workhorse Surefly. For storage, the rotor arms can be
folded down to the side of the vehicle for storage.
22
Silicon Chip
Terrafugia (www.terrafugia.com) is designing
an autonomous mass market four-seat flying car.
It will have folding
wings with wingtip
mounted propellers used
for vertical flight which
later fold back to allow
The TF-X in driving mode. . .
forward propulsion via a
and flying mode. The wing-tip
rear mounted ducted fan.
propellers (used for vertical
One megawatt (1341hp) take-off) are folded back during
of power is available at forward flight and thrust comes
launch via a gasoline hy- from a rear-mounted ducted fan.
brid electric drive.
Range is 800km, cruise
speed is 320km/h and
pricing will be in the
range of high end luxury
cars. Video: “The Terrafugia TF-X” https://youtu.
be/wHJTZ7k0BXU
Rendition of the Volocopter 2X in operation.
The fully electric Volocopter 2X (www.volocopter.com/
en) is an 18-propeller 2-seat autonomous drone and has
the backing of German car company Daimler. Each of the
18 motors delivers a power output of 3.9kW and it has a
cruise speed of 100km/h.
One of the advantages of this design is that it is relatively
quiet. It is currently certified in Germany as a light sport
multicopter and also as an ultralight.
Its maximum take-off weight is 450kg (including a payload of 160kg) and its range is 27km at the optimal cruise
speed of 70km/h. It has a ballistic parachute and redundancy in motors and propellers as well as other safety systems.
Its nine separate battery packs can be fast-charged in under 40 minutes, or slow-charged in under two hours and
the packs can also be quickly swapped if necessary.
Videos: “Volocopter’s flying taxi takes off at CES” https://
youtu.be/tODIvUmH6cs and “Making of Dubai Public Demonstration Flight” https://youtu.be/ROJ76foyihs
Celebrating 30 Years
siliconchip.com.au
XTI Aircraft TriFan 600
The Y6S in forward flight.
The XTI TriFan 600. Once the plane reaches cruise speed,
a door closes over the fuselage-mounted fan.
XTI Aircraft Company, based in Colorado, USA (www.
xtiaircraft.com) is designing the hybrid fuel and electric
power TriFan 600, primarily aimed at the business market. As the name suggests this aircraft has three combined
lifting and forward propulsion fans.
The company claims this aircraft can be flown under
current aviation regulations. The maximum cruise speed
will be 556km/h and the range will be 2222km. Cruise altitude will be 29,000ft.
There is space for a pilot and five passengers. Video:
“XTI Aircraft Video 2017 with Slides.mp4” https://youtu.
be/AOapUy1ee64
Y6S
The 2-seat Y6S is being developed by Autonomous
Flight Ltd (www.autonomousflight.com) in the UK. It is a
tri-fan design with a tiltable pair of front rotors and wings
for forward flight.
It will have a maximum speed of 113km/h, 1500ft cruising altitude and a range of 130km.
Manned test flights will start later this year. A remarkably
inexpensive price of US$27,500 has been stated.
Video: “‘Y6S’ drone will be the first in the world to carry passengers and could revolutionise city commutes”
https://youtu.be/CtMPe24-WtA
Uber flight demonstrations
in 2020
As stated earlier, Uber are not building any aircraft of
their own but are working in conjunction with other manufacturers.
By 2020, Uber will need aircraft such as those mentioned
in this article which are in advanced stages of development
for its demonstrator flights; vertiport infrastructure to be
built; permission to fly in the airspace of the flight corridors
between vertiports and appropriate regulations to allow
operation of the aircraft and certification of aircraft types.
Initially aircraft will be piloted but they will eventually
become autonomous.
By the same year, Uber plan to have overcome three
factors:
(1) efficient flights, meaning the passenger drones can
fit into existing airspace use;
(2) acceptance of noise made by the vehicles and
(3) acceptance by passengers that the vehicles are safe.
Stop Press: Kitty Hawk’s “Cora” trialling across the pond . . .
As this issue went to press, inforIt appears to be supported at
mation came through that Google Cohigh level in the NZ government,
Founder Larry Page’s company, Kitty
with Prime Minister Jacinta Ardern
Hawk, had received certification to
helping to launch the Cora trial.
trial their “Cora” self-flying taxi in
The company’s aim is to have a
New Zealand, under approval from the
commercial flying taxi service in
New Zealand Government Department
operation before 2022. While it can
of Civil Aviation.
land and take off from a normal
It had previously been certified as an
runway, Cora doesn’t need to do so.
experimental aircraft by the US FAA. Kitty Hawk’s “Cora” in flight
And with a noise level far beThe fully-electric, two-seat Cora has
low that of a helicopter, it will not
an 11m wingspan, with twelve wing-mounted rotors to cause great disruption when it does pop down in builtenable vertical take-off and landing (VTOL) plus a sin- up areas – in places like building rooftops and car parks.
gle larger pusher-prop to enable it to fly like a normal
It is somewhat ironic that Kitty Hawk chose New Zeaaircraft once airborne. (see also photo page 14).
land for this next phase of aviation: Kitty Hawk is of
Capable of completely autonomous flight, Cora is said course the site celebrated as the first manned flight by
to have a range of 100km and a top speed of 150km/h.
the Wright Brothers on December 13 1903 – but many in
New Zealand was chosen as a test site because of its New Zealand claim that local farmer Richard Pearse flew
more relaxed regulations for such projects than, say, (and landed) a heavier-than-air machine on 31 March
Australia.
1903, nine months earlier than the Wright Brothers. SC
siliconchip.com.au
Celebrating 30 Years
May 2018 23
Swallow a Tiny
Capsule to Check
Your Gut!
by ROSS TESTER
Researchers at two Melbourne universities have come up with a new
way to analyse the gases in your gut, which could provide answers
to many medical mysteries. And that information can be transmitted
instantly to a smartphone app via Bluetooth.
W
e’re all used to swallowing
capsules containing medicine. They’re designed to
stay “sealed” until they reach a part of
the body where the medicine needs to
go, then the capsule dissolves.
For example, depending on the capsule skin composition and/or thickness, it might stay intact until it reaches the stomach, or the intestine, etc.
More recently, medical specialists
have been using another type of “capsule”, one definitely not designed to
break down because it contains an
ultra-miniature camera, along with
a light source and a memory card.
They’re intended to take photos every so often as they pass right through
the system.
After a period of up to few days,
they’re recovered (use your own imag-
ination!) and the photos are analysed
(perhaps a poor choice of word, there)
to find evidence of, say, ulcers, blockages, cancers and other nasties.
After suitable treatment, the camera
can be used over and over – they’re
still too expensive to be throw-away
items, though that is changing.
Another type of capsule can be used
to measure and analyse body temperature, respiration, blood and waste
chemistry and so on.
But until now, they’ve all suffered
the same disadvantage – clinicians had
to wait until the capsule emerged before the data could be read.
Gas-sniffing capsule
A group of researchers from Melbourne, led by Kourosh KalantarZadeh of RMIT University and Peter
Gibson of Monash University has recently published a paper in “Nature
Electronics” detailing a tiny ingestible electronic capsule which reports,
via radio, the concentration of various
gases in the human gut.
When paired with a pocket-sized
receiver and a mobile phone app, the
pill reports conditions in real-time as it
passes from the stomach to the colon.
Such data could clarify the conditions of each section of the gut, what
microbes are up to and which foods
may cause problems in the system.
Until now, collecting such data has
been a challenge.
Methods to bottle it involved cumbersome and invasive tubing and inconvenient whole-body calorimetry.
Early human trials of the gas-smiffing capsule have already hinted that
The electronics are packed into a capsule measuring just 26 x 9.8mm. It uses a receiver connected to a smartphone app.
24
Silicon Chip
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At 26 x 9.8mm, it’s larger
than typical medicine capsules –
but still well within the “comfort
zone” of most people.
the pill can provide new information
about intestinal wind patterns and gaseous turbulence from different foods.
The capsule is made according to
the “000” standard: 26mm in length,
with a 9.8mm external diameter.
It includes sensors for CO2, H2 and
O2 gases that occur in various aerobic
and anaerobic conditions, a temperature sensor, a microcontroller and a
433MHz transmission system plus the
button cells which power it.
One end of the capsule contains a
gas-permeable membrane that allows
for fast diffusion of gut gases.
A non-transparent, polyethylene
shell houses the internal electronic
components. The polymer shell is machined in two pieces, sealed together
using a bio-compatible adhesive.
Interestingly, the capsule was made
non-transparent, as volunteers showed
hesitation in swallowing capsules
with transparent covers, where they
could see the electronic circuits inside.
A combination of thermal conductivity and semiconducting sensors,
with an extraction algorithm, generate
the gas profiles and determine the gas
concentration in both aerobic and anaerobic segments of the gut.
siliconchip.com.au
The gas-sensing capsule uses a separate receiver which can be linked by
Bluetooth to a smartphone or computer. It is not yet in commercial production.
Celebrating 30 Years
May 2018 25
Inside the gut gas measuring capsule prototype. It is made
from non-transparent material because volunteers showed
a reluctance to swallow anything where they could see
electronics inside!
Capsule accuracy for measuring H2 and O2 was found to
be better than 0.2%, and for CO2 it was 1%. The key technological differences between human gas sensing capsules
and those used for animal trials on pigs is the implementation of an advanced gas detection algorithm. This uses
heat modulation to distinguish between H2 and CO2 with
much higher accuracy. An oxygen sensor is included to
locate the capsule in different gut segments, along with a
temperature sensor to measure the core body temperature
and sense the excretion of the capsule out of the body of
volunteers (when the temperature drops below 35°C).
The capsules also incorporate membranes with embedded nanomaterials that allow for the fast diffusion of dissolved gases, while efficiently blocking liquid.
Following trials on pigs, the researchers tested the capsule in six healthy people.
For the first, researchers monitored the pill’s intestinal
trek using ultrasound and linked locations with gas profiles. Overall, it took 20 hours to get from one end to the
other, spending 4.5 hours in the stomach, 2.5 hours in the
small intestine, and 13 hours cruising through the colon.
In that time, the pill took continuous gas measurements,
revealing potentially useful information in addition to gut
position.
For instance, CO2 and H2 levels peaked in the early hours
of its time in the colon while O2 levels crashed throughout
this stretch of the trip.
That correlates with how anaerobic bacteria (those that
live without oxygen) inhabit the colon and ferment undigested food into short-chain fatty acids that play significant
roles in our health and metabolism.
In the next human trial, the researchers had one person
swallow the pill twice. The first time, he ate a very highfibre diet (50 grams per day) for two days prior to swallowing the pill. Two weeks later, he swallowed another pill after eating a low-fibre diet (15 grams per day) for two days.
In the high-fibre test, the man passed the pill in about 23
26
Silicon Chip
One end of the capsule has a semi-permeable membrane to
allow gases to enter and be analysed; however liquids are
prevented from entering
hours. But he was not happy about it. The super dose of fibre caused abdominal pain. In its four hours in the colon,
the pill recorded elevated levels of O2, which could mess
up anaerobes. Indeed, an analysis of fecal bacteria during
this phase showed a shift toward species associated with
poor gut health.
There were also problems in the low-fibre scenario. The
pill took a little more than three days to work its way out.
It spent 13 hours in the stomach, 5.5 hours in the small intestines, and a huge 54 hours in the colon. In fact, about 36
hours after taking the pill, the man was given a high dose
of fibre to try to move things along.
Prior to that fibre intervention, H2 gas levels in the colon
had plummeted, suggesting a drop off in fermentation. It
picked back up 12 hours after the fibre treatment.
Last, the researchers recruited four more healthy patients to pass the pill. Two ate a high-fibre diet (though not
quite as high as the first trial), while the remaining two ate
a low fibre diet. This showed similar patterns seen in the
earlier trials.
In an accompanying editorial, mechanical engineer Benjamin Terry of the University of Nebraska-Lincoln concluded that the capsules “have remarkable potential to help us
understand the functional aspects of the gut microbiome,
its response to dietary changes, and its impact on health.”
“It might not be too long before a routine healthcare visit
involves a check of your vital signs and a request to swallow a tiny electronic monitoring device,” he added.
SC
Acknowledgement:
Information based on Nature Electronics, Vol 1, January 2018
Celebrating 30 Years
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Introducing:
Part 1:
by Duraid Madina and Tim Blythman
Our all-new 800W
Uninterruptible
Power Supply
(+)
We’ll say it right up front: this will not be a cheap project to build. But
if you do build it, we believe you will end up with a UPS that is a better
performer than anything else on the market at even two or three times the
price. And even then (unlike most commercial units), the design is quite
flexible if you wish to expand its already exceptional capabilities. So if
you’re in the market for a UPS (and who isn’t, with the quality [?!] of mains
power these days?) you will go a long way to find better value than this.
28
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Celebrating 30 Years
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We
searched
high and
low for a
high quality,
low-cost case to
house the UPS but
proved the two terms
are mutually exclusive!
However, this case is ideal for
the job, being pre-drilled and
slotted for excellent ventilation.
I
f you aren’t familiar with the concept of an Uninterruptible Power Supply (UPS), it provides a back-up for
the mains supply to an important piece of equipment
(such as a corporate server or other mission-critical system), so that it won’t shut down during blackouts.
The typical use for a UPS is to give plenty of time – a
few minutes to perhaps an hour or so – to save work before it’s lost – or in large organisations, long enough for a
mains generator to be fired up and take over.
Some UPSes are designed to give hours, and occasionally days or even more, of power to enable an enterprise
to keep working as if the blackout didn’t exist. But these
are VERY expensive systems, relying on a large (and even
more expensive!) battery bank to keep them supplied.
A UPS is now standard equipment for computer systems
in commerce or industry but they are becoming more popular for home or small business.
Laptop computers don’t need a UPS as their internal
battery does the same job. But the printer or large monitor
connected to a laptop will obviously cease working during a blackout. Powered via a UPS, work can continue.
Disaster power
A UPS like the one we are describing could be used
in a lot more situations.
ifications
Features & spnsec
plug
For example, perhaps with a few modifications, it could power all your computers, your
modem and all your entertainment equipment in the event
that you experience a blackout for many hours.
It could keep some or most lights working, allowing an
orderly (and safe) exit from deep within otherwise-dark office blocks (sorry, you’ll have to use the stairs as the lifts
won’t be working!).
Or if you have a much longer blackout, it could perhaps
run your refrigerator for several days during a long power
outage which could occur after a bush fire, a big storm or a
flood. That would mean you would not lose any food due
to spoilage. And of course, it means that you can keep your
mobile phones and notebooks and tablets fully charged so
you can stay in contact with the outside world.
Just how long you could run a refrigerator would depend on the power rating of its compressor and the temperature setting. Or perhaps it could allow you to also run
a gas heater or oven which requires 230VAC at low power
to run the igniter and the control electronics.
So a UPS is an important accessory for a variety of reasons in both business and in the home.
But why would you want to build this one instead of
buying a commercial unit? Wouldn’t that be cheaper? Not
in this case.
• Power input: 10A mai
s
• Output socket: four switched GPO
800W
er:
pow
ut
• Continuous outp
• Peak output power: 1200W
• Battery capacity: 588Wh
• Inverter type: pure sinewave
, 4h <at> 135W, 5h <at> 110W
, 1h <at> 500W, 2h <at> 260W, 3h <at> 175W
• Approximate runtime: 35m <at> 800W
<40ms (two mains cycles)
• Response time after mains failure:
cycle)
g back to mains: ~20ms (one mains
• Power interruption when switchin
ustable)
• Brownout threshold: 200VAC (adj
AC (adjustable)
260V
d:
shol
thre
out
cut• Over-voltage
y 5 hours from flat
• Battery charging time: approximatel
• Quiescent current: 19W
battery
ing off inverter, battery charging, low
• Status indicators: mains good, runn
UPS software)
rce
ng interface (compatible with open-sou
• PC interface: USB serial monitori
s are nearly flat
erie
batt
n
kout; continuous tone sounded whe
• Audible alert: beeps during a blac
e
harg
battery cut-out with zero battery disc
• Protection: 10A mains fuse, lowe)
harg
disc
es (full
• Battery longevity: at least 1500 cycl
siliconchip.com.au
Celebrating 30 Years
LiFePO4 batteries
This UPS has high capacity, very safe LiFePO4
batteries which can be
deep discharged without damage – something
that can easily occur in
a long blackout. Plus
it uses an Arduino to
monitor and control it.
And while this UPS
is conservatively rated at 800W, it actually
employs a 24V DC to
240VAC true sinewave
inverter which is rated
to deliver 1200W or up
to 2400W surge (useful
to start motors or run a
microwave oven for a
short period).
May 2018 29
To a large degree, our 800W UPS is based on existing modules which
we connect together in an appropriate manner. The photos above
show two of the main components: at left is the pair of Drypower 12V,
23Ah batteries which we connected in series for 24V DC, while at
right is the Giandel pure sinewave inverter, which is used to power
equipment from the batteries when mains power goes down.
The conservative limitation to 800W is determined by
the batteries but you could possibly run at the full 1200W
continuous output of the inverter for short periods without any problems.
So let’s talk about the batteries. Most commercial UPSes
come with sealed lead-acid (SLA) batteries. The problem
with SLA batteries, apart from being very heavy and bulky,
is that they are easily damaged or even destroyed if you
allow them to discharge below 11V – and that can easily
occur in a typical UPS.
We speak from experience – and we’ve heard that our
experience is not uncommon.
We used to have a UPS on the SILICON CHIP office server,
because blackouts are fairly common in the northern beaches of Sydney (we’ve had quite a few in the last decade). But
the one we were using failed because its lead-acid battery
was deeply discharged by a long blackout over a weekend.
We replaced it but only a few months later, it went bad
again after yet another extended blackout so we just gave
up and removed it.
As it uses Lithium iron-phosphate batteries our new UPS
design is a lot more robust than that commercial unit so
it won’t fail in the same manner. They will survive hundreds, if not thousands of blackouts (perish the thought!).
Why did we use lithium iron-phosphate batteries instead
of lithium-ion or lithium-polymer? In a word: safety! They
are much less likely to catch fire!
While a fire is unlikely with a Lithium-ion or Lithiumpolymer battery, it isn’t unheard of – and the sudden failure of a battery of this size could be very dramatic. And
since this is a DIY project, we can’t rule out mistakes being made during construction.
So we wanted the safest possible option.
While some UPSes are able to guarantee no loss of power
at all during a blackout, most operate by feeding the incoming mains directly to the load, as long as the mains voltage
is OK, but then switching over to inverter operation if the
mains waveform goes bad or disappears entirely. Normally
this switching is done with a relay or relays and so there is a
very brief switch-over period where the load gets no power.
But most devices will not be affected by this. For example,
30
Silicon Chip
all desktop and server computers these days run from a
switchmode power supply, which rectifies the mains to
charge a large capacitor or capacitors to around 350V, which
then power the switching circuitry.
It takes some time for the filter capacitor bank to discharge to the point where the output voltages are affected.
So as long as the switch-over time is short, the supply and
thus computer will operate uninterrupted.
Similarly, a motor-driven appliance such as a refrigerator will have some inertia and the loss of mains for a fraction of a second will likely not affect its normal operation.
And most low-cost UPSes do not have a sinewave output
when running off the battery. They usually have a “modified square wave” or even a square wave output, since it’s
easier to produce and the switchmode supply in a computer
will run just fine off a square wave (or even high-voltage
DC, for that matter).
Our design uses a “proper” sinewave inverter so is usable with a much wider range of devices.
Want more grunt?
Now before we go on to discuss the design philosophy
behind this project, we should point out that many aspects
can be modified or greatly expanded to suit your particular application.
Want higher power output or much longer run for more
extended blackouts? No problem, just substitute a bigger
inverter and a bigger (much bigger) battery bank.
Want to operate from solar panels to use it for off-grid
power? Again, no problem (we will discuss these various
possibilities in a later article).
12V or 24V operation?
Our initial design brief for this project was to have a
rated output of at least 500W. So what would be the right
battery voltage?
To deliver 500W, a 12V inverter would require an input
current of over 40A, which would be harsh on the battery
and inverter and require very thick cables. So we started
looking for inverters and batteries in the range of 24-48V.
It quickly became apparent that 24V batteries and in-
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These three photos show some of the other modules we used – while not so fundamental as those
shown opposite, they’re important nevertheless! At left is the Victron Battery Balancer, required because
we used (for economy reasons) two 12V DC batteries instead of a single 24V DC. Even when adding in the cost of the
balancer, two batteries are a much better proposition. Centre is the 12V switchmode power supply used to power the
Arduino, while at right is the 24V, 5A mains charger for the batteries.
verters were less common and more expensive than 12V
types, and 36V/48V batteries and inverters even more so.
Two 12V batteries (24V) seemed like the best compromise.
We decided to use two Drypower 23Ah 12.8V LiFePO4
batteries in series, which were supplied by Master Instruments (Cat No IFM12-230E2). We considered using a 25.6V
LiFePO4 battery but a similar capacity model cost significantly more than twice as much as the two 12V batteries.
Using two batteries meant that we would need a charge
balancer, to ensure that the two battery voltages are kept
similar – but even when we include the cost of the balancer, the two 12V batteries are still significantly cheaper.
This battery bank then drives a Giandel 24V/1.2kW
pure sinewave inverter which we bought from the Giandel Australia website for $138 plus postage (Cat No PS1200DAR/24). This is excellent value.
It comes with a pair of battery cables with eyelet lugs
and also a remote control that attaches to the unit using
telephone-style flat cabling. We hooked this up to an Arduino, which is then able to monitor the inverter status
and switch it on and off.
This inverter has a typical efficiency figure of around
90% and it includes a cooling fan and substantial heatsinks so it can deal with the approximately 100W of dissipation at full power.
As already noted, the inverter is rated at 1.2kW (2.4kW
peak) but the specified batteries can’t supply sufficient
current to allow such a high power delivery. They are rated at 35A continuous which works out to around 800W
at the output when you take inverter losses into account.
That’s still handily above the target we had set ourselves
for this project.
The 588Wh nominal capacity of the battery bank is specified at a 5-hour discharge rate, which is what our specification of five hours battery life for a 110W load is based on.
Curves are not provided to show how capacity diminishes
at higher discharge rates but lithium-chemistry batteries
normally have a low internal impedance so we believe our
moderate de-rating of capacity with increasing load should
be approximately right.
We also considered designing a “line interactive” or “onsiliconchip.com.au
line” UPS, where the load is always powered by the inverter and the charger provides the DC current to operate
it when mains is available. This avoids the need to switch
the load between mains and the inverter and also, poor
mains power quality (ie, distorted waveform) is not transferred through to the load.
However, that approach would require a charger capable
of around 30A which would be large and quite expensive
and it would also be less efficient due to the constant conversion from 230VAC to low-voltage, high-current DC and
back to 230VAC. Hence, we decided to design a “standby
UPS” instead, as presented here.
By the way, the inverter output is specified as 240VAC;
somewhat higher than 230VAC. So when the UPS switches
the load to the inverter, the supply voltage will typically
increase slightly.
But this is still well within the Australian mains specification of 230VAC+10%,-6% so it should not present any
problems. In many parts of Australia, the mains supply is
typically above 240VAC anyway.
Charging and mains switching
Having decided on the two most important components
of our UPS system, ie, the batteries and inverter, there were
still other important details to be determined. These included how the batteries are charged once mains returns
after the inverter has been operating (and indeed, are kept
charged long-term), how we determine when to switch the
output sockets from mains to the inverter output and how
that switching is performed.
Charging is quite simple; we purchased a 5A mains
charger designed for LiFePO4 batteries and it’s permanently
wired to the incoming mains socket so that whenever mains
is present, it’s charging the batteries. Like other Lithiumbased rechargeable batteries, LiFePO4 use a constant-current/constant-voltage (CC/CV) charging scheme.
So the charger will deliver 5A to the batteries until the
voltage across them reaches 29.2V (14.6V per battery or
3.65V per cell). It will then hold the terminal voltage at
29.2V as the charge current decreases until it reaches a low
level, at which point the batteries are considered charged.
Celebrating 30 Years
May 2018 31
Fig.1: block diagram of the SILICON CHIP
800W UPS. Much of the “magic” is in
the Arduino software and shield which
will be described in detail next month,
along with full circuit and construction details.
However, the inverter needs to be kept on constantly so
that it’s always ready to take over, should the mains supply cut out. Therefore, it draws several watts from the batteries constantly and the battery voltage will never quite
reach 29.2V (it sits at around 29.15V). This should not pose
a problem; they are effectively float charged.
Enter the Arduino controller
We’re using an Arduino Uno to monitor the mains voltage, via a small mains transformer. The primary of this
transformer is connected across the incoming mains supply
and the voltage from the secondary is divided down and
fed to one of the Arduino’s analog inputs via a biasing network which keeps the analog pin voltage in the 0-5V range.
The Arduino is constantly sampling the mains waveform and if it detects an under-voltage or over-voltage condition, or a significant deviation from a sinewave, it immediately switches the output over to the inverter. It only
switches the output back to mains when it determines that
the mains waveform and voltage are stable and have been
for a few seconds.
The switching is accomplished by using three DPDT relays which are controlled via a relay driver shield and the
Arduino. Both the Active and Neutral wires are switched.
Relay logic for safe switching
Now refer to Fig.1 which is the block diagram for our
high power UPS. It shows how the three relays are arranged.
RLY2 is the mains changeover relay and it is arranged so
that there is no possible way that the output of the inverter
could be connected to the mains. RLY1 is used to connect
mains to RLY2 (and on to the output) while RLY3 is used
to connect the inverter to RLY2 (and on to the output).
Why do we need three relays when it might seem that
only one or two relays might be able to switch the load
between incoming mains or the output from the inverter?
32
Silicon Chip
The reason for using three relays in this manner is that
there is no way to precisely lock the phase of the inverter
output waveform to the incoming mains waveform.
While both are nominally at 50Hz, they could be in phase,
180° out of phase or anywhere in between. The phase difference between them is likely to slowly drift over time,
due to slight differences in the two frequencies.
So it’s entirely possible that the momentary mains voltage could be +350V while the momentary inverter output
voltage could be -350V. A single 250VAC-rated relay is not
designed to handle 700V DC between two terminals on the
same pole. There could be an insulation breakdown and/
or major contact arcing and this could destroy the inverter.
By having an extra relay between each AC source and
ensuring that both RLY1 and RLY3 are off at the time when
RLY2 is switching, we avoid applying any more than the
normal mains peak voltage across a single relay.
When the unit is powered off, all the relays are off and
so the output sockets are not connected to anything, except
for the Earth pins, which are connected to mains Earth and
also the unit’s chassis.
When the unit powers on, it checks the mains voltage and
waveform and assuming they are good, it switches RLY1
on. This connects mains to the output sockets and load(s).
If mains goes bad or disappears altogether, the unit immediately switches RLY1 off. Then, after a short delay, it
switches RLY2 and RLY3 on. So the load is briefly disconnected from mains altogether (for around 10ms), then
connected to the output of the inverter, which is already
running.
When mains power comes good again, RLY3 is switched
off and after a brief delay, RLY2 is switched off and RLY1
switched on. Again, there is a brief period where the outputs are not connected to either mains or the inverter. This
ensures a safe change-over.
The unit is also designed to perform a sequenced change-
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over in this manner should its own power supply fail or
when it is purposefully switched off, using a switch mounted on the rear panel. This allows you to, for example, disconnect the UPS from mains so you can move it to a different location without it discharging its batteries.
Indicator LEDs
We’ve fitted three indicator LEDs on the front panel, so
you can tell what is happening. The green LED at far left
is on continuously while the output is connected to mains
and flashes if mains is not present or not clean.
The yellow LED in the middle lights continuously when
the output is being fed from the inverter. While the output is running off mains (and the green LED is solidly lit),
the yellow LED will also flash to indicate that if there is a
problem with the inverter, such as if the Arduino detects
it is not running when it should be.
The red LED at right starts flashing when the battery
voltage drops. The flashes become faster as the batteries
discharge until it is on continuously when the remaining
charge is around 10%.
The unit is also fitted with a piezo buzzer which beeps
intermittently while the output is running off the inverter and it changes to a continuous tone when the batteries
are nearly flat.
If the battery voltage drops below about 21V, the Arduino switches the inverter and relays off. It also shuts itself
down. The drain on the battery becomes almost zero. While
these batteries do incorporate their own over-discharge
protection, we feel it’s still good practice to minimise the
load at low voltages.
The unit is able to “bootstrap” itself and power back up
when mains returns and this procedure is described below.
It can also be manually switched off and powered back on
later if necessary.
Powering itself
We need a source of 12V DC to run the three relays and
Parts list – 800W Uninterruptible Power Supply (UPS)
1 vented 3U rack-mount case, 559mm deep [Bud Industries
RM-14222+TBC-14253+TBC-14263]
[Digi-Key 377-1392-ND; 377-1396-ND; 377-1397-ND]
2 Drypower IFM12-230E2 12.8V 23Ah Lithium Iron
Phosphate batteries [Master Instruments]
1 Victron Energy 2x12V Battery Balancer [Master
Instruments – www.master-instruments.com.au]
1 Giandel PS-1200DAR/24V Pure Sinewave Inverter with
cables [www.giandel.com.au]
1 5-7A LiFePO4 charger [Master Instruments, AliExpress]
1 DETA 6224B Silver Four Outlet Power Point or similar
[Bunnings 4430423]
3 12V DC coil, 10A 240VAC cradle relays [Jaycar SY4065]
3 DPDT chassis-mount relay cradles [Jaycar SY4064]
1 12V 1.3A enclosed switchmode power supply
[Jaycar MP3296]
1 12.6V CT 7VA transformer [Jaycar MM2013]
4 screw-on equipment feet [Jaycar HP0832]
1 3AG safety fuseholder [Jaycar SZ2025]
1 3AG 10A 250VAC fuse
1 connector to suit battery charger (see text)
1 Arduino Uno or compatible
1 Freetronics 8-Channel Relay Driver Shield
[Core Electronics Cat CE04549]
1 Arduino control shield (details next month)
1 green chassis-mount LED with chrome bezel
[Altronics Z0265, Jaycar SL2645]
1 yellow chassis-mount LED with chrome bezel
[Altronics Z0224] with 1kW series resistor
1 red chassis-mount LED with chrome bezel
[Altronics Z0264, Jaycar SL2644]
3 1kΩ 0.25W resistors
1 NO momentary pushbutton switch
Fasteners
8 M5 x 90-100mm bolts or machine screws
12 M5 x 10mm machine screws
28 M5 nuts
6 M4 x 10mm machine screws
6 M4 nuts
6 M4 shakeproof washers
siliconchip.com.au
4 M3 x 32mm machine screws
6 M3 x 15mm machine screws
28 M3 x 10mm machine screws
1 M3 x 6mm machine screw
34 M3 flat washers
34 M3 nuts
4 25mm-long 3mm ID untapped spacers
8 15mm-long 3mm tapped Nylon spacers
4 M3 x 25mm Nylon machine screws
Cables, wires and insulation
1 2-wire mains cable with figure-8 plug*
2 3-wire mains cables with moulded 10A plugs*
1 100mm length of 40A+ rated wire
1 2m length red medium duty hookup wire
1 2m length black medium duty hookup wire
1 2m length yellow medium duty hookup wire
1 1m length white light duty hookup wire
1 1m length yellow light duty hookup wire
1 1m length red light duty hookup wire
1 1m length black light duty hookup wire
1 cable gland to suit 3-wire mains cable
[eg, Jaycar HP0732]
1 150mm length 6mm diameter heatshrink tubing
1 50mm length 10mm diameter heatshrink tubing
1 50mm length 16mm diameter heatshrink tubing
1 50mm length 20mm diameter heatshrink tubing
* Can be cut from spare power cables, extension cords or
similar
Other hardware
2 Carinya MABF2101 Make-a-Bracket flat plates, 100 x 200
x 1mm [Bunnings 3975858]
6 Carinya MA0003 25 x 25 x 40 x 1mm angle brackets
[Bunnings 3975955]
5 adhesive wire clamps
6 small P-clamps
10 4mm crimp eyelets
2 red 6.3mm insulated crimp spade lugs (for the power
switch)
30 small black cable ties
Celebrating 30 Years
May 2018 33
5V DC for the Arduino. While we could simply run both
off one of the batteries, this would not be ideal as it would
present an unbalanced load to the overall battery pack. It
would also place a load on the batteries when they are
nearly flat.
To avoid this problem, we have fitted a small mains
switchmode power supply inside the case and wired this
in parallel with the output sockets. So when mains power is
present, this powers the Arduino and relays and when running off the inverter, the inverter powers this switchmode
converter instead. When the output is switched off, this
totally disconnects the Arduino and relay power supply.
So during a short blackout, the Arduino will be powered
by the inverter and will simply switch back to mains power
once it’s restored. But if there’s a long blackout and it powers down, when mains power comes back, the output is
disconnected. So how does it start back up and switch on
the inverter (in case it’s needed later) and RLY1?
The answer is that we’ve added a small relay on the Arduino shield which normally connects the secondary of
the mains-sensing transformer to a diode. Current flows
through that diode and into the 12V supply bypass capacitors, providing an initial source of power for the module.
(Note that this fourth relay is not shown in the diagram of
Fig.1 but it is on the control shield).
Once RLY1 is on, that relay is also energised, disconnecting the transformer from the diode. This means that
the transformer is not being loaded, so its output is once
again a good proxy for the mains voltage.
In fact, this relay is briefly energised before RLY1, giving
the Arduino the chance to verify that the mains waveform
is clean before the load is connected. The inverter can not
necessarily be used at this stage because the batteries are
probably flat. But they will start charging as soon as mains
returns and will soon be ready for use.
Switching it on without a mains source
We have considered that this unit may also be useful as
a source of emergency power. For example, you could use
it to back up the power to your fridge so that the contents
don’t go off during a blackout but you might later decide
to unplug your fridge and move it to power some other
equipment such as lights, a TV and so on.
In this case, during an extended blackout, you may need
to switch the UPS off and then later switch it back on but
unless you have a generator, you won’t have a source of
230VAC to “bootstrap” it.
So we have added a momentary pushbutton switch to
the front panel which briefly connects the nominally 24V
battery bank to the input of a 12V regulator which then
feeds the Arduino and relays.
Holding this button for a few seconds gives the unit
enough time to switch the inverter on and power the load
from the inverter. You can then release the button and the
unit will continue to run until it is switched off or the battery goes flat.
We’ve also fitted a rocker switch on the rear panel which
allows you to shut down the internal switchmode supply
that powers the Arduino and relays. This means you can
unplug the UPS from the mains, flick the switch and it will
gracefully shut down.
The batteries will remain charged and it can be powered
back on later by flicking the switch again and plugging it
34
Silicon Chip
back into mains, or alternatively, using the pushbutton
method described above.
Inverter control
The inverter has a “soft start” feature which ramps its
output voltage up over a few seconds when it’s switched on.
This would be handy in many situations but is unwanted
in a UPS because you need to be able to switch over to inverter power in a very short time. But there’s also a delay
of around 0.5-1 second between pressing the on/off button
and the inverter powering up, so clearly we have no choice
but to run it constantly, ready to switch over.
We do need to ensure it’s shut down when the batteries
go flat. While it has an internal under-voltage lockout that’s
actually very close to the minimum specified voltage for
these batteries (20V total, 10V per battery), it isn’t that accurate. We should ideally switch the inverter off before the
battery voltage drops that low. And we also need to ensure
it’s switched on when the unit is starting up.
The inverter we’ve specified is supplied with a small “remote control” box that has a single LED and a pushbutton
switch. It’s attached to the inverter via a 4-wire telephone
style flat cable. The same controls (LED and button) are
provided on the inverter itself.
The LED and button share one common connection, with
the LED wired between the common terminal and a second wire. A small current flows through this loop when
the inverter is powered. The button briefly connects this
common wire to a third wire. If the button is held down for
around half a second, the inverter starts up or shuts down.
We’ve interfaced the inverter with the Arduino using
two optocouplers. The Arduino drives one to simulate a
button press, shorting the two wires to switch power. The
second optocoupler LED is connected in place of the LED
on the remote control box and pulls an Arduino pin low
when the inverter is operating.
A software routine on the Arduino compares the inverter
status to the desired status and “presses” the button when
necessary to turn it on or off.
This isolation allows the Arduino ground to be connected to the battery negative terminal and it can then monitor the battery voltage using a simple resistive divider
(100Ω/10kΩ) to one of its analog pins, allowing it to determine the charge state, both for display purposes and to
decide when to shut the inverter down.
Choosing a case
Commercial UPSes of this size are often housed in rackmounting cases. This is convenient since they can then
mounted in a server rack, along with the servers they are
protecting. But rack-mount cases can also be fitted with
feet and used in a standalone manner.
We spent some time trying to find a low-cost metal box
to build the UPS into but in the end, couldn’t find a good
solution. It was also difficult to find a rack-mount case
which would fit all the required hardware (due to the required depth of at least 450mm) but we eventually located
one at a reasonable price.
It’s three rack units tall (3RU = 133.5mm), the standard
19-inch width and made from aluminium by a US company
called Bud Industries. It is supplied as a kit which includes
the front, back, sides and hardware while the top, bottom,
rack rails and handles are available separately.
Celebrating 30 Years
siliconchip.com.au
The completed UPS (sans lid!)
showing the internal layout.
The two batteries are clamped
under the punched metal plates
at the right while the pure
sinewave inverter is on the
left. We’ll show the layout
and construction detail next
month. While you might
think the silver Deta
four-outlet power point
on the rear panel seems
like gilding the lily
somewhat, they’re only a
couple of dollars dearer
than a boring old white
one . . . and it really
looks the part, matching
the aluminium case!
We haven’t bothered fitting the rack rails or handles to our
prototype but they aren’t expensive or difficult to obtain.
Luckily, availability is good; the case is available from
US electronics retailers Digi-Key and Mouser and they
both offer free express international delivery if you order
the required items together (see parts list). We also fitted
it with instrument feet from Jaycar as there are quite a few
exposed screw heads on the underside.
We’ve opted for a solid base and vented lid as the inverter and batteries can get quite warm during operation. The
side panels have many drilled holes which provides decent
ventilation and also makes fitting cable clamps quite easy.
One of the good aspects of using a natural aluminium
case such as this one is that it’s quite easy to Earth the entire chassis. This is critical for safety; if a mains wire comes
loose inside and contacts the case, it will cause the fuse to
blow. Otherwise, the case could become live which would
be very dangerous.
We have Earthed the rear and bottom panels separately,
with the other panels electrically connected via common
screws and also direct panel contact.
Sourcing a battery charger
Master Instruments can supply two suitable battery chargers, the Fuyuan FY2902000 (2A) or FY2907000 (7A). The
2A version has a standard 2.1mm inner diameter DC plug
so you just need a matching socket while the 7A version
uses an XLR plug; suitable sockets are readily available
(eg, from Jaycar).
Other chargers are available but they may come with
a different plug and so you will need to find a matching
socket. Or alternatively, cut the plug off and crimp some
eyelet terminals onto the bare wires for direct connection
to the battery terminals.
Regardless of which charger you use, it must be designed
specifically for LiFePO4 batteries and have a charge termination voltage of 29.2V. While these batteries are quite
robust, they may not last very long if regularly charged to
the wrong voltage.
Control algorithm
The most critical part of the Arduino software is the
“mains-good” detection algorithm. The transformer secondary voltage, which is a proxy for the mains voltage, is
siliconchip.com.au
sampled 1000 times per second, ie, 20 times per cycle for
a 50Hz supply. These samples go into a 32-sample buffer,
so there is just over one full cycle worth in the buffer at
all times.
To convert this into a meaningful number, we calculate
both a root-mean-squared (RMS) average and measure the
peak-to-peak voltage.
For a sinusoidal signal, the RMS value is exactly equal to
the peak-to-peak value divided by 2 x √2, or approximately
2.8284. The peak-to-peak calculation is usually quicker to
pick up excessively high mains voltage while the RMS calculation is faster at detecting a brownout or blackout, the
latter often being detected within a quarter of a cycle (5ms).
The RMS calculation starts by taking the average of the
ADC readings to establish a ‘mean’ that we can reference
the values to. We then add the squares of the differences
between our values and the mean.
Then we divide the sum by the number of samples –
this is our mean of squares, and its square root is the RMS
value, after which the scaling factor is applied to get our
actual RMS value in volts.
As soon as the mains voltage reading is found to be outof-bounds, the relay switching sequence begins, to transfer
the load(s) over to the inverter. The unit will not switch
the load back to mains operation unless the mains voltage
stays within a tighter set of bounds for several seconds.
This increase in the strictness acts as a kind of hysteresis, preventing the unit from switching back and forth if
the mains voltage is on the cusp of being too high or too
low. The unit will simply switch to the inverter in this case
and won’t switch back until the mains voltage goes back
to a more normal value.
The transformer introduces quite a bit of error into the
voltage measurements made by the Arduino (and to a lesser
extent, resistor and regulator tolerances). We will provide a
calibration process to allow you to set the thresholds more
accurately in a later article.
Construction
There will be detailed construction and wiring details
in the second article in this series, to be published in the
June issue. That article will also have details on the control
shield circuitry, including assembly instructions required
to build the driver shield.
SC
Celebrating 30 Years
May 2018 35
Turn things on or off if they’re too fast ... or too slow... etc!
Deluxe
Frequency Switch
by John Clarke
Switch devices on or off according
to the frequency of just about
any sensor signal up to 10kHz.
So you can switch something on
or off if a sensor signal frequency
goes above or drops below a
figure which you can easily set.
Features
• Energises a relay when a signal goes above a
preset frequency and keeps it on until the signal drops below a second preset frequency
• Adjustable hysteresis can be used instead of
setting upper and lower frequencies
• Switching frequency can be from 1Hz up to
10kHz.
• Adjustable switching delay
• Two sets of 5A changeover relay contacts
• Easy pushbutton set-up
• Can be set up on the bench or in situ
• Threshold can be set using a signal
generator or frequency meter (eg, DMM)
• On-board signal frequency range indicators
• Power, threshold and relay-on LED indicators
T
feathering blades on suitably and much more.
here are many applications for
equipped turbines.
It is also much easier to set up
a device of this type. Just some
Of course, there are countless oth- than our previous Frequency Switch
of the things we thought of “off
er uses – you’re probably thinking of in June 2007 (siliconchip.com.au/
the top of our heads” include:
• Cutting power (or fuel) to a motor others that suit your particular appli- Article/2261) and the main reason for
cation.
that is that it is based on a PIC16F88
if it exceeds a certain speed
As long as it has, or can be fitted rather than the LM2917 frequency to
• Switching a fan on at low vehicle
speeds to provide improved cool- with a sensor, to provide a frequency voltage converter. (That first Frequenwhich varies with speed, temperature, cy Switch was quite tricky to set up!)
ing.
• Giving a warning to change gears flow etc, you can use our new Deluxe
when the engine RPM is approach- Frequency Switch. It can do all of this Setting the two frequencies
You need to set up two
ing the tacho red line.
frequencies, not one as you
• Switching from long
might have thought.
to short intake run- Specifications
Why do you need two
ners at a particular en- Supply voltage: 10-16V
frequencies? We need to set
gine RPM to optimise Supply current: 20mA with relay off; 60mA with relay on
two frequencies because if
power delivery.
Signal frequency range: 1Hz to 10kHz
the signal from your cho• Switching off a pump
sen sensor varies by even
if a flow meter records Signal amplitude: >1.4V peak-to-peak
a small amount at close to
the water flow is out- Threshold setting resolution: 20Hz at 10kHz; 1Hz at 2.27kHz; 0.2Hz at
the switching threshold,
side a specific range. 1kHz; 0.002Hz at 100Hz.
the relay would be con• Switching on an alarm Hysteresis: 0-50%
stantly chattering on and
if wind speed exceeds Switching delay: signal period plus 0-500ms
off – not good at all. So
a certain threshold.
Signal frequency bands: <10Hz, 10-100Hz, 100Hz-1kHz, 1-10kHz
we set an upper frequency
• Applying a brake or
36
Silicon Chip
Celebrating 30 Years
siliconchip.com.au
threshold above which the sensor signal must rise before the relay switches
on. And then we set a lower frequency threshold below which the sensor
signal must drop before the relay is
switched off.
You can set the two frequencies
close together or far apart.
Setting the frequencies is dead-easy
and there are several methods for doing it. The first method is to feed in
your wanted set frequency, say 500Hz,
from an oscillator or other source to
the sensor input and then press switch
S2. Then feed in the wanted lower frequency, say 400Hz, and then press S1.
The second method is arguably even
easier. You just set one frequency, say
500Hz, and then use an on-board trimpot (VR1) to set the hysteresis. This
will effectively set the lower frequency
(down to a minimum of 250Hz in this
example) and you can tweak it at the
time of installation.
If you don’t have an oscillator you
could use the real signal that you intend controlling the unit with, so long
as you can hold steady it at the required frequency/frequencies for long
enough to press the switch(es).
Alternatively, if that’s too difficult,
you actually can get the microcontroller to generate the wanted frequencies.
This second method is more involved
than the first and we will describe the
procedure later in this article.
Detection time and delay
You can also configure the unit with
a switching delay which is adjusted
with trimpot VR2 and can be set between zero and 500ms (ie, half a second). This ensures that if the signal
frequency only momentarily
crosses one of the thresholds,
it will not cause the relay to switch.
The input signal
frequency must remain at or beyond
the threshold for the
entire delay time
before any relay
switching will occur.
Each time the frequency crosses the
threshold, the delay time starts again.
Fig.1: This block diagram describes how the microcontroller measures frequency.
If you prefer switching to happen
immediately then set the response
time to zero (ie, VR2 fully anticlockwise).
LED indicators
To help in the set-up and installation procedures, we have included
indicator LEDs to show when an input signal is present and its frequency range:
• LED2 lights for frequencies between
0.5Hz and 10Hz;
• LED3 lights between 10Hz and
100Hz;
• LED4 between 100Hz and 1kHz;
• LED5 for frequencies between 1kHz
and 10kHz and all four LEDs light if
the frequency is above 10kHz.
Other LEDs show when the set
threshold frequency is reached and
whether the relay is on or off.
Relay options
The relay is a double-pole changeover (double throw) type (ie, DPDT)
which can switch one or two loads,
each up to 5A/48V (8A if you use the
specified relay from Altronics).
You have the option to get the relay
to switch on if the sensor signal rises
above the threshold frequency (set by
Here’s the complete frequency
switch, ready to mount inside its case (it
suits a UB3 jiffy box but could also be mounted inside
the equipment it is controlling if there is room).
siliconchip.com.au
Celebrating 30 Years
S2) and switch off if the sensor signal
drops below the threshold set by S1.
The alternative is to get the relay to
switch on if the sensor drops below
the lower threshold frequency (set by
switch S1) and switch off if the sensor signal rises above the threshold
frequency (set by switch S2). The second mode is activated by installing a
link at JP1 on the PCB.
Block diagram
Fig.1 (above) shows how the Deluxe
Frequency Switch monitors the signal
frequency. The PIC16F88 micro’s internal clock is derived from a 20MHz
crystal which is driven by an internal
oscillator amplifier.
The resulting 20MHz clock signal
is divided by four to produce a 5MHz
signal which drives an internal 16-bit
timer, TIMER1. This comprises two
8-bit cascaded timers, TIMER1H and
TIMER1L.
We have implemented an 8-bit overflow counter (OVER) in the unit’s firmware. That extends TIMER1 out to 24
bits, so it rolls over every 3.355 seconds [or 224÷5,000,000]. This equates
to an input frequency close to 0.3Hz.
Hence, the unit is designed to handle
signals from 1Hz and up.
The input signal is fed to pin 6,
which is also the Capture/Compare/
PWM (CCP) pin. The Capture module hardware in the micro is
configured so that
on each positive
signal transition
at this pin (ie,
low-to-high),
the values of
TIMER1H and
TIMER1L are
copied into the
CAPTURE1H
and CAPTURE1L registers and
an interrupt flag
is set.
This then trigMay 2018 37
Fig.2: the circuit is based around a PIC16F88-I/P, which measures the incoming frequency and energises the relay if
the frequency is above or below certain values and whether JP1 is present or not. It also has pre-settable response
times and hysteresis to prevent “chattering”. LEDs give you visual indication of the operation as well.
gers an interrupt handler routine
which copies the contents of the OVER
register into the CAPTURE OVER variable.
The timers and overflow counters are
then reset to zero, ready to count until the next input positive going edge.
The captured count represents the
number of pulses from the 5MHz clock
signal over the period between the two
positive input signal edges.
So for example, a 1Hz input signal
will have a one-second period between
each positive edge. The count value
stored will therefore be 5,000,000
(5M). At 1kHz, the period between
positive edges is 1ms and the captured
value will be 5000.
To calculate the frequency, all we
need to do is to perform the calculation F(Hz) = 5,000,000 ÷ value. Or we
can calculate the period as P(s) = value ÷ 5,000,000.
But in reality, the micro just has to
convert the upper and lower threshold settings to these same count units
and then compare the counter values
38
Silicon Chip
to those stored values, to determine
whether either threshold has been
crossed.
On-board frequency
generation
Where the microcontroller produces
an output frequency for you to measure during adjustment as per setup
method on page 41), pin 6 (CCP1) is
configured differently. Rather than being in Capture Mode, with pin 6 as an
input, it is used in Compare Mode and
pin 6 is an output.
TIMER1 is still driven with the
same 5MHz signal but the TIMER1L,
TIMER1H and OVER registers are preloaded with values calculated from
the frequency to be produced. Each
time OVER register overflows, the pin
6 output toggles and new values are
loaded into the TIMER1L, TIMER1H
and OVER registers.
Because pin 6 toggles each time
the counters overflow, the output frequency would be half what you might
expect based on the period value for
Celebrating 30 Years
the required frequency. So we need to
divide the period by two to give two
separate half periods.
This means there will be an error
whenever an odd period value is used,
since dividing it by two will yield a
remainder of one.
To solve this, and avoid the inaccuracy, two different pre-load values are
used. They are used alternately to load
into the TIMER1L and TIMER1H registers. So the duty cycle will not quite
be 50% but the frequency produced
TP1 voltage
Hysteresis
(adjusted
with VR1)
when setting
upper threshold
5V
3.75V
2.5V
1.25V
625mV
312.5mV
50%
43%
33%
20%
12%
6%
Table 1: Hysteresis setting versus
voltage at TP1.
siliconchip.com.au
will be accurate.
The values from each of the separate
period values are loaded into the TIMER1L, TIMER1H and OVER counters
alternately. At the same time, the output at pin 6 is changed in level.
For those interested, the values to
pre-load into TIMER1L, TIMER1H and
the OVER variable are calculated as
224 - (5,000,000 ÷ f (Hz)) ÷ 2, with the
alternative value being one higher in
cases where 5,000,000 ÷ f Hz is odd.
Circuit description
The full circuit shown in Fig.2
is based on microcontroller IC1, a
PIC16F88. This monitors the input
frequency, jumper state (JP1 and JP2),
switch state (S1 and S2) and trimpot
settings (VR1 and VR2). It also drives
the frequency LEDs (LED2-LED5),
threshold LED (LED6) and the relay
coil (RLY1) and its associated LED
(LED7) via NPN transistor Q2.
Power is fed in via CON1 and the
supply is nominally 12V DC. Diode
D1 provides reverse polarity protection and its cathode connects directly to the positive terminal of the relay
coil, applying a nominal 11.4V to it as
well as to the 5V regulator, REG1 and
it powers the rest of the circuit.
A 10F electrolytic capacitor is used
to filter the supply voltage and transients are clamped using a 16V zener
diode (ZD1), with the peak current limited by the series 47Ω resistor.
The supply is further filtered by another 10F capacitor and then REG1
reduces the 11.4V supply to 5V for IC1
and input conditioning transistor Q1.
The power LED, LED1, is connected
across the 5V supply with a 3.3kΩ series current-limiting resistor.
The input signal is fed into CON2
and it’s AC-coupled via a 10F capacitor and 10kΩ resistor to the base
of Q1. The 470pF capacitor filters any
transients while diode D2 clamps the
base voltage at -0.7V for negative excursions. Q1 inverts and amplifies the
signal, suitable for the capture compare input (CCP1) at pin 6 of IC1.
Frequency measurement
modes
When the micro is configured to generate frequencies for setting the upper
and lower thresholds, the output signal appears at pin 6 and TP3. For this
to work, there must be no input signal at CON2 and this means that Q1
is biased off and it will not load the
siliconchip.com.au
Fig.3: component layout for the Deluxe Frequency Switch with a matching photo
below. We suggest using an IC socket for IC1 – and make sure when you place
the connectors, their wiring access holes all point to the outside of the PCB.
output signal from pin 6.
20MHz crystal oscillator X1 is connected to IC1, between its CLKO and
CLKI pins, to allow for accurate and
wide-ranging frequency measurements. The MCLR-bar reset input is
tied to the 5V supply via a 10kΩ resistor to provide a power-on reset for
the microcontroller.
Internal pullup currents within IC1
hold the RB1 and RB2 inputs high
when switches S1 and S2 are not
pressed and similarly, are enabled for
the RB5 and RB6 inputs which are connected to jumpers JP1 and JP2. These
inputs are pulled low if a switch is
pressed or jumper plug inserted and
this can be sensed by IC1.
Output pins RA0 (17), RB4 (10), RB7
(13) and RA1 (18) drive signal indicators LED2-LED5 via 3.3kΩ currentlimiting resistors at around 1mA each.
Similarly, output RA4 (pin 3) drives
the threshold LED, LED6. The RB3
output (pin 9) switches transistor Q2
on when it goes high. This transistor
in turn switches on the relay. Diode
D3 quenches back-EMF from the coil
as Q2 is switched off.
Celebrating 30 Years
LED7 is also switched on when the
relay is powered. It’s wired across the
relay coil and uses a 10kΩ series resistor due to the higher voltage (11.4V).
It provides the same current to LED7
as for the other LEDs.
Trimpots VR1 and VR2 set the default hysteresis and delay time and
both are connected across the 5V supply, with their wipers connected to
analog inputs AN2 (pin 1) and AN3
(pin 2) respectively. The voltages at
these pins are converted to digital values using IC1’s inbuilt 10-bit analogto-digital converter (ADC). The 100nF
capacitors between each of these two
pins and ground provide a low-impedance source for the ADC during
conversions.
Construction
The Deluxe Frequency Switch is
built on a double-sided PCB coded 05104181 and measuring 102 x
58.5mm. It will fit in a plastic utility
box measuring 129 x 68 x 43mm.
Follow the overlay diagram, Fig.3,
when installing the parts. Fit the resistors first. The colour codes are shown
May 2018 39
overleaf but we recommend that you
use a digital multimeter (DMM) to
check the values before soldering them.
Diodes D1, D2, D3 and ZD1 are next
and these need to be inserted with
the correct polarity, with the striped
end (cathode, k) oriented as shown
in the overlay diagram. Diode D2 is
the 1N4148 type while D1 and D3 are
1N4004.
Parts list – Deluxe
Frequency Switch
1 double-sided PCB coded 05104181,
102 x 58.5mm
1 DPDT 12V DC coil relay (RLY1)
[Jaycar SY-4052 {5A},
Altronics S 4270A {8A}]
2 2-way screw terminals with 5.08mm
pin spacing(CON1,CON2)
2 3-way screw terminals with 5.08mm
pin spacing (CON3)
2 2-way pin headers with shorting
blocks (JP1,JP2)
1 18-pin DIL IC socket (for IC1)
1 20MHz crystal (X1)
2 SPST PCB-mount tactile pushbutton
switches (S1,S2)
[Jaycar SP0600, Altronics S 1120]
2 PC stakes (TP GND,TP3)
Semiconductors
1 PIC16F88-I/P microcontroller
programmed with 0510418A.HEX
(IC1)
1 LP2950ACZ-5.0 low dropout
regulator (REG1)
1 BC547 100mA NPN transistor (Q1)
1 BC337 500mA NPN transistor (Q2)
1 16V 1W zener diode (1N4745) (ZD1)
2 1N4004 1A diodes (D1,D3)
1 1N4148 signal diode (D2)
7 3mm LEDs (LED1-LED7)
Capacitors
1 100µF 25V PC electrolytic
2 10µF 16V PC electrolytic
1 10µF non-polarised (NP) PC
electrolytic
4 100nF 63V/100V MKT polyester
1 1nF 63V/100V MKT polyester
1 470pF ceramic
2 27pF NP0/C0G ceramic
Resistors & Potentiometers (all 1%,
0.25W)
1 1MΩ 1 100kΩ
4 10kΩ
6 3.3kΩ 1 1kΩ
1 47Ω
1 10kΩ vertical multi-turn trimpot,
3296W style (VR1)
1 10kΩ mini horizontal trimpot, 3386F
style (VR2)
40
Silicon Chip
We recommend using an IC socket for IC1. Take care with orientation
when installing the socket and when
inserting the IC. For the test points, we
used two PC stakes, one for TP GND
and the other for TP3. We left the remaining test points as bare pads so a
multimeter probe can be inserted.
Install the two 2-way pin headers
for JP1 and JP2 and then follow with
the capacitors.
The electrolytic types must be fitted with the polarity shown (long
lead to pad marked plus; the stripe
indicates the negative side) and note
that the 10F NP capacitor is non polarised and so can be installed either
way around.
Next, mount transistors Q1 and Q2
and also REG1. Take care not to mix
them up as they come in identical
packages.
Trimpots VR1 and VR2 are next to
be fitted. They may be marked as 103
instead of 10kΩ. Orient VR1 with the
adjusting screw as shown.
CON1 to CON3 can now be installed. CON1 and CON2 are 2-way
types and CON3 comprises two 3-way
screw connectors dovetailed together.
Fit all connectors with the wire entry
to the edge of the PCB.
Finally, the LEDs and relay RLY1 can
be installed. We placed the LEDs close
to the PCB, but they can be mounted
higher or mounted off the PCB if you
wish, connected with flying leads.
Although presented as a bare PCB,
the unit fits in a UB3 Jiffy box. In this
case, attach the PCB to the base of the
box using spacers. First, mark out and
drill 3mm holes for each of the corner
mounting holes.
You will also need to drill holes at
each end of the box for cable glands. A
gland at one end is used for the power
and signal wires while a gland at the
other end allows the relay contacts to
be wired up as required.
Set up
You have several options for setting
the unit up. You can set it up before installation using or an oscillator or the
actual signal source (if it can be held
steady enough) when you install it.
1) Oscillator method: Power the unit
up with a 12V power supply wired to
CON1. Connect the oscillator to CON2.
Set the signal amplitude to 2V peakto-peak or 0.7V RMS.
Set the oscillator to your desired upCelebrating 30 Years
Using a tacho signal
Say you are using the engine tacho signal to switch the relay if a certain engine
RPM is exceeded – say 6000 RPM.
If you have a 4-cylinder, 4-stroke engine,
6000 RPM = 100 revolutions per second.
Since this type of engine fires two cylinders
per crankshaft rotation, then the threshold
should be set to 200Hz [100 x 2].
per threshold frequency (eg, 500Hz)
and press S2. Then reduce the oscillator to set the lower threshold (eg,
400Hz) then press S1. That’s all there
is to it.
If you want to set a single threshold
frequency (ie, the upper threshold) and
use the hysteresis setting, fit a link to
JP2. Then adjust trimpot VR1 for the
required hysteresis (percentage) while
you monitor the voltage at TP1. Then
set the oscillator for the desired frequency and press S2.
Alternatively, if you want to set a
single threshold frequency at the lower threshold and use the hysteresis
setting for the upper threshold, fit a
link to JP2. Then adjust trimpot VR1
for the required hysteresis while you
monitor the voltage at TP1. Then set
the oscillator for the lower threshold
frequency and press S1.
Table 1 shows some the relationship
between the voltage at TP1 and the
percentage hysteresis. For example, if
you set VR1 to give 1.25V at TP1, the
hysteresis will be 20% and the resulting lower threshold frequency will be
20% lower than the frequency you set
with switch S2.
Note that you can also set the unit
with only one threshold frequency and
that will mean the relay will latch on
when the signal goes above the threshold and will stay on until the power
is turned off.
To set just a single threshold frequency, set the oscillator to the desired frequency and then press S2.
Then disconnect the signal from CON2
and wait until the signal LEDs all are
off. Then press S1 to set the lower frequency to zero.
No link is required at JP1 if you want
the relay to switch on as the frequency
rises above the threshold set by S2 (and
turns off when the frequency drops below that set by S1).
Alternatively, install JP1 if you want
the relay to switch on as the frequency falls below the threshold set by S1
(and turn off when the frequency rises
siliconchip.com.au
above the threshold set by S2).
lier) you need to adjust
trimpot VR2. You can
set the delay anywhere
between zero and half
a second.
If you don’t want
a delay set VR2 fully
anti-clockwise.
2) Frequency meter method: The
advantage of this approach is that you
don’t need an oscillator but you will need
a frequency meter or
oscilloscope to measInstallation
ure the frequency appearing at TP3.
Connect the 10-16V
To get into this
DC power source between the
mode, connect your
+12V and GND inputs at CON1.
frequency meter or
For automotive installations,
DMM between TP3
automotive-rated wire should
and GND.
be used and the +12V termiSwitch off power,
nal needs to connect to the
hold down both S1
switched side of the ignition.
The PCB is designed to fit into a UB3 Jiffy box, as shown here –
and S2 and then
That way, the unit only opbut it could also be “built in” to equipment it is controlling. You
switch on the powerates when the ignition is
may also be able to source the 10-16V DC from that equipment –
er. The micro then
switched on and the vehicle
as long as it isn’t turned off by the frequency switch!
produces a 100Hz
battery won’t go flat after long
signal at TP3.
Then remove JP1, use S1 & S2 to ob- periods of being parked.
To adjust this default frequency to
tain the lower threshold frequency, inThe easiest way to connect the GND
obtain your desired upper threshold,
sert JP1 again and press S1.
terminal in a vehicle is to wire it to the
press S1 and S2 until it reaches your
Alternatively, if you just want to set chassis using a crimped eyelet secured
target. S2 increases frequency, while
the upper threshold frequency with S2 to a convenient screw terminal.
S1 decreases frequency.
and have the hysteresis setting made
You may need to drill a separate hole
Short presses of the switches will
for the lower threshold as set by trim- in the chassis for this connection, or
alter the frequency at a slow rate. For
pot (VR2), then you must have a link utilise an existing earth connection.
faster changes, hold the switch down
fitted to JP2 before you start the proceWire CON2 to a suitable sensor. This
and the rate will change to a faster rate
dure. Similarly, you can set the lower can be the speedometer sensor, an ECU
after two seconds. Continue to depress
threshold with S1 and have the upper tachometer output, an injector or camthe switch for another two seconds and
threshold set by the hysteresis percent- shaft position sensor and so on. If you
the frequency will change at an even
age value as set by VR2.
haven’t already set the unit up, do so
faster rate.
Now turning off the power takes the as described above above.
This allows you to run through the
micro out of the mode whereby it proThe relay contacts are labelled Norentire frequency range in less than one
duces an output frequency at TP3. It mally Open (NO), Normally Closed
minute but still be able to do finer adthen reverts to normal operation, mon- (NC) and Common (COM).
justments with brief switch presses.
itoring the input frequency instead.
To switch power to a load, wire one
Having reached your target frequenThen fit a link to JP1 if you want the of its supply lines in series between
cy, insert JP1. Then press S2 to set the
relay to switch on as the frequency falls
either the COM and NO terminals (so
upper threshold frequency. Then rebelow the threshold set by S1 (and turns that it’s only powered when the relay
move JP1. Then press S1 to reduce
off when the frequency rises above that
is energised) or COM and NC terminals
the frequency to the lower threshold.
set by S2).
(so it’s switched off when the relay is
Then re-insert JP1 and press S1 to set
No link is required at JP1 if you want energised).
the lower frequency threshold.
the relay to switch on as the frequency
Note that the relay contact current
Note the two-step process to set each
rises above the threshold set by S2 (and rating is 5A for the Jaycar relay and 8A
frequency. In other words,with JP1 out,
turns off when the frequency drops be- for the Altronics relay (see parts list).
use S2 and S1 to adjust the frequency to
low that set by S1).
If a higher current is required, you
the wanted value, insert JP1 and press
If you want to configure the unit with can switch 12V DC to the coil of a largS2 to set the upper threshold.
a switching delay (as described ear- er relay using RLY1.
SC
Resistor Colour Codes
o
o
o
o
o
o
Qty. Value
1
1MΩ
1 100kΩ
4
10kΩ
6 3.3kΩ
1
1kΩ
1
47Ω
siliconchip.com.au
4-Band Code (1%)
brown black green brown
brown black yellow brown
brown black orange brown
orange orange red brown
brown black red brown
yellow violet black brown
5-Band Code (1%)
brown black black yellow brown
brown black black orange brown
brown black black red brown
orange orange black brown brown
brown black black brown brown
yellow violet black gold brown
Celebrating 30 Years
Small Capacitor Codes
Qty. Value
o
o
o
o
4
1
1
1
F
Code
100nF 0.1F
1nF 0.001F
470pF
27pF
-
EIA
Code
IEC
Code
104
102
470
27
100n
1n
470p
27p
May 2018 41
SAD
HAPPY
To discover that the elusive bit
that you want is stocked in the
Silicon Chip ONLINE SHOP!
There's a great range of semis,
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WeMos R1 D2 WiFi Board
A WeMos R1 D2 Arduino-compatible
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Micromite LCD BackPack V2 complete kit
Includes PCB (green), 2.8-inch TFT touchscreen, programmed micro, SMD Mosfets for
PWM backlight control, lid and all other onboard parts (May 2017).............$70.00
5m Water Level Sensor (4-20mA)
Pressure-based water level sensor with a
5-6m lead as used in the WiFi Water Tank
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Includes PCB, 2.8-inch TFT touchscreen,
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Includes PCB, programmed 100-pin SMD
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Includes PCB, programmed 64-pin SMD
micro, crystal, connectors and all other
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GPS MODULE
Onboard antenna, 1pps output, operation to
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5V 0.8W 160mA Solar Panel
Monocrystalline silicon, 99 x 69mm, ~6V
open circuit, ~5V full load, two solder
pads on the underside of the panel…$4.00
Logic-level Mosfets
Pair of CSD18534KCS N-channel …… $5.00
Or complementary pair of N & P-channel
Mosfets (as used in Burp Charger) … $7.50
IPP80P03P4L04 P-channel Mosfet
SC200 Amplifier hard-to-get parts
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2.4GHz WiFi Antennas
Supplied with a matching chassis-mount
SMA socket and attached U.FL/IPX connector cable.
2dBi omnidirectional (28mm)….$10.00
5dBi (175mm)………….….......$12.50
AD9833 DDS module
A Direct Digital Synthesis module using the AD9833
IC and a 25MHz crystal oscillator. (April 2017)
with programmable attenuator (green) ….… $25.00
without attenuator (blue) …………………... $15.00
Elecrow 1A/500mA Li-Ion/LiPo charger
board with USB power-pass through
Provides a regulated 5V output at
500mA from the cell, plus a 1A charger
and automatic input-to-output passthrough. Supplied with three 2-wire
JST 2.0 cables.…............. $15.00 ea
Isolated High-Voltage Probe
Pack of hard-to-get parts including
HCNR201-050E linear optocoupler, op
amps and HV capacitors & resistors
(Jan 2015) ……………………… $35.00
SiDRADIO parts
125MHz crystal oscillator, mixer, dual gate
Mosfet, 5V relay and more ……… $20.00
RF Coil Former pack (Oct 2013) …… $5.00
Currawong stereo valve amplifier
Hard-to-get parts including 5 x 39µF 400V
capacitors, HV transistors, regulator and
blue LEDs (Nov 2014) ………… $50.00
A high-current P-channel Mosfet with low onresistance in a TO-220 package. Used in the
Water Tank Level Meter (Feb 2018) and AM
Radio Transmitter (Mar 2018).….....… $4.00
Ultra Low Voltage Bright LED Flasher kit
Includes PCB, LDR, high-brightness blue
LED, all SMD parts, an extra capacitor plus
extra resistors to change flash frequency
and duty cycle (Feb 2017) …….… $12.50
CP2102-based USB/TTL serial converter
Includes a micro-USB socket and 6-pin
right-angle header (top) …………. $5.00
Includes a USB Type-A socket and
5-pin header with a 5-way female Dupont
cable (bottom) …………………. $5.00
MCP1700 3.3V Low-dropout Regulator
3.3V LDO regulator in a convenient TO-92 package,
as used in many projects; up to 6V input and 250mA
output ……………………………………… $1.50
DS3231-based RTCC module
Real-time clock & calendar module w/
4KB EEPROM, I2C interface & mounting hardware
with LIR2032 cell ………...… $7.50
no cell ……………………….. $5.00
Don't forget: Silicon Chip Subscribers qualify for a 10% discount on all these items!
YES! We also stock most Silicon Chip project PCBs from 2010 and even earlier!
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42
Silicon Chip
Celebrating 30 Years
siliconchip.com.au
Y
Using Analysing and
optimising
audio circuits
by Simulation
Part IV
by Nicholas Vinen
We concluded our last tutorial (September 2017) saying that
our next LTSpice tutorial would cover simulating op amps and
audio circuits. It has been a while coming . . . but here it is!
S
imulating audio circuits can be
useful for a number of reasons, including:
• optimising filter component values
for the desired roll-off point and
minimal passband ripple
• characterising complex and/or cascaded filter responses – corner frequency, roll-off rates, out-of-band
attenuation, bandwidth limitations, etc
• optimising amplifier circuits for stability, bandwidth, etc
• measuring frequency response and
headroom
• checking expected circuit operation
• verify DC operating conditions
• checking that component voltages,
currents, dissipation and heating
are within safe operating limits
This article will cover most of the
above tasks and the circuits and techniques presented here can be applied
to the remainder (and others we haven’t
mentioned).
Filter optimisation
There are dozens of different kinds
of filters that you might use in an audio
circuit, including low-pass, high-pass,
band-pass and notch types from simple passive (RC, LC) filters to complex
multi-pole active filters or resonant
passive filters.
The characteristics of the most simple
RC filters can be calculated quite easily, using well-known formulas such as
f (-3dB) = √(2π x R x C) to determine the
corner frequency for an RC high-pass
or low-pass filter. But as soon as you
start working with multi-pole filters or
multiple cascaded RC filters, the calculations become much more difficult.
Luckily, simulating such circuits is
simple and will quickly give you gain
and phase plots.
For example, let’s say that we have
two cascaded RC low-pass filters with
a buffer stage between them. And say
they use identical components, so they
have the same -3dB corner frequencies and 6dB/octave roll-off. We can
use 1kΩ resistors and 1nF capacitors
to keep it simple.
So we expect the resulting combination to have a 12dB/octave roll-off
but the -3dB frequency of a single filter (159kHz) is now the -6dB point of
Fig.1: a simple secondorder RC low-pass filter
drawn up in LTspice,
using ideal buffer E1 to
isolate the stages. We
can then compare its
performance to more
typical second-order
filter circuits to see
their pros and cons.
siliconchip.com.au
Celebrating 30 Years
the combined filter. So what is the new
-3dB point?
Simulating it
Rather than using an op amp model as the buffer stage between the two
filters, we’ll use a unity-gain voltagecontrolled voltage source. This has
the benefit of being simpler to use
(no need to wire up supply rails etc),
infinite bandwidth, no distortion and
no noise.
To set up this simulation, we create
a new schematic sheet in LTspice and
add and wire up the components as
shown in Fig.1. Refer to the earlier articles in this series for details on how
to do this. See www.siliconchip.com.
au/Article/10677
We already introduced the voltagecontrolled voltage source, in this case,
component E1. You need to right-click
on it and set the “Value” field to 1 so
that it operates at unity gain. For the
voltage source, right-click on it and
click on the “Advanced” button to
show all the fields, then set the “AC
Amplitude” field to 1V (under “Small
signal AC analysis”).
We label the input and output nets
using the “Label Net” button in the toolbar, for easier analysis later. Finally, select the Simulate -> Run menu option
and then switch to the AC Analysis tab
and set the type of sweep to Octave, the
number of points per octave to 10, start
frequency to 10Hz and stop frequency
to 10MegHz (other options would be
valid but let’s stick with these for now).
Do not set the stop frequency to
May 2018 43
Fig.2: Bode plots showing the
frequency and phase response for the
intermediate and output notes of the
Fig.1 circuit. We can then use cursors
to determine their -3dB points and
calculate the roll-off rates.
10MHz, since this will be interpreted
as 10mHz!
Having run the simulation, click
on the output node and a plot similar
to that shown in Fig.2 should appear
(we’ve also clicked on the junction of
C1 and R1 to compare the response of
a single stage). The output response is
shown in green and the green dotted
line is the output phase. The intermediate response is shown in blue. As you
would expect, the combined response
has a steeper roll-off.
Now, to determine the -3dB point,
click on the “V(output)” label at top
and cursors appear, along with the
box shown at lower right, which contains additional information. Drag the
horizontal cursor to the right until the
Mag: reading in the box is very close to
-3dB and then you will see the corner
frequency at left, which is just above
100kHz. Phase and group delay readings are also shown.
Comparing other multi-pole
filter arrangements
The problem with cascading two RC
filters with a buffer in between to produce a two-pole filter, is that the resulting output impedance pf the cascaded
filter is relatively high. But it is possible to build a two-pole filter around
a single buffer/gain stage and obtain a
very low output impedance. Two common approaches to this are Sallen-Key
and Multiple-Feedback filters.
An excellent website for designing
such a filter is at: siliconchip.com.au/
link/aajq
One of the biggest problems with
designing this type of filter to achieve
a specific response is that you inevitably need components with unrealistic values, such as 4.39kΩ or 1.42nF.
With some tweaking, you may arrive
44
Silicon Chip
at component values which are close
to what’s actually available.
But that leaves us with two questions: how much does the deviation
from ideal values affect the filter response, and which of the two filters
topologies is best? LTspice can help us
answer both these questions.
For this exercise, let’s aim to build a
realistic filter with the same -3dB point
and roll-off as we determined above
with our naive attempt, ie, 102.375kHz
and 12dB/octave respectively.
At the website above, we set the
filter order to 2, cutoff frequency to
102.38kHz and experimented with the
“Desired Rx” value until we got realistic looking values below. This was
with a “Desired Rx” value of 2.4kΩ.
We then drew up both resulting filter
circuits in LTspice, as shown in Fig.3.
There are several important points
to note about this circuit we’ve drawn
up. Firstly, we have chosen to use
LT1464 op amps as these have 1MHz
bandwidth and this will provide a
good demonstration of how op amp
bandwidth effects filter behaviour.
Also, we have used the Net Label
tool to label the supply rails of each
op amp V+ and V- and we then added two extra stacked voltage sources,
V2 and V3, both set to 5V DC with the
junction connected to ground. By labelling the top and bottom V+ and Vas well, we’re providing ±5V supply
rails for each op amp without cluttering up the schematic.
The output of the “naive” filter has
been re-labelled out1 so that we can
label the two new filter outputs out2
and out3, for easy comparison. (In case
you can’t immediately see out2 and
out3, they are just above U2 and U3).
U2 is used for the Sallen-Key second-order filter which uses two resistors and two capacitors, all with
different values, while the MultipleFeedback second-order filter is based
around U3 and it uses three equal-value resistors plus two capacitors.
The Multiple-Feedback filter is an
inverting type while the Sallen-Key
is non-inverting; this may be imortant in some applications. While we
were able to use equal-value resistors
in the Multiple-Feedback filter, that
isn’t guaranteed to always be the case.
Note that the output of the two new
filters is taken from the output pin of
an op amp, so the impedance is low
and can be fed into another filter network. You would need an extra op amp
buffer for the naive filter to achieve the
same result.
Now since these are all second-order
low-pass filters with the same corner
Fig.3: here we’re simulating three low-pass filter circuits drawn using op amp
models, all with a -3dB point of 100kHz.
Celebrating 30 Years
siliconchip.com.au
if we needed to). So it ends up attenuating the signal even further.
Another couple of things to note:
both of the new filters give less attenuation of the signal below the -3dB point,
ie, they roll-off more quickly which is
good if you’re going for a “brick wall”
type response. And the use of a real
op amp has actually pushed the naive filter -3dB point slightly higher,
to around 110kHz, which is why the
curves don’t all meet at one point.
Higher bandwidth op amps
Fig.4: the resulting frequency response plots of the three filter circuits shown in
Fig.3 (green=out1, blue=out2, red=out3). While the graphed lines may seem light
here, they are quite visible on-screen.
frequency, you would expect the results to be very similar but you might
be surprised.
Comparing filter responses
We now run the same AC analysis as
before but this time, after clicking on
the out1, out2 and out3 nets to plot the
response, we right-click on the phase
axis at right and click the “Don’t plot
phase” button to de-clutter the resulting Bode plot.
We’ve expanded the plot to fill the
window for increased clarity and the
result is shown in Fig.4. The naive
filter response is shown in green, Sallen-Key in blue and Multiple-Feedback in red.
The most surprising aspect to this
plot is that while both the additional
filters have a much faster roll-off above
the ~100kHz -3dB point, above 1MHz
(the -3dB bandwidth of the op amps),
the naive filter actually provides superior attenuation.
And as shown the Sallen-Key filter
does a particularly poor job at higher
frequencies, with a peak at around
-15dB attenuation at 1.8MHz and it’s
not much better at higher frequencies either.
This is because capacitor C4 couples some of the signal from the input straight to the op amp’s output
and its limited bandwidth means that
it isn’t able to prevent that coupled
signal from feeding through. (To explain, there is no extra open-loop gain
at higher frequencies and that means
that negative feedback cannot act to
provide a low output impedance).
The Multiple-Feedback filter does
a better job because capacitor C5 is
siliconchip.com.au
a smaller value and there are two resistors, R5 and R7, in series before it,
plus C6 will shunt much of the feedthrough signal to ground. Even so, you
can see that the slope of the red trace
changes slightly around 1MHz to be
more flat, allowing the blue trace of the
naive filter to “catch up” to it at 1MHz.
That’s because the naive filter starts
with a completely passive RC filter
which rejects at least some portion
of the signal regardless of the op amp
bandwidth. And the op amp’s limited bandwidth actually helps us here,
since there’s no path for the signal to
“feed through” it (ignoring parasitic
PCB capacitance, which we aren’t simulating here although we could add it
So how does this change if we use a
higher bandwidth op amp? That’s easy
to test; simply delete U1-U3 and replace them with LT1357s which have
a gain-bandwidth product of 25MHz.
Then re-run the simulation. The result
is shown in Fig.5.
All three curves now meet at the design -3dB point of 102.375kHz and it’s
clear that the Multiple-Feedback filter
now gives the best performance, with
much less effect on frequencies below
100kHz than the naive filter, a much
quicker roll-off above this point and
very little change in its rate of attenuation up to 10MHz; just a slight change
in the rate of attenuation, which reaches -75dB at 10MHz.
By comparison, the Sallen-Key filter
gives virtually identical performance
up to 1.4MHz but it reaches a maximum attenuation of -50dB at 2.2MHz,
above which is attenuation factor actually falls, giving -40dB at 10MHz. Its
Fig.5: the same
frequency response
plots as shown in
Fig.4 but this time,
with 25MHz op
amps, giving better
results. You can see
that the Sallen-Key
filter is still less
than ideal but its
rebound has been
pushed to a higher
frequency.
Fig.6: a similar plot
to Fig.5 but this
time up to 100MHz,
so we can see how
the filters behave
between 10MHz
and 100MHz.
Celebrating 30 Years
May 2018 45
Fig.7: a simplified hifi audio amplifier circuit simulated using components available in the libraries supplied with LTspice.
curve crosses the naive filter for a second time at 2.73MHz, with the naive
filter continuing to provide attenuation,
reaching -72dB at 10MHz.
If we go back to the schematic,
right-click on the simulation command (which starts with “.ac”) and
change the finish frequency to 100MHz
(“100MegHz”), we get the plot shown
in Fig.6.
This shows that the Sallen-Key bode
plot has a peak of -31dB at 35MHz,
above which it again begins to slowly
roll off. By comparison, the MultipleFeedback filter does continue to increase its attenuation at higher frequencies although at a reduced rate.
The naive filter overtakes it at
15MHz, where both reach -78.5dB.
The Multiple-Feedback filter reaches
-100dB at 100MHz while the Naive filter is at -132dB by 100MHz.
Simulating an amplifier with
discrete components
Our article on Amplifier Stability
and Compensation in the July 2011
issue gave fairly detailed information
on using SPICE to simulate an amplifier and test it for stability under difficult conditions, for example, when it
is driven into clipping.
Rather than go back over that, we will
instead build a simple amplifier circuit
in the simulator to analyse the amplifier efficiency, determine the dissipation
in the major components and examine
how power flows from the transformer
through to the loudspeaker load.
We’ve drawn up a minimalistic hifi
Fig.8: the voltage across load resistor RL is shown in
mauve while the dissipation in that resistor (ie, load
power) is in green.
46
Silicon Chip
power amplifier circuit in LTspice and
this is shown in Fig.7. We’ve used only
components from the built-in libraries. The test input signal, a 2.1V peak
sinewave is from V1. This is fed into
the base of PNP transistor Q1, which
forms a differential input pair with
Q2. Q2 is connected to the output via
a 12kΩ/510Ω divider, setting the amplifier gain to 24.5 times.
NPN transistors Q3 and Q4 are the
current mirror load for the input pair
while PNP transistor Q5 is the constant
current source for their emitters. The
differential stage output current flows
from the collector of Q1 to the base
of Q8, the VAS (voltage amplification
stage) transistor which has a 100pF
compensation capacitor, to stabilise
the amplifier.
Fig.9: this shows how the amplifier output voltage plus
the AC and DC supply voltages behave when power is first
applied.
Celebrating 30 Years
siliconchip.com.au
Fig.10: this
demonstrates how
current is drawn
in brief bursts
from the simulated
transformer
secondaries at their
voltage peaks.
Q10 and its two base resistors form
the Vbe multiplier that sets the bias
voltage for the output stage and thus
the quiescent current. The bias resistor
values were determined experimentally and set the output stage quiescent
current to 120mA per transistor pair.
PNP transistor Q9 is the constant current source for the VAS while Q6 controls the base bias for both Q5 and Q9.
The output stage consists of driver
transistors Q11 and Q14 and power
transistors Q12, Q13, Q15 and Q16 (in
Darlington emitter follower configuration). These have 0.1Ω emitter resistors
and there is an RLC filter at the output
to isolate the load (at high frequencies)
and ensure stability. The test load is an
8-ohm resistance, RL.
The power supply consists of sinewave voltage sources V2 and V3 which
represent the two halves of a centretapped transformer secondary (45-045VAC). This is rectified by bridge
rectifier DP1-DP4 and the supply is filtered by a pair of 10,000F capacitors.
Examining power supply
behaviour
Fig.8 shows the output voltage in
mauve. This is a zoomed-in portion of
the simulation output since the waveform is clipped initially as the power
supply filter capacitors charge up. But
if we’re interested in looking at the output power, that muddies the water. As
expected, the output is a sinewave. The
2.1V peak input has been amplified by
the 24.5 times gain to yield peak voltages of just over ±50V.
The green plot is the instantaneous dissipation in the load resistor.
This is plotted by holding down the
ALT key in Windows and then clicking on the load resistor, RL. Control-clicking the green text at the top
(“V(output)*I(RL)”) then yields the integral box shown at lower right. This
reveals that the amplifier is delivering
siliconchip.com.au
around 165W average to the load in
this condition.
The instantaneous dissipation in
RL is 0W when the applied voltage
passes through 0V and rises to a peak
of around 330W at both the positive
and negative sinewave maxima. Note
that this is a sine-squared waveform
which is why there is a 2:1 ratio between peak and RMS power, not the
sqrt(2) ratio you would expect for a
normal sinewave.
Fig.9 shows a “zoomed out” version
of the simulation plot where you can
see the V+ (green) and V- (blue) power
rails initially charging up.
This is unrealistically fast as we
have simulated a transformer with a
zero ohm output impedance; you could
add a small series resistance and/or inductance if you wanted a more realistic simulation of amplifier switch-on.
The mauve waveform once again
shows the amplifier output and you
can see that it is initially clipped by
the low supply rail voltages, especially on negative excursions due to R25
and C11, which form an RC low-pass
filter for the negative rail at the front
end of the amplifier.
These components are important to
prevent supply rail ripple due to the
load current from affecting the input
pair and VAS but they do slow down
the amplifier’s start-up somewhat. And
as shown, they also make the waveform
initially clip asymmetrically.
Normally, this would not be a problem as there would typically be a relay
between the amplifier and the output
terminals with a delayed switch-on to
prevent a thump from the speakers at
power-up.
The red and cyan traces in Fig.9 are
the simulated transformer secondary
waveforms and they show how the
supply rails are pumped up when the
transformer secondary voltages peak
and the rails slowly decay, as the load
current is drawn during the subsequent mains half-cycles. You can also
see how the two halves of the centretapped secondary alternately charge
up the supply rails.
This is shown in more detail in
Fig.10. This time the supply rails are
plotted in blue (V+) and cyan (V-) while
the simulated secondary voltages are
in red and green. Current from voltage
sources V2 and V3, representing the
transformer secondaries, is shown in
grey and mauve.
Ignoring the initial very high current on the first mains half-cycle, the
remaining current pulses are semirealistic and you may be surprised to
see that zero current is drawn from the
transformer most of the time, with brief
peaks to nearly 40A being drawn over
a ~1ms period every 10ms.
Calculating amplifier
efficiency
If we zoom into the plot so that we
remove the initial surge current and
then CTRL-click the I(V2) text at the
top of the window, this gives us an
RMS current of 8.3A.
If we assume a Class-AB amplifier
efficiency of 70%, for 165W output we
need an input power of 235W and with
two 60VAC secondaries, you would
expect 2A [235W ÷ 60V ÷ 2] = drawn
from each supply rail.
Fig.11: averaging
the power
drawn from the
transformer to
calculate the
amplifier input
power, so we
can calculate its
efficiency. The
circuit is shown
larger in Fig.7.
Celebrating 30 Years
May 2018 47
Fig.12: the
instantaneous
dissipation in the
output and driver
transistors. These
can be averaged to
estimate how hot
they will get.
The reason for the discrepancy is the
fact that current is only drawn for such
a short period during the secondary
voltage peaks. This means that I^2R
losses in the transformer, wiring, rectifier etc will all be a lot higher than
you would get with a resistive load on
the transformer.
If you think about it, though, it’s
very rare for a transformer to have a
resistive load. Transformers are mostly
used to drive rectifiers in similar configurations to this. Hence, transformer
ratings tend to be quite conservative
as they have to deal with supplying
such high peak currents with a low
duty cycle.
So does this mean that a huge
amount of power is being wasted in the
transformer? Not really. It just means
the power factor is poor. We can determine the real power drawn from the
“transformer” by labelling the output
(top) of V2 as V2V and the bottom of
V3 as V3V, then re-running the simulation, and plotting the product of current and voltage.
To do this, we right-click on the
resulting plot and selecting “Delete Traces”, then right-click again
and select “Add Trace” and type
in the formula: “I(V2)*V(V2V)”.
Add another trace with the formula
“I(V3)*V(V3V)”. We can then zoom
into a single mains cycle and controlclick the formula at the top of the window to get an average reading. The
result is shown in Fig.11.
You need to be careful when zooming that you get exactly 20ms (or a multiple thereof) on the horizontal axis or
the averaged values will not be correct.
We get a figure of very close to 123W
for both V2 and V3. Thus the total power draw of the circuit is 246W. That
means the actual amplifier efficiency
is 67% [165W ÷ 246W], pretty close
to the 70% that we estimated earlier.
48
Silicon Chip
Determining device
dissipation
We can measure the dissipation in
the output transistors, driver transistors and rectifier diodes by alt-clicking them and then control-clicking
the formula that appears at the top of
the window.
Fig.12 shows the dissipation of one
pair of output transistors in green and
blue and one of the drivers in red. As
you can see, we get a reading of around
17.5W for each of the four main output devices.
Repeating the same exercise gives a
dissipation figure of 2W total for the
two drivers plus 2W in each of the rectifier diodes, for a total (including the
load) of 245W [165W + 17.5W x 4 +
2W x 5], leaving just one watt unaccounted for, most of which turns out
to be due to the 0.1Ω emitter resistors.
So this shows how the simulation
can help you determine efficiency, calculate device dissipation and so on.
It’s a good idea to check dissipation
for the smaller transistors too.
Depending on the current through
each stage, they could potentially be
buys
close to their specified limit as they
would normally be in much smaller
packages than the output transistors.
You could also easily measure the
peak and average current in the output
devices to check that they are within
with each device’s capabilities.
Conclusion
While this article has covered a lot
of ground, there are still many other
audio circuits that we have not discussed and which can benefit from a
SPICE simulation but we don’t have
the space to cover them all.
However, the above should give you
an idea of how to “probe” and measure the simulated circuits. It’s especially helpful for tweaking component types and values to achieve an
optimal result.
For example, you could increase
the amplitude of the input sinewave
to the amplifier and investigate what
happens when the amplifier is driven
into clipping.
You could build a simulated loudspeaker load based on resistors and
inductors and possibly even include
a crossover network, to better explore
how the load’s reactance affects amplifier operation, stability and efficiency.
All the circuits shown in this article
are available for download from the
SILICON CHIP website (in a ZIP package) so feel free to experiment, probe,
tweak and find out for yourself just
how they work and what effect your
changes will have.
After all, you can’t blow anything
up! In fact, why not over-drive things
to destruction just to see what happens? It’s a simulation: you won’t have
to buy any new components!
SC
Linear Technology
More than a year ago, Analog Devices completed the acquisition of Linear Technology (the owners of LTspice).
LTspice is still available as a free download but you can now access it via siliconchip.
com.au/link/aajo
You may find that if you have an older installation of LTspice, the automatic update
feature no longer works because the URL it fetches is no longer valid. We suggest you
download and install the latest version from the above link, which should then be able
to keep itself up-to-date.
One major advantage of the new version is that there are now many Analog Devices
(ADxxxx) parts available to simulate, along with the existing set of Linear Technology
(LTxxxx) parts.
However! We have found the latest version of LTspice (version XVII) to be considerably less stable than the older version that we used (version IV). Hence, you may wish
to keep your old version of the software in case these bugs have not yet been fixed. You
may notice that some of our screen captures are from the earlier version, for this reason.
Celebrating 30 Years
siliconchip.com.au
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battery drain when not in use. Sold in pairs.
SADDLE
HC-4030
LUG BOLT STYLE
HC-4034
ISOLATING (NEGATIVE POST) HC-4038
$
INOX BATTERY
CONDITIONER
19 95
FROM
3.7V 18650 2600MAH LI-ION
PROTECTED BATTERY SB-2299
3.2V LIFEPO4
RECHARGEABLE BATTERIES
Fully protected against overcharge,
over-discharge, short-circuit, and overcurrent to keep the battery in good shape
and devices safe.
• Rechargeable
Lithium iron phosphate (LiFePO4) is
more chemically stable type of lithium
rechargeable cell. Very popular due to
increased safety and longer cycle life.
• 600mAh, 1600mAh & 3000mAh available
52
Capable of taking an 8-16VDC
input voltage, and giving a stable,
regulated 13.8V/14.4V 4-stage
charger output to give your
auxiliary battery a full 100% charge.
• Input voltage: 8 - 16VDC
• Output current: 40A max
$
FROM
39 95
SF-2249
BATTERY ISOLATOR
SWITCHES WITH AFD*
QP-2263
Versatile battery tester for vehicle
or vessel batteries.
• LCD panel of voltage as well
as LED indication for
under/overcharge
• Suitable for 12V and 24V batteries
1195
$
4 STAGE 40A DC TO DC BOOST
CHARGER MB-3690 WAS $349
24 95
SB-2305
$
NOW
299
12/24V BATTERY TESTER
NA-1420
Removes or
reduces sulphation.
92ml pack sufficient
for most automotive
batteries.
Due mid May
Warns you when battery power is running
low & disconnects power through the unit
when power gets too low. Plug and play
operation, no tools required!
• Max Power Output: 8A
• Connection: Cigarette Lighter
• 95(L) x 35(W) x 155(H)mm
SAVE $50
SAVE $10
$ 95
FROM
49 95
Durable and rated for massive output.
Protects alternator when switching batteries
in and out of the circuit.
2 POSITION SF-2249 $39.95
4 POSITION SF-2250 $49.95
*AFD - Alternator Field Disconnect
SB-1723
FROM
$
2
$ 95
NI-MH RECHARGEABLE BATTERIES
Nickel Metal Hydride (Ni-MH) batteries offer
superior features to Nickel Cadmium (Ni-Cd)
rechargeable batteries. AA,AAA, C, D & 9V.
Nipple or solder tabs.
• Higher current capacities
• High drain performances
Follow us at facebook.com/jaycarelectronics
39 95
DUAL CHANNEL LI-ION
AND NI-MH BATTERY
CHARGER MB-3635
Supports charging of
LiFePo4, Li-ion, Ni-MH, and
Ni-Cd batteries. Individual
charging lanes. LCD feedback.
• Charging Current: 500mA / 1000mA
• 67(W) x 129(H) x 38(D)mm
Catalogue Sale 24 April - 23 May, 2018
TECH TALK:
Multi State Charging States
Smart Chargers have a pre-set charging cycle such as 3, 4 or 9 stages. The charging voltage
and current is optimised in each stage to suit the type of battery being charged, this ensure
maximum operating efficiency and battery life. Below are some common charging states:
READ THE FULL ARTICLE:
jaycar.com.au/charging-states
DESULPHATION:
Pulsing current and voltage, removes sulphate
from the lead plates in sulphate batteries.
RECONDITION MODE: This mode charges at higher voltage to recondition
the sulphate and increase battery life.
SOFT START:
Charging starts with reduced current until battery
voltage reaches a normal condition for charge.
ANALYSIS:
Tests the condition of the battery. If is unable to
hold charge it needs to be replaced.
BULK MODE:
During this stage the battery is charged to up to 80% capacity,
which is the majority of its charge.
FLOAT:
When battery is fully charged, this state maintains a trickle, minimal
charge current, to ensure the battery remains fully charged.
PULSE MODE:
Maintaining the battery at 95-100% capacity. The charger monitors
the battery voltage and injects a pulse to maintain the battery charge.
ABSORPTION MODE: Completes the charge up to (or close to) 100% at a
slower charge rate in order to protect the batteries working life.
Multi-State Battery Chargers:
High tech SLA battery chargers for automotive, marine, motorcycle, workshop or industrial use. Capable of
recharging the battery and maintaining the charge state indefinitely. Safe to leave connected for months.
$
49 95
$
89 95
169
$
6/12VDC 1.5A
3 STATE CHARGER MB-3609
6/12VDC 4A
4 STATE CHARGER MB-3611
Suits all SLA batteries: Wet cell, gell cell and AGM
• Output voltage: 6/12VDC
• Max output current: 1.5A
• Capacity: 6-20Ah
• 110(L) x 58(W) x 46(D)mm
Uses a microprocessor to diagnose the battery's state of
charge. Suits all SLA batteries: wet cell, gell cell and AGM.
• Output voltage: 6/12VDC
• Max output current: 1A/4A
• Capacity: 7-80Ah
• IP65 rated
• 200(L) x 70(W) x 50(D)mm
12V-7.2A/24V-3.6A 9 STATE CHARGER MB-3613
Fully automatic 9 state charger for 12 or 24V sealed lead
acid (SLA) batteries- wet cell, gel cell and AGM.
• Output voltage: 12/24VDC
• Max output current: 7.2A/3.6A
• Capacity: 14-160Ah
• IP65 rated
• 210(L) x 90(W) x 60(D)mm
$
$
NOW
299
SAVE $50
12V-15A/24V-7.5A 9-STATE CHARGER
MB-3607 WAS $349
Fully automatic 15A high current charger with maintenance
charging of all types of SLA batteries as well as leadcalcium batteries from 50 - 250Ah, and either 12V or 24V.
• Output voltage: 12/24VDC
• Max output current: 15A/7.5A
• Capacity: 50-250Ah
• IP65 rated
• 260(L) x 135(W) x 70(H)mm
$
Advanced electronic and fully automatic. Charge
multiple batteries such as cranking and house
batteries simultaneously once connected to
shore power.
• 5 multi-stage charging
• Initialize, fast charging, optimizing, maintaining,
smart storage modes
• Suits flooded, standard AGM & GEL batteries
• IP68 waterproof rated
• LED system & status indicators
12A 12/24V DUAL MB-3616 WAS $299
20A 12/24/36V TRIPLE MB-3617 WAS $399
79 95
12VDC LEAD ACID
BATTERY TESTER
QP-2261
Tests most automotive cranking lead
acid batteries, including an ordinary
lead acid battery, AGM flat plate,
AGM spiral, and GEL batteries.
• 6-30VDC voltage range
• 125(L) x 70(W) x 25(H)mm
MB-3616
ON-BOARD MARINE BATTERY CHARGERS
FROM
34 95
BATTERY BOXES
Protect your batteries with these sturdy
boxes. Perfect for mounting in your boat,
trailer or caravan.
FITS 40AH SLA BATTERY HB-8100 $34.95
FITS 100AH SLA BATTERY HB-8102 $39.95
Battery not included
To order: phone 1800 022 888 or visit www.jaycar.com.au
SAVE $50
$
NOW
349
SAVE $50
MB-3617
SB-1698
$
NOW
249
FROM
129
$
12VDC SLA DEEP CYCLE
GEL BATTERIES
Leakproof and completely sealed, ideal for
solar power, 4WD, camping etc.
26AH SB-1698 $129
40AH SB-1699 $199
100AH SB-1695 $379
See terms & conditions on page 8.
SB-1680
$
FROM
279
12VD DEEP CYCLE AGM BATTERIES
Designed to store large amounts of energy,
they give superior deep cycling performance
for many different recreational and industrial
applications such as camping, boats,
motorhomes etc.
75AH SB-1680 $279
100AH SB-1682 $329
53
Workbench Essentials:
There has been an obvious resurgence in people getting back to the workbench and
reviving skills involving manual dexterity. As you will see across the following pages,
Jaycar has all the DIY tools you'll need to equip your workbench so you can create
projects from the power of your brain and your hands.
$
NOW
249
SAVE $50
3
5
4
179
$
$
NOW
59 95
SAVE $10
1
$
39 95
6
$
59
95
$
2
NOW
69 95
1. ANTI STATIC MAT TH-1776
• Ideal for field service people
• Mat folds out to work area of 600 x 600mm
(approx)
• 2 pouches at one end
• Ground lead and and wrist strap included
2. 8 PIECE SCREWDRIVER AND TOOL SET
TD-2031
• Quality rubber-moulded insulation for
in-hand comfort
• VDE approved to 1000V
• Insulated right to the tip
3. 65W ESD CONTROLLED SOLDERING
STATION WITH DIGITAL DISPLAY
TS-1440 WAS $299
• Excellent temperature stability and
anti-static characteristics
• 230-240VAC supply voltage
• 200 - 480°C temperature range
• 65W capacity heater
• 0.5mmt tip supplied
• 146(L) x 115(W) x 98(H)mm
4. SOLDER FUME EXTRACTOR
TS-1580 WAS $69.95
• Removes dangerous solder fumes
• Ball bearing high volume fan
• ESD safe
• Spare filters, pack of 5 - sold separately
(TS-1581 $9.95)
• 260(H) x 200(W) x170(D)mm
5. 0 TO 30VDC 5A REGULATED LAB
POWER SUPPLY MP-3840
• Digital control, large LED display
• Built-in over-current & short circuit
protection
• Output current: 0-5A
• 270(L) x 120(W) x 185(H)mm
6. MINI TRUE RMS AUTORANGING DMM
QM-1570 WAS $89.95
• Compact, IP65 rated
• Drop tested from 2m height
• Cat III 600V Safety Rating
• AC/DC voltages up to 600V
• AC/DC current up to 10A
• Temperature -20°C to 750°C
• Includes test leads and carry case
SAVE $20
CAT III Clamp Meters
Our range of CAT III Clamp Meters makes the best general troubleshooting tool for
commercial and residential electricians and includes features found on more expensive
units such as autoranging, data hold, non-contact voltage, relative measurement
and auto power-off. Multi function with Resistance, Capacitance, Frequency and
Temperature, all Clamp Meters are supplied with quality temperature probe and
carry case.
MP-3242
NEW LOW PRICE!
ORRP $239
199
$
$
SAVE $40
VARIABLE LABORATORY
AUTOTRANSFOMER (VARIAC) MP-3080
Encased in heavy-duty steel housing, this
unit enables the AC input to a mains powered
appliance to be easily varied between 0 to
full line voltage (or greater).
• 500 VA (fused) rated power handling
• 0-260 VAC <at> 50Hz output voltage
$
22 95
WAS $129
WAS $159
SAVE $10
SAVE $30
SAVE $10
$
59 95
$
99
149
$
400A AC QM-1561
400A AC/DC QM-1563
• Cat III 600V, 4000 count
• AC/DC voltage < 600V
• AC current < 400A
• Jaw opening 30mm
• Cat III 600V, 4000 count
• AC/DC voltage < 600V
• AC/DC current < 400A
• Jaw opening 30mm
54
• Cat III 600V, 4000 count
• AC/DC voltage < 600V
• AC/DC current < 1000A
• True RMS, min-max,
bargraph and more
• Jaw opening 40mm
Follow us at facebook.com/jaycarelectronics
Versatile switchmode power supplies in a
range of different configurations.
12VDC 5A
MP-3242 $59.95
19VDC 3.4A
MP-3246 $59.95
24VDC 2.7A
MP-3248 $59.95
12VDC 5A (5 PLUGS) MP-3243 $64.95
8
5 WAY CRIMPING TOOL
Consists of all
the standard 1/4" (6.35mm) QC tabs and
receptacles and also odd QC sizes ie: 3.3mm
and 4.8mm sizes. 160 pieces.
1000A TRUE
RMS AC/DC QM-1566
60W DESKTOP STYLE AC ADAPTOR
$ 95
QUICK CONNECT
PACK PT-4530
WAS $69.95
FROM
59 95
$
TH-1828
Cuts and strips wire. Can also
cut bolts with diameter M2.6,
M3.0, M3.5, M4.0 & M5.0.
34 95
42 PIECE ASSORTED
SOLDER SPLICE HEATSHRINK PACK WH-5668
Quickly create sealed soldered joint in one go. Each splice
has just the right amount of solder to create a secure and
well-insulated connection. Includes assorted colours and
sizes to suit various cable size.
See website for full contents.
Catalogue Sale 24 April - 23 May, 2018
EXCLUSIVE
CLUB OFFERS:
FOR NERD PERKS CLUB MEMBERS
WE HAVE SPECIAL OFFERS EVERY MONTH.
LOOK OUT FOR THESE TICKETS IN-STORE!
15% OFF
15% OFF
F
3D
PRINTER
F
O
15%FILAMENT*
3D PRINTER
FILAMENT*
PRINTER
3DEXCLUSIVE
ENT*
MOFFER
CLUB
FILA
*EXCLUDES 3D PRINTER PARTS & ACCESSORIES
NOT A MEMBER? Visit www.jaycar.com.au/nerdperks
NERD PERKS CLUB OFFER
*EXCLUDES 3D
*EXCLUDES 3D
PRINTER PARTS
PRINTER PARTS
& ACCESSORIES
& ACCESSORIES
CLUS E
CLUB OFIV
FER
NERD PERKS CLUB
OFFER
NOT A MEMBER?
NERD PERKS CLUB OFFER
EX
Sign up NOW! It’s free to join.
Valid 24/7/17 to 23/8/17
NOT A MEM
BER?
E Sign up NOW! It’s free to join.
EXCLUSIV
CLUB OFFE
2RFOR
JUST $6
$49.90
BER?
NOT A MEM! It’s free to join.
Valid 24/7/17 to
10% OFF
23/8/17
Sign up NOW
Valid 24/7/17 to
23/8/17
PORTABLE POWER SUPPLY BUNDLE
PURE SINE WAVE INVERTERS 600W - 1500W
9V ALKALINE BATTERY SB-2423 $3.95
2.1MM DC PLUG
WITH SCREW TERMINALS PA-3711 $4.95
9V BATTERY SNAP PH-9232 95¢
VALUED AT
$9.85
MAINS WI-FI
CONTROLLER MODULE
WITH APP
SAVE
35%
MS-6126 REG $29.95
SAVE
15%
12V 600W 20A MI-5720
12V 1000W 30A MI-5722
12V 1500W 30A MI-5724
NERD PERKS
NERD PERKS
NERD PERKS
NERD PERKS
SAVE
SAVE
SAVE
SAVE
20%
20%
SOLDERING IRON TIP CLEANER
TS-1512 REG $12.95 CLUB $9.95
Cleans and rejuvenates soldering iron
tips. 15g.
ABS IP66 ENCLOSURE
HB-6404 REG $34.95 CLUB $27.95
Large 200(L) x 200(W) x 130(D)mm.
35%
20%
THERMAL TRANSFER TAPE
NM-2790 REG $12.95 CLUB $7.95
100x100x0.5mm. Pack of 2.
12V 45W DIN RAIL POWER SUPPLY
MP-3190 REG $49.95 CLUB $39.95
Single output. Built-in EMI filter.
NERD PERKS
NERD PERKS
NERD PERKS
NERD PERKS
SAVE
SAVE
HALF
PRICE!
25%
15%
20%
NON-CONTACT IR THERMOMETER
QM-7218 REG $34.95 CLUB $27.95
Ultra compact. IP67 rated.
30 DRAWER CABINET
HB-6323 REG $29.95 CLUB $24.95
280(W) x 210(H) x 130(D)mm.
ANTI STATIC WRIST STRAP
TH-1781 REG $17.95 CLUB $8.95
Expanded lead length approx. 1.8 m
NERD PERKS
NERD PERKS
NERD PERKS
SAVE
HALF
PRICE!
SAVE
15%
DIGITAL AUDIO CONVERTER & REPEATER
AC-1592 REG $54.95 CLUB $44.95
Signal output to TOSLINK and Coaxial ports
simultaneously.
GREENCAP CAPACITOR PACK - 60 PIECES
RG-5199 REG $11.95 CLUB $5.95
From 0.001uF to 0.22uF. 100V.
NERD PERKS CLUB MEMBERS RECEIVE:
15%
OFF
3D PRINTER FILAMENT*
SAVE
USB 3.0 SDXC/MICRO SD CARD READER
XC-4782 REG $16.95 CLUB 11.95
Supports up to 32GB SDHC and 2TB SDXC.
NERD PERKS
SAVE
25%
25%
250G DUST REMOVER
SPRAY CAN NA-1018
REG $19.95 CLUB $14.95
Non-CFC, non-flammable gas.
BLADE FUSE HOLDER
SZ-2013 REG $34.95 CLUB $24.95
32VDC. 30A.
YOUR CLUB, YOUR PERKS:
REMEMBER TO GET YOUR CARD SCANNED
AT THE COUNTER TO GET POINTS*.
$1 = 1 POINT,
500 POINTS = $25 JAYCOINS GIFT CARD
Conditions apply. See website for T&Cs
*
*Excludes 3D printer parts & accessories
To order: phone 1800 022 888 or visit www.jaycar.com.au
See terms & conditions on page 8.
55
What's New:
We've hand picked just some of our latest new products. Enjoy!
$
59
CAR BOOM BOX
95
WITH AMPLIFER QM-3410
6” woofer and powerful tweeter,
for great overall sound. Play your
favourite music from multiple
sources using various inputs:
RCA, USB, microSD card slot or
stream live via Bluetooth.
• USB & microSD card input
• 1200W PMPO output
• FM Radio
• Power: 12VDC, 2A /240VAC
• 400(W) x 220(H) x 195(D)mm
169
$
$
TPLINK AC1200 VDSL/ADSL
MODEM ROUTER YN-8440
69 95
Takes your standard microphone level and
boosts it for compatibility with line-level
6.5mm inputs. Stereo RCA output.
• Volume control
• Mains powered
9
$ 95
9
Build a project with heaps of 7-segment
displays without using up a lot of IO pins!
• SPI interface
• 15mm panel height with red 9mm digits
• MAX7219 features dimming and digit
decoding
$
Due early May.
39 95
12V BATTERY LOW VOLTAGE
PROTECTOR MB-3677
NBN/UFB REPLACEMENT POWER
SUPPLY 12V 2.5A MP-3538
Automatically shuts off power to
the connected device if voltage
drops below 11.6V.
• Power status indicator
• No installation required
Plug-in replacement power supply for direct
connection into your NBN or UFB connection
box. No wiring required. Suitable for use
with FTTP optical fibre boxes as used in
Australian NBN and New Zealand UFB
networks. Compliant with Australian and
New Zealand Safety Standards.
• Input: 100 - 240VAC 50/60Hz
• Output: 12VDC 2.5A
69 95
19 95
$
LED PROJECTION LIGHT SL-3403
RGB 8X8 LED MATRIX ZD-1810
Light up your home or garden.
Mains powered, IP65 weatherproof
housing. Includes a garden stake,
stand, and wall-mounting kit.
• 125(D) x 155(H) x 100(W)mm
Full RGB 8x8 Matrix controlled
through 32 pins. Flush edges for
creating extended displays.
• 192 LEDs in 64 pixels
12 95
$ 95
8 DIGIT 7 SEGMENT
DISPLAY MODULE XC-3714
19 95
$
$
2 CHANNEL MICROPHONE MIXER
WITH PREAMPLIFIER AM-4201
Unlock the full potential of your internet
connection. Combined dual band Wi-Fi
speeds of up to 1.2Gbps, eliminating lag and
buffering from your online experience.
Due early May.
$
9
$ 95
IR REMOTE CONTROL
FOR ARDUINO® XC-3718
LED TRAFFIC LIGHT MODULE
FOR ARDUINO® XC-3720
LED PUSHBUTTON MODULE FOR
ARDUINO® XC-3722
Add IR remote control to
your next Arduino® project.
Compact design with 21
buttons including numbers
and channel controls.
Set up a basic status display for your next
project. Universal colour codes: RED,
YELLOW, GREEN. Stop, Caution, Go.
• 10mm red, yellow, green LEDs
A simple pushbutton module with a
green LED, ideal for adding an input to a
breadboard design or other project.
• 5V and 3.3V compatible
TERMS AND CONDITIONS: REWARDS / NERD PERKS CARD HOLDERS FREE GIFT, % SAVING DEALS, DOUBLE POINTS & MEMBERS OFFERS requires ACTIVE Jaycar Rewards / Nerd Perks Card membership at time of purchase. Refer to website
for Rewards/Nerd Perks Card T&Cs. PAGE 3: Nerd Perks Card holders receive special price of $34.95 for Power Usage Monitor Project (1 x XC-3802 + 1 x XC-4610 + 1 x XC-3850 + 1 x WH-3025 + 1 x HM-3230) when purchased as bundle. PAGE 7:
Nerd Perks Card holders receive special price of $6.00 for Portable Power Supply Deal (1 x SB-2423 + 1 x PA-3711 + 1 x PH-9232) when purchased as bundle. Nerd Perks Card Holders gets 10% OFF Regular Price for Pure Sinewave Inverters with
Solar Regulators 600W-1500W applies to MI-5720, MI-5722 & MI-5724. 15% OFF 3D Printer Filament (excludes 3D printer parts & accessories).
STUA
RT H
WY
GA
ON
RA
W
YA
R
A
LV
I
CA
NA
ON
COLES
EXPRESS
Head Office
320 Victoria Road,
Rydalmere NSW 2116
Ph: (02) 8832 3100
Fax: (02) 8832 3169
ES
CR
AW
RR
YA
1800 022 888
www.jaycar.com.au
GI
RD
OR
GA
GE
E
AV
N
ST
A
NE
TO
YS
RO
S
OO
Y E
W
WA R
N
TE ENT
GA E C
AR
B
M
O
HO
UT
RD
Y RE
WA NT
TE CE
S
GA ING
TH
OR
PP
O
H
LW
FOR YOUR NEAREST STORE &
OPENING HOURS:
NEW STORE: PALMERSTON
Gateway Shopping Centre, Cnr Stuart Hwy,
Roystonea Ave & Yarrawonga Rd NT 0830
PH: (08) 8900 0025
97 STORES & OVER
140 STOCKISTS NATIONWIDE
Online Orders
www.jaycar.com.au
techstore<at>jaycar.com.au
Arrival dates of new products in this flyer were confirmed at the time of print but delays sometimes occur. Please ring your local store to check
stock details. Occasionally there are discontinued items advertised on a special / lower price in this promotional flyer that has limited to nil stock
in certain stores, including Jaycar Authorised Stockist. These stores may not have stock of these items and can not order or transfer stock.
Savings off Original RRP. Prices and special offers are valid from Catalogue Sale 24 April - 23 May, 2018.
Don’t let one small “oops” fry your
computer – and cost you $$$$!
USB
PORT
PROTECTOR
by Nicholas Vinen
Using your PC or laptop to power a 5V project that you’re working on
is very convenient – but it’s so easy to make a small slip while plugging
something into a breadboard and oops! That’s exactly what happened to
one of our staff members. For a while after the incident, it looked like his
(own!) laptop was toast. But fortunately he was able to safely reset it and
it came back to life. But he was SO lucky! Next time he’ll definitely be
using this simple, economic device . . .
W
e won’t name the hapless person who thought
he’d cooked his laptop. To avoid embarrassment, we’ll simply refer to him as A.P. (ie, Accident Prone).
This is one of those projects we know
will be useful because A.P. kept asking “is
it finished yet” as he obviously needed it!
That incident obviously spooked him and
why wouldn’t it? He could have lost a lot of
work and spent quite a bit of
money and time on buying a
new computer and then setting it up, which could have
taken several days.
We do a lot of development
work, increasingly with Arduinos and similar microcontroller
modules. We also do quite a bit of
bread-boarding, often in combination with the Arduinos.
When you’re doing this kind of work and you have external power supplies or voltage sources connected to your
siliconchip.com.au
circuit, that’s just asking for trouble.
You may not realise it but when an Arduino board (or
similar) is plugged into your computer’s USB port, you’re
just one slip away from potential disaster.
For example, say you’re running the Arduino
from a 12V plugpack, because it’s driving some
12V relays or a motor or whatever. So there’s a
source of 12V right near a bunch of other connections on the Arduino board, just looking
for an excuse to find its way onto the USB
5V rail and into your computer.
One slip, and oops! It could blow
up the Arduino, your shield(s),
and even your computer.
Not only will this USB
port protector vastly improve the chances of
your computer surviving such an event,
it may also prevent
damage to the Arduino board and whatever
Celebrating 30 Years
May 2018 57
Fig.1: the circuit diagram of the USB Port Protector. Diode D3, zener TVS1 and transistor Q1 are all connected between
VCC and GND and shunt current when an excessive voltage is applied, while polyswitch PTC1 and fuse F1 prevent large
currents from flowing if the fault is serious. Diodes D1 & D2 and zener TVS2 protect the D+ and D- data lines.
shields or other circuitry are plugged into the USB port.
We can’t promise it will be 100% safe but it’s certainly a
lot safer than if you aren’t using any protection...
You might expect USB ports to have some kind of builtin protection against external voltages being fed in. After
all, all kinds of devices can be plugged into these ports, including external hard disks and amplifiers and other gear
which has its own, separate power supply.
In fact, many USB ports do have some protection, such
as series PTC thermistors (“polyswitches”) to limit fault
currents, transient voltage suppressors and so on. But this
protection varies between computers and is often absent
in laptops and notebook computers.
Let’s face it, there’s a lot less space inside portable computers – and manufacturers also want to keep the computer
as light as possible and save money where they can. That
means leaving out anything that isn’t absolutely necessary.
Regardless of what sort of protection your USB port
may have, this USB Port Protector is small and cheap, so
why not add in an extra layer of defence? If you ever manage to activate its protection, it will have paid for its cost
many times over!
Circuit description
The circuit of the USB Port Protector is shown in Fig.1.
USB plug CON1, which plugs into your computer, is shown
on the left side while the USB socket, CON2, goes to the
connected device (Arduino, etc) is on the right. Just to be
clear – the potential danger of overload from excessive
voltages or currents comes via CON2.
The ground connection and the two differential data lines,
D+ and D-, are wired straight through between plug and
socket (ie, CON1 and CON2) while 5V flows through fuse
F1 and positive temperature coefficient thermistor PTC1.
58
Silicon Chip
We’ve used both a fuse and PTC because the fuse reacts
faster to very high currents, protecting the rest of the circuitry on the board if there’s a serious fault, but the PTC
does not need to be replaced if it “trips” and helps the circuit to handle moderate overloads without damage.
PTC1 normally has a low resistance – around 100mΩ
below 1A – but if the current through it increases, its resistance rises, limiting it at around 2A (given enough time
for it to heat up). This would normally only occur if the
5V line rises above 5.5V and the Port Protector is shunting
current in order to prevent it rising further.
In fact, the Port Protector does very little as long as the
USB supply voltage is in the normal range of 0-5.25V and
the D- and D+ lines are in the normal range of 0-3.3V. Green
LED1 lights up to indicate power is present but that’s about
it. The unit draws around 3mA in this condition.
If the 5V rail is pulled negative, ie, below 0V (eg, you’ve
accidentally shorted it to the output of a transformer or
some other supply rail) then schottky diode D3 will conduct. This prevents VCC from going below about -0.5V.
D3 is a high-current diode, capable of handling 15A continuously and 275A for around 5ms, so it makes a very effective clamp. It limits the voltage on VCC to -0.55V at 15A,
so your PC is safe from damage from negative voltages on
the supply line.
Should the overload condition persist, either PTC1 will
limit the overload current to a safe level or F1 will blow, disconnecting the compromised circuitry from your computer.
Clamping positive voltages
It’s even more likely that you might accidentally short
the 5V rail to a higher voltage, eg, 12V from a car battery.
Just think of the heavy currents which will fry anything
connected to it! The Port Protector has active and passive
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Fig.3: the fuse
blow time for
F1 (black) and
“trip” time for
PTC1 (blue)
at various
current levels.
The relevant
portion of Q1’s
SOA curve
from Fig.2 is
plotted in
red and you
can see
that F1 will
protect Q1
for fault
currents
above 2A.
Fig.2: safe operating area (curves) for the ECH8102 PNP
transistor, used in this device as a protective shunt. The
vertical red line corresponds to a shunt voltage of 5.5V
and its intersection with the SOA curves shows how
long the transistor is guaranteed to survive at various
collector current levels.
systems to handle this situation.
The active system is the first line of defence. It comprises high-current PNP transistor Q1 and shunt voltage reference REF1. The 1.2kΩ/1kΩ resistive divider across the 5V
supply feeds 45.45% of the supply voltage to the adjust
terminal of REF1. It’s designed to sink current into its cathode terminal as soon as this adjust terminal exceeds +2.5V.
So given the voltage divider, that means that it will sink
current when the supply exceeds 5.5V (2.5V ÷ 45.45%).
This will cause a voltage to develop across the 470Ω resistor and once that voltage exceeds around 0.7V (Q1’s baseemitter voltage), Q1 will switch on and shunt the 5V supply rail, pulling it down.
In this manner, REF1 and Q1 act to limit the 5V supply
rail to just over 5.5V. Q1 is capable of handling more than
10A but since there will be 5.5V between its collector and
emitter, it can only do that for a very short time before it
overheats. But at the same time PTC1 will rapidly heat up
and increase its resistance, to limit that current. And in
any case, if the current exceeds 3A, for example, the fuse
will very quickly blow before Q1 is damaged.
So REF1/Q1 act together as a very precise and very fast
clamp. When REF1 is sinking current from Q1’s base, Q2
will also normally switch on as its base is also pulled
around 0.7V below its emitter, via the 10kΩ resistor. This
will light up red LED2, indicating that the clamp is operating and that you have a problem. LED2’s current is limited by its low base current and relatively fixed gain (hFE).
REF1 can sink up to at least 100mA and Q1 has a current
gain (hFE) in the hundreds, so Q1 is more than capable of
passing its full peak current rating of 24A in this circuit.
Note that LED2 may go out if there is a persistent overload, since when Q1 heats up, its base-emitter voltage will
drop and it may drop low enough below Q2’s base-emitter switch-on voltage that it will no longer switch on. But
chances are that PTC1 and/or F1 will have acted to limit
the fault current by that stage anyway.
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The only problem with the clamp provided by Q1 and
REF1 is the reaction time. It takes a short time for REF1
to react to an increase in the feedback voltage and it also
takes time for Q1 to switch on – around a microsecond.
Passive clamping
This is why we also have a transient voltage suppressor, TVS1 connected across the 5V supply rail. It’s a passive device which will react more-or-less instantly to excessive voltage.
But like most zener-type devices, the difference between
the voltage at which it will start to conduct current and the
voltage across it when a large current is flowing is quite
large. We’ve selected the most suitable device possible but
it’s still not ideal.
The “working voltage” for TVS1 is defined as 5V but
it’s designed to pass only 1mA or so at 6.0V. The clamping voltages are specified as 9.8V at 1A and 13.5V at 42A.
So clearly, we can’t rely on this device to protect the PC
since it would allow quite a high voltage to be fed back in
before taking effect. Hence our dual-action strategy, with
TVS1 there to limit very brief, high-voltage excursions (eg,
a static discharge) and also to “fill in the gaps” for the short
period until Q1/REF1 are able to switch on and shunt the
fault current.
Protection for the signal lines
We’ve also included 3V transient voltage suppressor
TVS2 (take care of the metal tab on the underside of its
body, as it could short out the connection when soldered)
and dual schottky diodes D1 and D2 to protect against damaging voltages being fed in via the D+ and D- signal wires.
This is unlikely, since these lines normally go straight to
some sort of USB/serial adaptor or micro on a development board and so there aren’t many exposed components
to accidentally short.
But it’s still possible that a high voltage fed into your
Celebrating 30 Years
May 2018 59
+5V rail (or +3.3V rail, or some other supply point) could
damage the USB/serial adaptor or microcontroller and allow current to flow through into the D+ and/or D- lines.
So we decided that we should provide at least some protection for these lines, as well.
The half of dual diodes D1/D2 that connects between
ground and the signal line prevents them from being pulled
too far below ground.
We’re using smaller diodes here since a large diode would
have too much capacitance and would interfere with USB
signalling. But these diodes are still rated at 300mA continuous and 1.25A for 10ms, with a forward voltage below
1V up to several hundred milliamps. So they should provide decent protection.
TVS2 has a breakdown voltage of around 3.6V at 1mA
and a clamping voltage of 6.5V at 25A. So the combination
of D1/D2 and TVS2 should conduct significant current away
from the D+/D- lines well before their voltages reach 5V.
Most USB ports would not be damaged by these voltages.
We can’t put a voltage suppressor like TVS2 directly between the D+ and D- lines and ground because it would have
far too much capacitance. But the series diodes between
D+/D- and TVS2 have a much lower capacitance that’s effectively in series with that of TVS2, so they have virtually no effect on signalling. We tested our prototype with
a “hi-speed” USB card reader and it functioned normally.
Is it bulletproof?
In a word, no, but if it does fail, the Port Protector is likely to fail in such a way that it still protects your computer.
Parts list – USB Port Protector
1 double-sided PCB, coded 07105181, 32.5 x 19mm
1 PCB-mount USB Type A horizontal plug (CON1)
1 PCB-mount USB Type A horizontal socket (CON2)
[eg, Altronics P1300]
1 SMD fuse, 3216/1206 package, 1A super fast blow [Vishay
MFU1206FF01000P100]
1 SMD 1.1A PTC thermistor, 3216/1206 package
[Bourns MF-NSMF110-2]
1 30mm length of 20mm diameter clear heatshrink tubing
Semiconductors
1 AN431AN shunt reference IC, SOT-23 (REF1)
1 ECH8102 12A PNP transistor, ECH8 (Q1)
1 BC856 100mA PNP transistor, SOT-23 (Q2)
1 high-brightness green LED, 3216/1206 package (LED1)
1 high-brightness red LED, 3216/1206 package (LED2)
1 CDSOD323-T05S transient voltage suppressor, SOD-323
(TVS1)
1 SM2T3V3A transient voltage suppressor, DO-216AA (TVS2)
2 BAT54SFILM dual 300mA schottky diodes, SOT-23 (D1,D2)
1 15A 30V schottky diode, DO-214AB (D3; MCC SK153)
Capacitors
1 100nF SMD X7R ceramic, 3216/1206 package
Resistors (all SMD 3216/1206 package, 1%)
1 47kΩ
(coded 4702 or 473)
1 10kΩ
(coded 1002 or 103)
1 1.2kΩ
(coded 122)
1 1kΩ
(coded 102)
1 470Ω
(coded 471)
60
Silicon Chip
While our testing shows that it’s robust and can handle significant overloads without damage, if you apply just the
right (worst possible) combination of voltage and current, it
may be possible to blow Q1 or TVS1 before fuse F1 blows.
Still, our testing suggests that the most likely outcome of
a serious overload is for F1 to blow and at least it’s cheap
and (relatively) easy to replace.
The difficulty in designing a circuit like this to be able
to withstand anything you can throw at it is that in order
to effectively protect against a high current source being
connected to the VCC line, it needs to absorb quite a lot of
power in a brief period. And while the PTC and/or fuse
should ideally cut the power to protect the other components, they may not be fast enough.
Fig.2 shows the “safe operating area” (SOA) curves for
transistor Q1, taken from the ECH8102 data sheet. We’ve
added a vertical red line to show the typical voltage of
about 5.5V across Q1 while it is conducting.
While this is a high-current transistor, it is quite tiny so
if a high current is applied, it will quickly overheat and
might fail. As shown in Fig.2, it’s guaranteed to survive
24A at 5.5V (132W!) for somewhere between 500µs and
1ms. For longer periods, the maximum allowable current
is lower; around 3A (16.5W) for 10ms, 1.5A (8.25W) for
100ms and 300mA (1.65W) continuously.
Beyond this, it may survive but that isn’t guaranteed. Our
testing has shown that for a single pulse, these ratings are
very conservative. But it’s good practice to design a circuit
to stay within these ratings.
The “trip” times for PTC1 (blue) and F1 (black) are shown
in Fig.3. We’ve also plotted the relevant portion of the SOA
curve for Q1 in red so that you can compare them. As you
can see, F1 responds considerably faster than PTC1 and
in fact is very likely to blow before Q1’s SOA is exceeded
for currents above 2A.
For fault currents between 300mA and 2A, it’s possible
that Q1 will overheat and fail before either F1 blows or PTC1
acts to limit the current. And in fact, PTC1 is not guaranteed
to do anything for fault currents below 1A. You will need
to notice red LED2 lighting and resolve the fault yourself.
Still, as we said above, the ratings for Q1 seem to be pretty conservative and as long as the overload is limited to no
more than a second or two, we would expect it to survive.
Looking at Fig.2, you may wonder why we’ve bothered
with the PTC at all, given that its “trip” current is higher
than the fuse blow current over most of the graph. But keep
in mind that PTC1 is considered to be “tripped” when it
has reached a high enough resistance value to keep the
fault current below 2.2A. It will still have some effect in
reducing the fault current even at lower current levels and
shorter time spans, because its resistance will start to increase well before it has fully tripped.
And you also have the option of replacing F1 with a zeroohm resistor (or just soldering across the pads) and relying
on PTC1 to limit fault currents. This does increase the risk
of blowing Q1 in a serious fault (although, as we said, it’s
pretty robust) but doing so would also increase the chance
that the unit will survive a moderate overload unscathed
and you won’t have a blown fuse to replace.
Note that while replacing Q1 is a bit of a pain, it’s actually quite cheap (under $1) so if Q1 does “throw itself on
the grenade” and fail while protecting your computer from
damage, at least it isn’t an expensive failure.
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Figs.4&5: top and bottom overlay diagrams for the USB Port Protector. Use these as a guide during construction. Be careful
with the polarity for TVS1, TVS2, Q1 and LEDs1&2. It’s easiest to start by fitting Q1 and TVS1, then the remainder of topside SMD components, then the bottom-side components and finally, CON1 and CON2. The matching photographs above
are reproduced close to twice actual size, for clarity.
Sourcing the parts
Most of the parts are surface-mount devices (SMDs) and
they are all available from Digi-Key or Mouser in the USA.
Most are also available from element14 in Australia.
While both Digi-Key and Mouser offer free express international delivery for orders over $AU60, the parts for
this project will cost you much less than that.
So we are also making the parts available a kit, to make
it easier to build the USB Port Protector. The complete kit,
including PCB and the USB input and output sockets will
sell for $15.00 (Cat SC-4574).
Construction
The USB Port Protector is built on a double-sided PCB
that measures 32.5 x 19mm and is coded 07105181. All
but four of the components are mounted on the top side
of the board, as shown in the overlay diagrams, Figs.4 & 5
and matching photos. The only through-hole components
are the USB plug and socket.
By the way, you may notice a minor difference between
the overlay diagrams and the PCB photos: we’ve changed
TVS2 to a more suitable part since building the prototype.
Most of the parts are fairly easy to solder, although some
of them are quite close together, to keep the unit compact.
It’s easiest to do in the following order.
Start with transistor Q1. This is in a fairly small ECH8
package, with four short leads on each side. The good news
is that most of the adjacent leads are connected together
so it doesn’t matter if you bridge the pins when soldering
(in fact, it’s pretty much unavoidable). Pin 4 is the base
connection and you need to make sure it doesn’t short to
pin 3, the emitter.
Start by identifying pin 1. There is a dot printed in the
corner on the top of the package but you will need a magnifier and good light to see it. Orientate the part so that it
matches the pin 1 markings on the PCB and smear a thin
layer of flux paste on all eight of its pads.
Apply a tiny amount of solder to the pad for pin 4, then
heat this solder while sliding the part into place. Check
that the other seven pins are correctly located above their
pads using a magnifier. If not, re-heat the solder joint and
carefully nudge the part. Repeat as necessary until it’s lined
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up, then solder the four pins on the opposite side of the
package. These are all joined together so you can do it as
one big solder joint.
Now apply solder to the three remaining pins and add
a bit of fresh solder to pin 4 as well. To tidy up the solder
joints, apply a little more flux paste on top of the solder and
then use some solder wick to remove the excess. Clean up
the flux residue with some methylated spirits, isopropyl
alcohol or other flux cleaner and then inspect it visually
to ensure all the solder joints are good.
That’s the trickiest part out of the way. Next, solder TVS1
in place, next to Q1. It’s fairly small and its cathode stripe
will not be terribly obvious so again, use magnification to
identify the cathode and orientate it correctly before tacking it place and soldering the opposite pin.
Now solder the SMD passive components in place; this
includes five resistors, one capacitor and the PTC thermistor. None are polarised; just be careful to fit each in
the location shown in Fig.4. The resistors will be printed
with a small code indicating their value (eg, 1.2kΩ code
is 122; or 12Ω x 102) but the capacitor will not be marked.
The resistor codes are also shown in the parts list opposite.
The next components to mount are reference REF1 and
transistor Q2. These are in identical SOT-23 packages so
don’t get them mixed up after taking them out of their packaging. They are polarised but have three pins each so the
orientation is obvious – see the pinouts in Fig.1.
Next are the two LEDs. Usually, the cathode is marked
with a green dot but sometimes the anode is marked instead. The easiest way to check is with a DMM set on diode test mode. The LED will light up with the red probe
connected to the anode and black to the cathode. You can
confirm the colour at the same time. Note that some DMMs
(eg, those powered by two AA cells) may not apply sufficient voltage to light up a green LED.
Solder these where shown on the overlay diagram; LED1
is green while LED2 is red and the cathodes are orientated towards the USB plug, as shown by the “K” markings
on the PCB.
Now solder schottky diode D3 in place. Add a little flux
paste to the pads first as it’s quite large but the procedure
Celebrating 30 Years
May 2018 61
is much the same as for the other two-pin devices. Just
make sure you apply the iron for long enough
to form good solder fillets between the
PCB and terminals of the device.
Then flip the board over and fit the
four remaining SMDs on the
bottom side, as shown
in Fig.5. D1, D2 and
ZD1 are polarised; also
pay particular attention
to the location of the
cathode stripe on ZD1.
The fuse is not polarised.
Finally, fit the USB plug and socket as shown. Both need
to be pushed down firmly onto the PCB before soldering.
The plug has a notch on the underside which the edge of
the PCB fits into. Note that the USB plug pins may be quite
short and may not protrude very far through the bottom of
the PCB, so it’s a good idea to solder them on both sides.
Just make sure you don’t accidentally bridge the pins.
Testing
Inspect the board to verify that all the solder joints are
good and that you have no unwanted bridges, then plug
it into a USB port on your PC. If you have a USB charger,
you could use that instead. Check that the green LED lights
up but the red LED should not.
You can then carefully measure the voltage across D3.
You should get a reading in the range of 4.5-5.25V (usually quite close to 5V), with the red probe to its cathode
(striped) end.
Now plug a small device like a USB card reader or flash
drive into the socket and verify that it powers up correctly.
Try reading the contents of the card/flash drive on your PC
and verify that it works normally without any unexpected
disconnection events.
If you want to verify that the Port Protector will definitely
protect your computer, you will need a ~6V supply and a
resistor with a value between 2.2Ω and 10Ω.
Unplug the Port Protector and anything that’s plugged
into it and use a clip lead to connect the USB socket shell
to the ground terminal of your 6V supply. Connect one end
62
Silicon Chip
of the test resistor to the
positive output of the 6V
supply (battery pack,
plugpack, etc) and then
touch the other end of
the resistor to the USB
socket pin that’s immediately adjacent to
fuse F1, on the underWe finished
side of the board.
our Port Protector
If you can do this
with clear heatshrink tube . . .
while
looking at the
just in case A.P. managed to drop
something into the Protector PCB! top of the board, you
should see both LED1
and LED2 light up. LED2 indicates that the protection is
operating. If you have a helper, they could measure the
voltage across D3. It should be close to 5.5V. This confirms
that the device is working.
Using it
To avoid accidentally shorting the 5V supply or either
of the signal lines during use, we suggest you encapsulate
the entire device in a short piece of heatshrink tubing, as
shown above. Clear tubing is convenient since you can still
see the components – but any colour will work.
Cut the tubing so that it covers the entire USB socket, up
to the lip that’s around the open end, and the very base of
the USB plug, up to where it projects from the PCB. Then
it’s just a matter of applying a little heat, eg, from a hot air
gun, hair drier or lighter (with the flame some distance
below the tubing).
Rotate the assembly until the tubing has shrunk into
place and try to avoid burning yourself in the process. If
it gets too hot to hold, put it down and let it cool before
shrinking the remainder of the tubing.
If you manage to blow the fuse, you will simply have to
cut the tubing off, desolder the fuse, clean the old solder
off using flux paste and some solder wick, solder a new
fuse in place and apply a fresh length of heatshrink tubing.
Or if you’re really clever, you may be able to cut a flap
in the tubing around the fuse, replace it and then glue the
flap back in place.
SC
Celebrating 30 Years
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SERVICEMAN'S LOG
The Serviceman's Curse
I reckon servicemen are cursed. I don’t mean
that people swear at us a lot (though they
might!), I mean that we bear the Curse of the
Serviceman. This means that when anything
breaks down, we always consider the repair
option first. It doesn’t really matter what has
broken or whether we usually repair or service
these things in our day jobs, it’s just that we
simply can’t help ourselves from wanting to fix
something that’s broken.
This is mostly fine if we just have
ourselves and our own household to
think about, but for some, it also means
that when any of our friends, acquaintances or colleagues break something,
we are often expected to fix their stuff
as well, just because we are servicemen! As if being our own go-to repair
siliconchip.com.au
guy isn’t enough. This is what I mean
by a Serviceman’s Curse.
While the more prosperous servicemen among us may have learned
to suppress the curse and are able to
chuck away the broken device and go
out and buy a replacement instead, for
me and many others, that is a difficult
Celebrating 30 Years
Dave Thompson*
Items Covered This Month
•
•
•
•
Car battery charger
CIG Transmig 200 welder
Compaq CQ61 laptop R&R
MR16 LED downlight repair
*Dave Thompson runs PC Anytime
in Christchurch, NZ.
Website: www.pcanytime.co.nz
Email: dave<at>pcanytime.co.nz
decision to make and we would have
to force ourselves to even consider it.
When something in my household
breaks, my first instinct is to weigh up
all possible options to repair it myself,
with the very last option being to buy
another one. Perhaps if I won big on
the lottery, or inherited a few gazillion
May 2018 63
bucks, this attitude might change – I’d
sure like to test that theory! But in the
meantime, I always consider repair before replacement.
I know plenty of people who think
the other way. They replace anything
that breaks with the latest and greatest new version, regardless of whether
it was repairable or not, but not many
of these people are servicemen. I can’t
really blame them; after all, they don’t
bear the curse!
Of course, there are exceptions; if a
repair isn’t feasible or economically
sensible, such as a dropped dinner
plate or wine glass then the curse
doesn’t really apply. Having said that,
I have been known to glue people’s favourite plates or porcelain figurines
back together. But if the broken article is even remotely within my skillsphere, then the curse awakens.
My neighbour invokes the
curse
A recent example involves a neighbour who tried to start his car the
other day while he still had a battery
charger connected. He subsequently
discovered that the charger no longer
worked.
I’ve done this myself in the past and
perhaps due to dumb luck, I’ve had no
problems, though it stands to reason
that one probably shouldn’t leave anything connected when cranking the
engine unless it’s designed to handle it.
This is especially true if the car battery is dead flat to begin with and we
are essentially relying on the output
of the charger alone to supply enough
grunt to fire up the motor. In such situations, the current draw through the
leads and internal components of the
charger can be considerable, and when
the car starts there is even more current introduced into the circuit by the
alternator’s output.
Many car battery chargers are simply
not designed to withstand this kind of
punishment.
Ordinarily, a guy would just think
the charger was dead, chuck it in the
bin and go out and buy another one
– especially given the current (hah!)
prices of chargers these days. In this
case, the sticky wicket was that my
neighbour had borrowed the charger
from a friend, and while it was by no
means new, it looked to him to be a
reasonably flash model as far as car
battery chargers go. He didn’t relish
the thought of having to cough up to
replace it.
He brought it over to my workshop
in a bit of a panic and asked if I could
have a look at it, at least to see whether
it was repairable. If not, he’d be chowing down on a large crow sandwich
and splashing out for a new charger.
I promised to see what I could do,
mindful of the fact that this would
probably end up being one of those
“pro bono” jobs all servicemen get saddled with and would more than likely
take up time I could ill afford to spare.
That said, I couldn’t refuse a neighbour
in need, especially as it was highly
likely that I could fix the charger. The
Serviceman’s Curse strikes again!
The charger was about as simple as
any electronic device can get. A mains
cable enters the plastic case through a
cheap-but-effective clamping arrangement and connects via a fuse to the
primary of a reasonably heavy-duty
transformer. The secondary is wired
to a small PCB with a glass thermal
cut-off switch, a couple of carelesslyplaced diodes and three LEDs.
Attached to that board are a couple of cables which then exit the case
through a rubberised grommet with
comically-large alligator clips on each
end; one red and one black. He might
have thought it flash but I disagreed;
it was a bog-standard battery charger.
The battery connector cables looked
to me to be a little on the light side,
considering the size of the transformer
and the cables that make up your average set of jumper leads. But I suppose
these modern-style, piddly-thin wires
would have the advantage of being
self-limiting and besides, they’d ordinarily only have to cope with a few
amps at the most for relatively short
periods anyway.
Servicing Stories Wanted
Do you have any good servicing stories that you would like to share in The Serviceman
column? If so, why not send those stories in to us?
We pay for all contributions published but please note that your material must
be original. Send your contribution by email to: editor<at>siliconchip.com.au
Please be sure to include your full name and address details.
64
Silicon Chip
Celebrating 30 Years
The LED indicators were mounted
inside the case but shone to the outside world by way of clear plastic
light tubes.
I’ve seen this method used before,
especially in devices like amplifiers,
radios and laptops and it tends to work
fine for them. But the inside of this
charger gets hot then cools down, over
and over, and this, when combined
with the natural ageing process, causes
the plastic to go opaque.
Because of this, the amount of
light reaching the user would likely
be pretty low. I’d wager these indicators would be barely visible during
the day, especially in bright sunlight.
I’d confirm that theory once I’d fixed
the thing…
Testing the charger
I plugged the charger into my lightbulb based load box and flicked the
box’s socket switch to on. I’ve gotten
into the habit of using this load box,
largely because it is set up on my workbench permanently and this makes
it the handiest power socket for any
mains-powered devices that cross my
desk. It can’t hurt, regardless of whether
I really need it or not.
The neighbour told me he’d plugged
the charger in and got no indication of
power, and with no specific mention
of fuses blowing or circuit-breakers
popping, it was unlikely that a shortcircuit was present. However, the test
rig socket is right there, so I used it.
The load box consists of two 250W
incandescent bulbs (remember them?)
mounted in a couple of lamp sockets
screwed to the top of a suitably-sized,
plastic hobby box.
The lamps are wired in series with
the Active wire and all three mains
wires are then terminated into a standard dual, switched mains socket on the
front of the box. The box is powered
from a wall socket.
I generally power any mains-powered equipment under test into the protected socket on the load box. If there
is an internal short or other, similarlynasty electrical fault present, the lights
glow to let me know while they limit
the voltage applied to the load, giving
me time to switch everything off safely
without the drama of blowing fuses or
the guts of the device under test flying
across the workbench.
I also have an adjustable auto-transformer (generally known as a Variac,
but mine isn’t Variac-branded) and I
siliconchip.com.au
use that for similar jobs, especially
those where it is more prudent to
slowly bring up the voltage than apply it all at once. I mostly use the lightbulb load box for mains-powered stuff
though, especially valve amps and
similar devices.
Both methods save replacing fuses
and reduce the risk of damaging other equipment on the same circuit, and
both are invaluable to the serviceman
who needs to work with mains-powered devices and they are well worth
the effort of building or purchasing.
As expected, the battery charger
did nothing on switch-on. No bright
lights on the load box and nothing
on the front panel of the charger. For
all intents and purposes, it was as if I
hadn’t plugged it in.
Delving into its innards
My first thought was a blown fuse.
There must be one, and while some
chargers have a fuse socket accessible
from the outside, this model didn’t,
so it had to be inside. Getting in was
easy enough, with only four long, PKstyle screws holding the case together
at each corner.
It is refreshing to be able to open up
something without having to resort to
cruder methods of removing those ridiculous and unnecessary “security”
fasteners that seem to be all the rage
these days.
It’s also getting increasingly rare to
find the screws out in the open and easily accessible to normal tools, instead
of being buried inside deep channels
or concealed under rubber feet, plastic bungs or warranty seals.
Once the screws were out, the case
split apart easily and the various components were laid bare. There indeed
was a fuse, in line with the Active lead
and right next to the cable clamp. The
fuse was obviously intact as I could
see it clearly, but I popped it from its
holder and checked it with my meter
anyway.
If it was dead, it wouldn’t be the first
time a fuse appeared undamaged but
was, in fact, open-circuit; a classic beginner’s trap. In this case, though, the
fuse rang out OK. On to the next component in the troubleshooting queue:
the transformer.
This also looked OK but then again,
something would have had to fail catastrophically for it to appear otherwise.
I measured the secondary windings
and got around 0.5W on my analog
siliconchip.com.au
multimeter; probably not that accurate
a reading but at least it had continuity.
When I measured the primary though,
it appeared to be open circuit.
A current surge might have burned
out the windings but I could see no
darkening of the yellow tape they
typically use to bind transformer coils
with and there wasn’t even the faintest
whiff of that distinctive burnt-enamel
smell that almost always goes handin-hand with high-current component
failures. I’d have to dig further.
After making a note of what went
where, I desoldered the transformer’s
wires and removed the four screws going down through the laminations and
holding it to the bottom of the case. I
do like these simple-to-disassemble
devices.
With the tranny out and sitting on
the bench, I re-measured the windings
with another meter just to be thorough
but got the same result; the primary
side was definitely open-circuit. Ordinarily, this is where most servicemen/repairmen would start looking
for a replacement transformer but as
I’ve already made clear, I hate throwing
things away (that curse again).
Anyway, without having any part
numbers or any other information
written on the component, I’d have
to either take an educated guess as to
its specifications or assess other, similar chargers to determine or approximate the voltages and ratings of their
transformers.
Either method would likely lead
me to a replacement component that
would be close enough for rock and
roll – it’s a car battery charger after all
– but that’s a bit too wishy-washy for
my liking. Besides, I wasn’t finished
with this dead transformer yet.
Fixing it the hard way
I started by removing as much of the
yellow tape that bound the windings
as possible, a task made difficult by
the way the E-I core kept getting in the
way. I got out one of my craft knives
and slid the edge of the blade between two of the hundreds of tightlylaminated shaped metal shims that
make up the core.
It went in relatively easily, meaning the laminations weren’t potted or
bonded together with varnish, as some
are. I removed the transformer’s folded
heavy-metal outer cover by bending
four metal locking tabs on the base out
of the way and lifting it clear.
Celebrating 30 Years
With the core now totally exposed,
I used a sharpened flat screwdriver
to carefully pry free a couple of the
E and I-shaped laminations from one
side. Now loosened, I could ease out
the rest of the laminations one by one
until there was a large pile of them lying on the bench.
What remained was a hard, white
plastic bobbin that held the primary
and secondary windings, and it was a
simple matter to strip the remaining
yellow tape away from the primary
side. Once gone, I could see nestled
at the very top of the now-exposed
windings a black, rectangular, twolegged component that I assumed to
be a thermal fuse, wired in series with
the primary winding.
I already knew it would be open circuit, as the clean state of the windings
showed nothing had burned out but
I measured it anyway. It was dead as
John Cleese’s parrot. I unsoldered it
and measured the windings beyond
it. My meter made it around 50W and
whether that was about right or not
I’ll leave to the mathematicians; all
I needed to know was that it seemed
about right to me.
I located another thermal fuse in
my parts store, which according to the
data sheets I downloaded from the web
was a suitable substitute for the original. Once soldered in, I re-bound the
primary windings with similar tape
and set about re-assembling the core,
a grubby job as each one is coated in
an anti-corrosion substance that if not
May 2018 65
actually oil, has very much the consistency and feel of it.
However, after I’d stuffed as many
of the laminations back into the bobbin as I could, I still had about a dozen “E”s and “I”s left over. No biggie,
or so I thought.
After a quick megger check to make
sure my insulation was good, I temporarily rigged up a mains cable to the
primary and used my auto-transformer
to power it up slowly. My multimeter
showed the secondary voltage rising
as expected as I wound up the power,
but then it happened; the transformer
started to buzz.
Above about 150VAC, the transformer was buzzing very loudly; I
guess I was going to need those extra
laminations after all! By using some
wood-workers’ clamps and a lot of
very colourful language, I managed
to shoe-horn all the remaining laminations back into the core. It was then
thankfully buzz-free.
That just left the simple matter of
reassembling everything, giving it another insulation test and trying it out.
It worked as well as it did before and
while those LEDs were barely visible,
my neighbour was hugely relieved and
grateful. He offered to pay, but I declined; it was the neighbourly thing
to do. Darn this Serviceman’s Curse!
CIG Transmig 200 welder repair
Sometimes it doesn't take a large
fault to stop equipment worth thousands of dollars from working. G. S.,
of Castle Hill, NSW, recently saved a
heavy-duty welder from the boneyard
and here is how...
My ex-neighbour Paul is into old
Ford Falcons from the 1960s. He restored a '64 ute some three years ago
and has two 1964 2-door coupes awaiting restoration. He also recently acquired a '63 Falcon station-wagon that
he's working on at the moment.
Sitting in his garage among that lot
is a real gem – a 1967 Ford Mustang
coupe that's currently a body shell and
a pile of parts. So why is he mucking
around with the Falcon station-wagon and not putting all his effort into
the Mustang restoration? I dunno but
he'll come up with all sorts of excuses
if pressed on the matter!
Vehicle restoration projects invariably require rust repairs and so, about
eight years ago, Paul acquired a second-hand CIG Transmig 200 welder.
This is a large 3-phase machine and
66
Silicon Chip
The faulty
contactor shown
inside the welder.
is mounted on a sturdy metal trolley
that can be trundled around in his
garage. It probably cost around $3000
new but had been acquired for a pittance by one of Paul's mates when a
business shut up shop.
Having no real use for it, the mate
eventually passed it on to Paul for an
even lesser pittance and he subsequently used it while restoring the ute.
It then sat unloved at the back of Paul's
garage for three years until he got his
station wagon restoration underway.
It wasn't long before the welder
was needed for this project and so the
machine was duly trundled out and
hooked up to the garage's 3-phase power
outlet.
Paul then pressed the trigger on the
wire-feed nozzle to check its operation
but no wire fed through. Instead, the
3-phase circuit breaker in the household fuse-box tripped out.
Puzzled by this, Paul reset the breaker and pressed the wire-feed trigger a
second time. The circuit breaker immediately tripped out again and it did
so a third time after he had reset it.
At that stage, Paul decided to ask my
brother, who is a licensed electrician,
to take a look at the machine for him.
I went along for the ride and when we
got there, we found that Paul had already removed the side panels from
the machine.
It took my brother just a few minutes to diagnose a faulty contactor.
This normally pulls in and powers up
a large transformer and various other
parts in the machine when the wireCelebrating 30 Years
feed trigger is pressed.
Our snap diagnosis was that the
contactor was probably full of gunk
and this conclusion was reinforced
when my brother demonstrated that
the machine could be powered up by
manually assisting the contactor to
“pull in” by pressing on it with an insulated probe.
Even then, the wire-feed mechanism
still wasn't working, so it looked like
this welder had two separate faults:
(1) a faulty contactor and (2) a fault in
the wire feed mechanism or in the circuitry that controls the wire feed motor (or perhaps even a faulty motor).
There was no point trying to diagnose the wire-feed problem until the
contactor problem had been resolved,
so it was up to Paul, an electrical fitter by trade, to take things from there.
He's not a man to let the grass grow
under his feet and so, the very next day,
he carefully labelled all the relevant
connections, then pulled the contactor out and cleaned it to within a millimetre of its life.
It did indeed prove to have a lot of
gunk inside and when it was refitted,
he was gratified to find that it now
pulled in when the wire-feed trigger
was pressed without tripping the circuit breaker. So that solved problem
number one.
Now for problem number two. With
no access to a manual, circuit diagrams
or spare parts, Paul figured that his
next best step was to seek professional
help to get the wire feed mechanism
working.
siliconchip.com.au
The faulty tantalum capacitor on
the control board was replaced
with a similar electrolytic
capacitor, with the adjacent 7812
regulator circled in red.
As a result, he loaded the machine
onto a trailer and carted it off to a specialist welder repair shop. They duly
called back a week later to say that both
the wire-feed mechanism and motor
were OK and that they had diagnosed
a faulty control board.
Unfortunately, given the age of the
machine (it's probably late 1980s or
early 1990s vintage), replacement control boards were no longer available.
And as far as they were concerned,
without a replacement control board,
the machine wasn't repairable.
Never one to give up, Paul now figured that he would try to get the control board fixed. And that's when he
flicked the problem my way.
I suggested that the best approach
would be to remove the board from
the machine and drop it around to me.
That way, I could inspect the board for
dodgy solder joints and test the various
semiconductors, electrolytic capacitors
and other parts at my leisure.
Having made the suggestion, I
thought he might drop the board off
in a week or two but as I said, he's not
a man to let the grass grow under his
feet. He turned up at my house within
the hour, clutching his faulty control
board with the external wiring leads
all carefully labelled.
I took a look at it the next day. Despite its age, it was still in good condition with no signs of corrosion. Its
main parts included a couple of 555
timer ICs, an LM3900 quad amplifier IC, several transistors, a relay, two
stud-mount SCRs and a stud-mount
siliconchip.com.au
diode. The external leads ran off to a
couple of pots and some spade clips.
So had one of the semiconductors
failed? Or was it a faulty relay, a dodgy
capacitor or a dry solder joint? If it
wasn't the latter, the easiest approach
might be to simply blanket-replace the
ICs and transistors and check out the
SCRs, the diode and the relay.
It didn't come to that though, because I quickly spotted what was almost certainly the cause of the problem. There were five 10µF 16V tantalum capacitors on the PCB, two of
them in the timing circuits of the 555
timers. Four of these tantalums were
dark blue but the fifth had turned a
pale blue colour with a greenish band
across it.
Surely it wasn't going to be this ridiculously easy? I stuck a multimeter
across the capacitor and it registered a
dead short! I then traced the PCB tracks
from the capacitor and found that it
was across the output of an adjacent
LM340T-12 12V regulator.
This device is mounted on a small
heatsink in one corner of the board
and provides a regulated 12V rail to
the 555 timers and the quad amplifier
(and possibly also the relay).
I removed the capacitor and the
short across the regulator's output
disappeared. I then replaced it with
a 10µF 16V electrolytic that I had on
hand. Two other 10µF bypass tantalums on the PCB were also replaced
with electrolytics, while those in the
timing circuits of the 555 timers were
left in place.
In theory, the LM340T-12 should
have survived since these devices
are short-circuit proof. However, I
replaced it with an equivalent 7812
regulator as a precaution, along with
an adjacent electrolytic capacitor for
good measure.
At that stage, it was tempting to apply power to the circuit and check the
operation of the 555 timers. However,
not having a circuit diagram (no luck
with Google), I was afraid that this
might risk damaging something, especially if two of those external leads
shorted together.
The best bet would be to test the control board in the welder itself. I called
Paul and told him what I had found.
He was on my doorstep some 25 minutes later, collected the part and shot
back home to refit it.
I was cautiously hopeful that it
would now work and I didn't have
Celebrating 30 Years
to wait long to find out. An ecstatic
Paul was back on the phone an hour
later and he was floating somewhere
between his Mustang chassis and seventh heaven. “You're a genius”, he
exclaimed. “The welder is working
perfectly!”
There's nothing like a bit of flattery
to massage the ego but at the end of
the day, this was really a joint effort.
My brother diagnosed the faulty contactor, Paul fixed the contactor, the
service centre correctly diagnosed a
faulty control board and yours truly
fixed the control board.
So a part costing less than a dollar
was all that prevented this valuable
welder from working. It's since been
used to weld some fresh sheet metal
into that old Falcon station wagon
but it's the Mustang restoration that I
reckon he should be getting stuck into.
Editor’s note: older Tantalum capacitors seem to go short circuit more often than you might expect so it’s well
worth taking a good look at any such
capacitors first when repairing something made before the year 2000 or so.
Compaq CQ61 laptop repair and
refurbishment
B. P., of Dundathu, Qld, spent quite
some time refurbishing and repairing
an old laptop for his wife to use. In the
process, he discovered and fixed some
classic laptop hardware problems and
also ran into some time-consuming
software pitfalls...
Our daughter has just started university. After five years of intensive use,
her old laptop was well and truly the
worse for wear, so she bought herself
a new laptop and she gave us her old
one when she came home during her
mid-year break.
When I assessed the old laptop, it
was in a rather dilapidated condition.
The keyboard had one key cap missing on the numeric keypad and most
of the top row of keys (numbers and
symbols) no longer worked.
The top silver layer of the touchpad was also worn off in places, revealing the black base colour, the keyboard surround had a lot of the black
paint worn off it and the lid hinges
were loose. Although the laptop still
worked, it was certainly beat up.
I started the repair by removing the
old keyboard, by undoing the securing screws on the bottom of the laptop.
I ordered a new keyboard and while
waiting for it to arrive, decided to conMay 2018 67
tinue working on it by plugging in a
USB keyboard.
This allowed me to do a factory reset
so that we could start with a fresh copy
of Windows 7. After that was done, I
uninstalled all the trial software and
I installed some additional programs
that were needed. Then I partitioned
the 500GB hard drive into two separate partitions so that data could be
stored on the D:\ drive, separate from
the operating system on C:\.
I noticed some issues with the Compaq factory version of Windows 7 that
I wasn't happy with, so I decided to
do a fresh install of Windows 7 from
an OEM disc (ie, one purchased from
Microsoft) instead.
This all went well, but then I noticed that the webcam driver was not
installed in Device Manager; it was
showing up as an unknown device. I
tried to locate the correct driver for the
webcam on the internet, however, this
proved difficult. I did eventually find
the driver and installed it but when I
went to test it with Skype, Skype said
that it was already in use by another
program. It wasn’t, though.
I thought I would try uninstalling
the webcam driver in Device Manager and then scanning for new hardware. This did not work, as the webcam then showed up as an unknown
device again. I decided to do another
factory reset to try to get the webcam
working correctly but because I'd altered the hard drive partitioning, the
restore partition was no longer present.
I still had the set of three restore
discs that we'd made when the laptop was new, so I decided I would
just use those.
I set about restoring the laptop from
those discs, but when I got to disc
three, it had a read error, so the factory reset failed. This left me with a
blank hard drive. That meant using
the OEM disc to reinstall Windows
7 again. So I was back to square one,
with the webcam still showing up as
an unknown device.
I then realised that we had a related Compaq laptop model, a CQ42,
that uses the same HP-101 webcam.
I checked what driver the webcam
used and it was a standard Windows
driver. I'd recently installed Windows
7 on the CQ42 without any issues and
Windows had found and installed the
webcam, so I wondered why I was having so many problems with the CQ61's
webcam.
68
Silicon Chip
I then tried to tell Windows to use
the driver that it should be using, but
this idea didn't work out and I was
still in the position of not having the
webcam working. At this point, I decided to give the laptop a rest and do
something else.
I went to my shed to look for something and when I opened a box to
check inside it, I discovered another
Compaq CQ61 that I'd been given
some time ago that I'd forgotten about.
This CQ61 was a cheaper variant with
much lower specifications than the
one I was working on, so I would use
it for parts.
I started dismantling it with the intention of using the top case half to
replace the well-worn top case half
on the one I was fixing. The touchpad
still had its original silver colour and
the keyboard surround was still in asnew condition.
These new parts would make a huge
difference to the original one. Unfortunately, the keyboard on this laptop
was also faulty and unusable.
After unscrewing a multitude of
screws, I had the donor laptop fully
dismantled and I retrieved the parts
that I wanted to use for the refurbishment. Then I turned my attention to
the laptop I was working on and I dismantled it. I was now ready to reassemble it, using the better parts from
both laptops.
Before proceeding further, I decided
to give the interior a good clean because there was a considerable amount
of dust inside it from the many years
of heavy use. I used a small paintbrush with natural bristles in order
not to generate static electricity while
brushing the dust off the motherboard
components.
When I got to the heatsink, I removed the fan for cleaning and I noticed that there was a thick layer of
dust on the inside of the heatsink's
fins, where the fan had been blowing air through it.
This dust was removed and
the fan was then thoroughly
cleaned, before being refitted.
This is a very common problem with older laptops and
often causes them to overheat and either lose performance or become unstable.
It was fortunate that I had
stumbled across the other
laptop and as a result, decided to take apart the one I was
Celebrating 30 Years
working on because if I hadn’t done
so and cleaned it out, chances are I
would have run into some of these
problems later.
At this point, I decided to also
transfer the lid assembly from the donor laptop (including the display and
webcam) because it was in slightly better condition than the original lid. By
this time, I was also suspecting that
the original webcam may be faulty,
so this was the perfect opportunity to
test this theory.
With the laptop partly assembled,
I propped the lid against a box, so
that I could connect it up and test the
screen and the webcam. Once booted, I
checked Device Manager and the webcam was now installed. I loaded Skype
and tested it and it now worked, indicating that the original webcam had
been faulty all along.
I then noticed that there was a problem with the replacement screen, as
it had several dead pixels in the lower right-hand section of the screen.
This blemish was not that bad and it
would not make a huge difference to
the laptop, but seeing that the original screen was in better order, I would
swap them over.
I dismantled the lid and fitted the
original screen to it and then I reassembled it and continued with reassembling the laptop. It's very important to
take particular note of which screws
go where when reassembling a laptop.
There are around five different
length screws in some laptops and
each screw must be used in the correct location to prevent damage (when
putting a long screw in where a short
one should go).
siliconchip.com.au
After a bit more work, the laptop
was reassembled and back in working
order again, except for the keyboard. I
was still waiting for the replacement.
In the meantime, my wife could just
use the laptop with the USB keyboard.
Eventually, the replacement keyboard
arrived and I fitted it; the laptop was
then fully refurbished and it has a new
lease on life.
This laptop is now around seven
years old and it would be classified as
being quite outdated. But it's still quite
suitable for light duty work, such as
web browsing, emailing, letter writing
and other general duties.
For a bit of work and less than $20
for the replacement keyboard, it's as
good as new. That’s a lot cheaper than
buying a new laptop, even a basic
one, and it’s still perfectly adequate
for most jobs and uses less electricity
than a desktop computer.
Having the donor laptop on hand
certainly saved me quite a bit on replacement parts and resulted in a more
cosmetically appealing end result with
the new top case shell to replacing the
well-worn old one.
This was my first major laptop repair and I was surprised that it was
nowhere near a difficult as I had imagined it would be. It's simply a matter
of proceeding with caution and paying
close attention to details.
There are also plenty of videos on
YouTube which go into considerable
detail about laptop repairs but I managed to do the refurbishment without
referring to any.
MR16 LED downlight repair
D. M., of Toorak, Vic, had a 12V
MR16 LED downlight fail far short of
its claimed 20,000+ hour lifespan. It
would have been cheaper to just buy
a new one but he wanted to know
what had gone wrong so set to taking
it apart…
I wanted to know what had failed
inside the MR16 LED lamp as I find
the claims for LED downlight life expectancy, typically of 20,000 to 50,000
hours, quite unlikely.
At eight hours per day, that would
amount to a service life of 7-17 years.
Although LED downlights have not
been available for 17 years, in my experience, most such lamps don’t even
last seven years.
My particular light was a Muller-Licht (house brand) Reflektor rated at 320
lumens and 5W. I carefully examined
siliconchip.com.au
the light to determine how it might be
disassembled without damage.
I found I could gently pry the top retaining ring off the body with a knife
which also caused the release of the
light diffuser, revealing the LEDs and
their heatsink.
Two Phillips-head screws could
then be removed from the heatsink,
allowing the separation of the top and
base portions of the light assembly (see
photos at right).
LED lights typically contain a driver which delivers a constant current
to the LEDs. I quickly determined
that it was the driver that had failed
as when power was applied directly
to the LEDs, they lit up. I decided to
obtain and install a suitable replacement driver.
I found one online that was rated at
the same current as the LEDs, 650mA
and only cost about $2.50. This driver has pins attached with the correct
size and spacing to plug into an MR16
socket.
So these could be used to replace the
existing pins on the lamp body, or alternatively, they could be desoldered
from the driver if necessary for other
applications.
The driver utilises a PT4115 chip.
The website where I bought it has details of the circuit; see siliconchip.
com.au/link/aajr
I removed the old driver from the
LED body and then the old MR16 pins.
Be careful removing the old pins as it
is easy to break the plastic body. In this
lamp, the pins were hollow.
You may be able to cut them and
then drill through to remove them
(with a very small diameter drill). I
tried twisting them with pliers which
ended up cracking the body of the case.
Alternatively, it might be easier to
leave the pins in place and desolder
the old driver, then solder them to
the new driver board. The driver is
housed in the otherwise empty “well”
in the base of the lamp, just above the
pins.
Having soldered the new driver in
place, I glued the ends to ensure the
pins would not move. Make sure any
conductive parts that might contact
each other to cause a short circuit are
appropriately insulated. The lamp
worked fine after that and so I put it
back into service.
This particular lamp replaced an existing halogen downlight and is driven
by an old-style iron core transformer
Celebrating 30 Years
Prying off the cover revealed the
retaining ring, diffuser, LEDs and
their heatsinks.
After removing two screws the LED
enclosure could be separated showing
two leads attached to a driver PCB.
The LED driver shown above is the
replacement one and is mounted
differently to the old driver.
Left: the replacement MR16 driver.
Right: the failed MR16 driver.
supplying 12VAC. These transformers are not as efficient as more modern
electronic ones but they do work with
LED replacement lamps.
Some modern electronic “transformers” designed for use with halogen lamps will not work with LED
replacements as they do not draw
enough current (or perhaps it’s because
they’re a non-resistive load).
There are many different designs of
LED downlight. Some such as the one
described here might be relatively easy
to disassemble, others might be more
difficult or impossible. Note that type
of repair is not very economical, especially if you include your time in the
calculation but I found the job to be
both fun and educational.
SC
May 2018 69
Look after your Lithiums!
By Nicholas Vinen
2x 12V
Battery
Balancer
Two 12V batteries are often significantly cheaper than one equivalent
24V battery but you need to be careful connecting batteries in series as
their voltages and state-of-charge may not be identical. The difference
in voltage can increase over time, leading to battery damage from overcharging and/or under-charging. This compact, low-cost device keeps
them balanced so that they last a long time.
O
cause they tolerate overcharging much less than a similar
n page 28 of this issue, we describe a high-perforlead-acid battery would.
mance Uninterruptible Power Supply (UPS) you
This design incorporates a low-voltage cut-out which
can build yourself, that uses two 12V LiFePO4 batprevents the batteries being discharged too far if it is unteries wired in series to form a 24V battery.
able to keep them balanced and its very low quiescent
This was a much cheaper solution than buying a 24V batcurrent of under 0.02mA means it will have virtually no
tery with equivalent performance, even taking into account
effect on battery life.
the $100 or so we paid for a commercial battery balancer.
It also incorporates a LED to show when it is monitoring
You can build this balancer for a lot less than that and
the battery voltages and two more LEDs to show when one
it will do a similar job.
or the other is being discharged or shunted.
Our version can’t handle quite as much
By default, the low-voltage cut-out is set up so that the
current, because it lacks the large
batteries are only balanced when they are being charged,
heatsink.
however, there are definitely situations where you might
But you can
want the batteries to be balanced during discharge, too.
easily parallel
In that case, you just need to
several of our
change a resistor or two in
balancers if you
order to adjust the cut-out
need a higher curthreshold so it is near the
rent capacity and
minimum battery voltthe cost would still
age. In this case, the cutbe quite reasonable.
out will still act to proIt can be used with prettect the batteries but will
ty much any battery chemallow
balancing during
istry, as long as the battery
charging and discharge,
voltages will stay within the
right down to that lower
range of 5-16V.
threshold.
Balancing is most critical
Shown
rather
significantly
oversize
for
clarity
(the
PCB
It’s a compact unit at
with lithium-based rechargemeasures only 31.5 x 34.5mm) – see the $2 coin for reference – just 31.5 x 34.5 x 13mm,
able batteries, though, beall components mount on this single board.
70
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Celebrating 30 Years
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Fig.1: the circuit for the Battery Balancer, shows the balancing section at top and low-voltage cut-out at bottom, based
around dual micropower op amps IC1 and IC2 respectively. IC1 drives dual Mosfets Q1 & Q2 to perform balancing
while necessary; IC2 drives the indicator LEDs and disables IC1 using Mosfet Q3 when the battery voltage is low.
so you can tuck it away inside just about any device. And
if the 300mA balancing current is not sufficient for your
purposes, all you need to do is wire two or more units in
parallel and they will operate in concert to keep the batteries balanced.
Balancing operation
There are two sections to the circuit; the balancer and the
low-battery cut-out. The entire circuit is shown in Fig.1,
with the balancing circuitry in the top half and the lowvoltage cut-out below.
Starting with the balancing section, schottky diodes D1
and D2 are connected in series with the two batteries so
that no damage should occur if they are wired up incorrectly. These diodes are then connected to Mosfets Q1a
and Q2b at the right-hand side of the circuit diagram, via
a pair of 27Ω 3W resistors.
These Mosfets are normally switched off and no current
can flow through them. If the voltage across one battery rises by more than 100mV above the other, the Mosfet across
that battery is switched on.
siliconchip.com.au
If the battery is being charged, this has the effect of shunting some of the charge current around that battery so that it
receives a lower charging current than the other, decreasing the voltage differential over time, as the battery with
the lower voltage is then receiving more charging current.
If the unit is operating while the battery is not being
charged, the effect is to slightly discharge the battery with
the higher voltage until they are closer in voltage.
It’s a linear circuit so the shunt current is proportional to
the difference in voltage. As the imbalance rises, so does the
shunt current until the limit of around 300mA is reached.
This is to prevent the Mosfet and resistor from overheating.
Detecting a voltage difference
A resistive divider comprising two 10MΩ resistors and
200kΩ trimpot VR1 is connected across the battery, before
diodes D1 and D2 so that their forward voltage does not
affect the calculation of the difference in voltages.
VR1 is adjusted so that the voltage at its wiper is exactly half that of the total battery. This half-battery voltage is
buffered by voltage follower op amp IC1a.
Celebrating 30 Years
May 2018 71
ing current, all the dissipation would
be in this resistor and none in the Mosfet, meaning the maximum current
• Minimum battery voltage: 5V
would be 200mA [14V ÷ 68Ω].
• Nominal battery voltage: 12-13V
We realised we could increase this
• Maximum battery voltage (fully charged): 16V
by 50% by splitting the dissipation be• Battery voltage difference for balancing to start: approximately 100mV
tween the Mosfet and its series resis• Battery voltage difference for maximum balancing current: approximately 130mV
tor. The resistor has a 3W rating while
• Maximum balancing current: approximately 300mA (multiple units can be paralleled)
the Mosfet has a 2W rating, giving the
• Maximum balancing power: approximately 4.5W (multiple units can be paralleled)
possibility of a total of just under 5W.
• Maximum recommended charging current: 10A per unit
With a battery voltage of 29V and a
• Quiescent current: < 20A
balancing current of 300mA, dissipa• Low-voltage cut-out threshold: 27V (can be changed)
tion is around 2.7W in the resistor and
• Low-voltage cut-out hysteresis: 0.25V
1.7W in the Mosfet.
We achieve this dissipation sharing
This op amp has a very high input resistance of around by preventing the Mosfet from turning on fully and using
40GΩ, resulting in a low input bias current of approxi- a lower value limiting resistor. This is the purpose of Q1b
mately 250pA, so the high values of these resistors (cho- and the three resistors between TP2 and TP3.
These resistors bias the gate of Q1b at a voltage that’s
sen to minimise the quiescent current) will not result in a
initially about halfway between the negative and positive
large error voltage.
The other half of the dual op amp, IC1b, compares the terminals of the upper battery (ie, at a voltage between that
voltage at the junction of the two batteries (from pin 2 of of pins 1 & 2 of CON1). However, as the balancing current
CON1) to the output voltage from IC1a. If the upper bat- for the upper battery increases, the voltage at the junction
tery has a higher voltage than the lower battery then the of the 27Ω resistor and Q1a drops and therefore so does
half-battery voltage will be higher than the voltage at pin 2 Q1b’s gate voltage.
Q1b is a P-channel Mosfet and so it switches on when
of CON1. That means that the voltage at non-inverting input pin 5 will be higher than at the inverting input, pin 6. its gate is a few volts below its source terminal. The source
As a result, IC1b’s output will swing positive. The ra- terminal is connected to the gate of Q1a, which is about 2V
tio of the 390kΩ feedback resistor to the 10kΩ resistor that above pin 2 of CON1 when Q1a is in conduction.
So as the current through Q1a builds and Q1b’s gate voltgoes to the battery junction (ie, 39:1) means that the output will increase by 40mV for each 1mV difference in bat- age drops, eventually Q1b begins to conduct, pulling the
gate of Q1a negative and cutting it off. This forms a negatery voltages.
Once the voltage at output pin 7 has risen by a couple tive feedback path and due to the gate capacitances, the
of volts, N-channel Mosfet Q1a will switch on as its gate circuit stabilises at a particular current level.
With 300mA through the 27Ω resistor, the voltage across
is being driven above its source, which connects to pin 2
it will be 8.1V [0.3A x 27Ω] and this translates to a gateof CON1 via a low-value shunt resistor (47mΩ).
So current will flow from the positive terminal of the up- source voltage for Q1b of around -2V, ie, just enough for it
per battery, through diode D1, the 27Ω 3W resistor, Mosfet to conduct current. The 4.7kΩ resistor between output pin
Q1a and then the 47mΩ resistor to the negative terminal 7 of IC1b and the gate of Q1a prevents Q1b from “fighting”
the output of the op amp too much.
of the upper battery.
Note that 8.1V is slightly more than half the typical voltOnce this current starts to flow, it will also develop a
voltage across the 47mΩ resistor which will increase the age of one 12V battery and this is why the resistor dissipates
voltage at pin 6 of IC1b, providing negative feedback. This slightly more than the Mosfet, in line with their ratings.
feedback is around 1mV/20mA, due to the shunt value.
This prevents Q1a from switching fully on. Rather, its Balancing the other battery
The other half of the balancing is a mirror-image; for balgate voltage will increase until the current through the
47mΩ resistor cancels out the difference in the two voltages. ancing the lower battery, Mosfet Q2b is a P-channel type and
Hence, the maximum shunt current of 300mA will thus switches on when its gate is driven below its source.
be achieved with an imbalance around 130mV (100mV + As with Q1a, its source is connected to the junction of the
two batteries via the 47mΩ resistor.
300mA x 0.047Ω ÷ 2).
When the lower battery voltage is higher than the upThe 10MΩ resistor between pin 3 of IC1a and pin 2 of
CON1 serves mainly to prevent the balancer from operating per battery, output pin 7 of IC1b goes negative, switching
should the junction of the batteries become disconnected Q2b on.
And the same current-limiting circuitry is present but
from CON1. It also makes setting the unit up and adjusting VR1 easier. It has a negligible effect on the voltage at this time, Q2a is an N-channel Mosfet, so that as current
pin 3 since there’s normally such a small voltage across it. builds through the lower 27Ω resistor and the voltage at
the junction of it and Q2b rises, Q2a switches on and limCurrent limiting
its the current to a similar 300mA value, with roughly the
Had we specified 68Ω resistors in series with Q1a and same dissipation split between the two components.
A 10nF capacitor across IC1b’s 390kΩ feedback resistor
Q2b (rather than 27Ω), there would be no need for additional
current limiting circuitry since the resistors would naturally slows down its action so that it doesn’t react to any noise
limit the balancing current within their dissipation ratings. or EMI which may be present at the battery terminals (eg,
However, this would mean that at the maximum balanc- due to a switchmode load).
Features & specifications
72
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Fig.2: use the PCB overlay diagram at
left and matching photo at right as a
guide to assembling the PCB. Only one
SMD component (a 10MΩ resistor)is
soldered to the bottom, the rest go on
the top as shown. The main aspects to
pay attention to during constructon are
that the semiconductors are correctly
orientated and that you fit the resistors
and capacitors in the correct locations.
It also prevents the circuit from oscillating due to the
negative feedback and the action of the current limiters.
Under-voltage cut-out
Commercial battery balancers tend to only operate when
the battery voltage is near maximum, as this is when they
are being charged. That avoids the possibility of the balancer discharging the batteries when they are under load.
However, we’re not convinced this is a good idea. It’s
possible to have a sufficient initial imbalance that one battery could be over-charged before the balancer even activates. And full-time balancing also has the advantage that
it can start re-balancing the cells as soon as an imbalance
occurs, which also avoids over-discharge and gives it more
time for re-balancing.
There is one other advantage to having a higher undervoltage lockout threshold and that is that it will prevent the
balancer being triggered due to differing internal resistance
of the batteries when under heavy load. This could create
a voltage difference between the batteries even when they
are at an equal state of charge.
If you want the balancer to be active even when the bat-
teries are not being charged, you still need the under-voltage lockout circuitry to prevent the balancer from over-discharging either battery. But in that case, you would change
its threshold to be close to the fully-discharged voltage of
your combined battery.
For a pair of lithium-based 12V rechargeable batteries,
this would normally be around 20V total.
That’s to protect against the case where one battery has
a failure (eg, shorted cell) which causes its voltage to drop
dramatically. The under-voltage detection circuitry will
then prevent the balancer from over-discharging the other
battery in response, and potentially destroying it. See the
section below on how to change the cut-out threshold if
you want to take this approach.
The increased battery drain of the low-voltage cut-out
section is only about 10µA. As a bonus, it drives the three
LEDs to indicate when the balancer is operating and which
battery is being shunted.
This is implemented using IC2a, another LT1495 op amp.
Its positive supply is the same as for IC1a but its negative
supply is connected directly to the negative terminal of the
bottom battery, allowing it to sense the total battery voltage
Many years ago, long before the days of smartphones and computers, even before the days
of television, it was considered a “right of passage” for dads to sit down with the sons (or
daughters) and help them as they built their own radio receiver. FM? Not on your life no such thing! DAB+? Hadn’t been invented yet! No, it was all good, old reliable AM Radio.
And they could listen to stations hundreds, perhaps thousands of miles away!
The beauty of it all was that they were building something that actually worked, something
they’d be proud to show their friends, to their school teachers, to their grandparents!
Enjoy those days once again as they build the SILICON CHIP Super-7 AM Radio
See the articles in
November & December 2017
SILICON CHIP
(www.siliconchip.com.au
/series/321)
SUPERB
SCHOOL
PROJEC
T!
•
•
•
•
•
•
•
Covers the entire AM radio broadcast band.
Has on-board speaker ... or use with headphones.
SAFE! –power from on-board battery or mains plug-pack
Everything is built on a single, glossy black PCB.
All components readily available from normal parts suppliers
Full instructions in the articles including alignment.
See-through case available to really finish it off!
IT LOOKS SO GOOD THEIR FRIENDS WON’T BELIEVE THEY BUILT IT!
siliconchip.com.au
Celebrating 30 Years
May 2018 73
(ie, between pins 1 and 3 of CON1) more easily.
This is done using a string of three resistors (390kΩ,
6.8MΩ and 1MΩ) connected across the batteries. These
form a divider with a ratio of 8.19 [(390kΩ + 6.8MΩ) ÷
1MΩ + 1]. The divided voltage from the battery is applied
to inverting input pin 2 of IC2a.
A 3.3V reference voltage is applied to the non-inverting input at pin 3. This is provided by micropower shunt
reference REF1, which is supplied with around 2A via
a 10MΩ resistor. The voltage at pin 2 of IC2a is therefore
above the voltage at pin 3 when the battery voltage is above
27V [3.3V x 8.19].
When this is the case, output pin 1 of IC2a is driven low,
pulling the gate of N-channel Mosfet Q3 to the same voltage as the negative terminal of the bottom battery. As the
source of Q3 is connected to the junction of the two batteries, Q3 is off and so does not interfere with the operation of the balancer.
However, should the total battery voltage drop below
27V, the output of IC2a goes high, switching on Q3 and
effectively shorting input pin 3 of IC1a to the junction of
the two batteries. This means that the voltages at pins 5
and 6 of IC1b will be equal (with no current flow through
the 47mΩ resistor, as will quickly be the case), therefore
preventing any balancing from occurring.
When the output of IC2a goes high, this also causes a
slight increase in the voltage at its pin 3 input, due to the
10MΩ feedback resistor. This provides around 1% or 250mV
hysteresis, preventing the unit from toggling on and off
rapidly. In other words, the battery voltage must increase
to 27.25V to switch the balancer back on.
When the output of IC2a is low and the balancer is active, IC2a also sinks around 0.25mA through LED1 and its
100kΩ series resistor, lighting it up and indicating the balancer is operating.
And when one or the other battery is being shunted, IC2b
amplifies the voltage across the 47mΩ shunt by a factor
of 2200 times. So if there is at least 20mA being shunted,
that results in around 1mV across the 47mΩ resistor which
translates to 2.2V at output pin 7 of IC2b, enough to light
up either LED2 or LED3. LED2 is lit if it’s the upper battery
being shunted and LED3 if it’s the lower battery.
dissipate up to around 4.5W. If you’re using a 3A charger,
that means it can handle a ~10% imbalance in charge between batteries (which would be unusually high).
However, with a 10A charger, it will only handle a ~3%
imbalance, with a 20A charger ~1.5% etc. A greater imbalance could potentially lead to over-charging as the balancer
can’t “keep up”. So if your charger can deliver more than
5A, you may want to consider paralleling multiple balancers and we would strongly recommend it for a charger capable of 10A or more.
When properly adjusted, the balancers will share the
load. Realistically, one of them will start balancing first
but if it’s unable to keep the imbalance voltage low, the
others will quickly kick in and shunt additional current.
Since the only external connections are via 3-way pin
header CON1, you could simply stack the boards by running thick (1mm) tinned copper wire through these pads
and soldering them to each board in turn. You can then
solder the battery wires to these wires.
Changing the cut-out voltage
Construction
To change the cut-out voltage, simply change the values
of the 6.8MΩ and 390kΩ resistors using the following procedure. First, take the desired cut-out voltage and divide
by 3.3V. Say you want to make it 24V. 24V ÷ 3.3V = 7.27.
Then subtract one. This is the desired total value, in megohms. So in this case, 6.27MΩ.
This can be approximated a number of ways using standard values. For example, 3.3MΩ + 3.0MΩ = 6.3MΩ which
is very close. So use these values in place of the 6.8MΩ
and 390kΩ resistors.
Keep in mind there will still be around 1% hysteresis,
so the switch-on voltage will be about 24.24V.
Two more examples would be a 22V cut-out, which would
require 5.67MΩ total; you could use 5.6MΩ + 68kΩ. Or for
a 20V cut-out, you would need 5.06MΩ which could be
formed using 4.7MΩ + 360kΩ.
The 12V Battery Balancer is built on a small doublesided PCB measuring 31.5 x 34.5mm and uses mostly surface-mounted parts. These are all relatively large and easy
to solder. Refer to the overlay diagram, Fig.2, to see where
each component goes on the board. Some of them (the ICs,
Mosfets, diodes and trimpot) are polarised so be sure to fit
them with the orientation shown.
There are two small SOT-23 package devices, Mosfet Q3
and voltage reference REF1. Fit these first. They look almost
identical so don’t get them mixed up; only the tiny coded
markings on the top of each set them apart.
Tack solder the central pin to the pad in each case then
check that the other two pins are centred on their pads and
that all pins are in contact with the PCB surface. If not, reheat the initial solder joint and nudge the part into place.
Then solder the two remaining pins and add a little extra
solder to the first pin (or a bit of flux paste and heat it) to
ensure the fillet is good.
Next, solder IC1, IC2, Q1 and Q2. They are all in eight-
Paralleling multiple boards
As stated, one board can handle around 300mA and will
74
Silicon Chip
Sourcing the parts
The PCB is available from the SILICON CHIP Online Shop
– simply search for the board code 14106181.
All the other parts are available from Digi-Key. While
they are based overseas (in the USA), you can pay using
Australian dollars and they offer free courier delivery for
orders of $60 or more. You can find the semiconductors on
their website by searching for their part number and then
narrowing down the list (eg, ignoring listings which are
out of stock or only sold in large quantities).
For the other, more generic parts like SMD resistors, you
can find them by searching for (for example) “SMD resistor 1206 4.7k 1%” and then sorting the result by price. The
cheapest part which matches the specifications should
do the job just fine. But be careful because sometimes the
search results include parts with different properties than
you are expecting. You will need to skip over those.
Mouser, another large electronics retailer based in North
America, will almost certainly have all the required parts
too. And if you don’t want to order from overseas, chances
are that you can get most of them from element14 (formerly
Farnell; http://au.element14.com).
Celebrating 30 Years
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pin packages and must be orientated correctly. Identifying
pin 1 can be a bit tricky. For IC1 and IC2, you have to find
the chamfered edge which is quite subtle. Pin 1 is on that
side. Q1 and Q2 have pin 1 marked by a much more clear
divot in the corner of the package. But you can also orientate IC1 and IC2 by matching the position of the markings
up to our photo.
In each case, make sure the device is positioned correctly and tack solder one pin, then as before, check the
locations of the other pads are correct and solder them
before refreshing the first joint. If you accidentally bridge
two pins with solder, use a little flux paste and some solder wick to clean it up.
The only remaining SMD parts which are polarised are
diodes D1 and D2. Fit these now, ensuring the striped end
goes towards the top edge of the PCB, as shown in Fig.2
and marked with “K” on the PCB. Then solder the two
3W resistors in place. Follow with the remaining SMD ceramic capacitors and chip resistors as shown in the overlay diagram.
For the two-pin devices, make sure that you apply the
soldering iron long enough so that the solder adheres to the
PCB and the component. Adding a little flux paste to the
PCB pads before positioning the part will make this easier.
There is a single component on the underside of the
board, a 10MΩ resistor positioned between CON1 and VR1.
Solder it in place but use a minimal amount of solder, so
that you don’t plug the through-holes underneath. You can
add more solder later after CON1 and VR1 are in place.
All that’s left then is to solder trimpot VR1 with the adjustment screw orientated as shown, and a pin header for
CON1. We used a normal pin header but a polarised header
would be a good idea if you’re going to use a plug to make
connection to the batteries so that it can’t be accidentally
reversed. If it is reversed, D1 & D2 should prevent damage
but the balancer won’t work!
Or you can solder the battery wires directly to these
three pads. They only need to be rated to handle 300mA
per board; medium duty hookup wire should be more than
sufficient, even if paralleling multiple boards.
Testing & set-up
Connect your batteries in series, then connect the negative-most terminal directly to the negative terminal on
CON1. Do not connect the junction of the two batteries to
the Balancer just yet.
Ensure that the total battery voltage is well above the
threshold and that they are reasonably close to being balanced. You can ensure they are balanced by charging both
independently and then connecting them in parallel via
a low-value, high-power resistor (eg, 1Ω 5W) and leaving
them for a few hours. The voltage across the resistor should
drop to a very low level once their voltages equalise.
Now connect the most positive terminal to the positive
pin of CON1 via a 1kΩ resistor and check that LED1 lights
up. LEDs 2 & 3 should remain off. Measure the voltage
across the 1kΩ resistor. It should be under 20mV. If it’s under 5mV or over 20mV, disconnect the battery and check
for errors in your PCB assembly or battery wiring.
Assuming the voltage is within the specified range, remove or short out the 1kΩ test resistor and then connect
the junction of the two batteries to pin 2 of CON1. LED2
and LED3 may light up. If so, rotate the adjustment screw
siliconchip.com.au
Parts list –
2 x 12V Battery Balancer
1 double-sided PCB, coded 14106181, 31.5 x 34.5mm
3 3-way right-angle or vertical pin header (CON1)
Semiconductors
2 LT1495CS8 dual micropower op amps, SOIC-8 (IC1,IC2)
1 ZXRE330ASA-7 micropower 3.3V reference, SOT-23
(REF1)
2 DMC3021LSDQ dual N-channel/P-channel power Mosfets,
SOIC-8 (Q1,Q2)
1 2N7000 N-channel signal Mosfet, SOT-23 (Q3)
1 green LED, SMD 3216/1206 (LED1)
1 red LED, SMD 3216/1206 (LED2)
1 blue LED, SMD 3216/1206 (LED3)
2 S1G 1A schottky diodes or similar, DO-214AC (D1,D2)
Capacitors (all SMD 3216/1206 X7R ceramic)
2 100nF 50V (measure value before installing!)
1 10nF 50V (measure value before installing!)
Resistors (all SMD 3216/1206 1%)
For tips and tricks
6 10MΩ (Code 1005)
on soldering SMD
1 6.8MΩ (Code 6804)
components, refer to the
2 5.6MΩ (Code 5604)
SILICON CHIP articles
“How to Solder
1 2.2MΩ (Code 2204)
Surface Mount Devices”
1 1MΩ (Code 1004)
in March 2008
2 390kΩ (Code 3903)
www.siliconchip.com.au/
2 100kΩ (Code 1003)
Article/1767
2 10kΩ (Code 1002)
and
2 4.7kΩ (Code 4701)
October 2009
1 1kΩ (Code 1001)
www.siliconchip.com.au/
2 27Ω 3W (SMD 6331/2512)
Article/1590
[eg, TE Connectivity 352227RFT]
1 47mΩ [eg, Panasonic ERJ-L08KF47MV]
1 200kΩ 25-turn vertical trimpot (VR1)
in VR1 until they are both off.
Now check that there is no balance current flowing by
measuring the voltage between TP1 and TP2, and between
TP3 and TP4. In each case, the reading should be zero. If
you get a non-zero reading between TP1 and TP2, current
is flowing through Q1a. And if there’s a voltage between
TP3 and TP4, current is flowing through Q2b.
Since you started out with balanced voltages, this should
not be the case, so adjust VR1 further until you get a zero
reading across both pairs of test points. Ideally, VR1 should
be adjusted to halfway between the point where the voltage starts to rise between one pair of test points, and the
point at which the voltage rises across the other pair of
test points. This ensures the balancing will be, for lack of
a better word, balanced!
The maximum reading you should get between one pair
of test points should be 8.8V. Any more than that and you
risk the resistor dissipation rating being exceeded. In this
case, disconnect the batteries and change the 10MΩ resistor right next to VR1 on the top side of the board with a
slightly lower value (eg, 9.1MΩ or 8.2MΩ) to reduce the
current limit.
If that doesn’t fix it then it’s likely that the current limiting circuitry is not working so you should check for soldering problems or faulty components.
SC
Celebrating 30 Years
May 2018 75
CIRCUIT NOTEBOOK
Interesting circuit ideas which we have checked but not built and tested. Contributions will be
paid for at standard rates. All submissions should include full name, address & phone number.
20V, 2.5A Adjustable Power Supply with current limiting
This adjustable power supply is
based on the venerable LM723C regulator IC and a handful of low-cost
components. It provides an adjustable
output voltage of 0-20V and adjustable
current limit of 0-2.5A.
When the current limit is reached,
the output voltage drops to keep the
current constant and LED2 lights to
indicate that it is in current limiting
mode.
It also provides voltage and current
metering (using analog meters) and
multiple supplies can be built and connected in series or parallel, to obtain
higher voltages or currents.
Normally, an LM723-based regulator cannot have an output voltage
lower than 2V but because this design uses the LM723C to drive a separate NPN pass transistor and due to
the clever feedback arrangement, the
output voltage can be adjusted all the
way down to 0V. It will also drop to
0V if short-circuited, due to the builtin adjustable current limiter.
Mains power is switched by DPST
switch S1 and passes through fuse F1
to be applied to the primary of 230V
to 24V transformer T1 (60VA). Bridge
rectifier BR1 and the 3300µF capacitor provide a ~30V DC unregulated
supply rail.
A 10nF capacitor across T1's secondary reduces switching interference
when the diodes in BR1 go into and
out of conduction.
The main regulating transistor is
Q4, a 2N3055 configured as an emitterfollower. Current flows from the main
filter capacitor to its collector via a 1W
7W resistor and 1N5401 3A diode D1,
which are used to provide the current
limiting feature, as described below.
The current from Q4's emitter flows
through two parallel 0.1W 2W resistors to the output.
These resistors effectively form a
0.05W 4W resistor which is used as
a shunt to measure the current flow.
The voltage across these resistors is
50mV/A and this is translated into a
current by trimpot VR3 and fed to the
ammeter movement.
Say VR3 is adjusted for a resistance of 125W. This will feed 1mA
(2.5 × 50mV ÷ 125W) to the meter at
2.5A, giving a full-scale reading on a
1mA meter.
If the meter used reads 0-5A, then
you would adjust VR3 for 250W instead, so that it would reach half-scale
at 2.5A.
Similarly, the voltmeter is connected
across the output via trimpot VR4. For
a 0-20V 1mA meter, you need to feed
it 1mA at 20V output, so you would
adjust VR4 for 20kW. Higher resistance
settings are needed for meters with
a higher voltage range, for example,
30kW for a 0-30V type.
The output voltage is controlled by
IC1, using its pin 5 (non-inverting)
and pin 4 (inverting) inputs and pin
11, which is the collector of its internal output transistor.
The emitter of that transistor is internally connected to the cathode of a
6.2V zener diode, which is supplied
with current via the 220kW resistor to
pin 10 and its anode is connected to
ground via pin 9.
When the voltage at pin 5 is higher
than the voltage at pin 6, the IC sinks
current from the base of Q3 via the
4.7kW resistor, into pin 11.
This causes Q3 to conduct, delivering current to the base of Q4, thus
raising the output voltage. When Q3
switches off, the 47W resistor between
Q4's base and emitter causes it to
switch off as well, lowering the output voltage.
A fraction of the output voltage is
fed back to the inverting input at pin
4, via a fixed resistive divider comprising 62kW and 22kW resistors. The
bottom end of this divider goes to the
wiper of potentiometer VR2 rather
than ground.
Pin 6 of IC1 provides a nominal
7.15V reference. This is used to bias
both the inverting and non-inverting
input pins. The non-inverting pin bias
is fixed at around 5.28V due to another
62kW/22kW divider, from the reference
output to pin 5 and then to ground.
The voltage at the wiper of VR2 can
be varied from the 7.15V reference,
down to 0V.
Consider the case when the wiper of
VR2 is at the 7.15V end, ie, fully anticlockwise. We know that the non-inverting input is held at 5.28V. To get
the same 5.28V at the inverting input
(pin 4), the output would need to be
0V. As VR2 is rotated clockwise and
its wiper voltage decreases, the output
voltage must increase in order to keep
the two input voltages equal.
Hence, VR2 can be used to vary the
output voltage all the way down to
0V and up to 20.16V (5.28V × [62kW
+ 22kW] ÷ 22kW).
The 470pF capacitor between pins
4 and 13 reduces the bandwidth of the
feedback loop, by feeding back fast
changes in the output voltage directly
to the inverting input pin.
Since pin 13 is internally connected
to the base drive for the output stage,
8.2V zener diode ZD1 limits the drive
to that output stage, preventing saturation and keeping the IC operating
in linear mode. Stability is also im-
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Celebrating 30 Years
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proved by the 1.8kW resistor across
the output terminals, which provides
a minimum load.
The current limit is set using potentiometer VR1 and controlled by PNP
transistor Q2. With no current drawn
from the output, the voltage across
VR1 and its 220W and 100W padder
resistors will be around 0.7V, ie, the
forward voltage of diode D1.
This voltage increases at around
1V/A, due to the 1W resistor in series
with D2. VR1 controls what fraction of
this voltage is applied to the base of Q2.
When this fraction exceeds around
0.6V, Q2 switches on and supplies
current to pin 11 of IC1, the same pin
that is driving output transistors Q3
and Q4. Since pin 11 can only sink
around 2mA, due to the 4.7kW series
resistor, this has the effect of forcing
the output transistors to switch off,
reducing the output voltage.
This, in turn, lowers the output current, which reduces the base drive to
Q3 and thus the output voltage should
stabilise at a level where the output
current flow is at a value as determined
by the rotation of VR1.
The padder resistors are chosen to
give a near-zero output current when
VR1 is fully anti-clockwise and the
full 2.5A that the supply is capable of
siliconchip.com.au
when it is fully clockwise.
The same voltage which drives the
base of Q2 is also applied to the base
of PNP transistor Q1 via a 47W resistor. Thus, Q1 will switch on when Q2
does, indicating that current limiting
is in effect by lighting LED2.
Construction
I have produced a single-sided PCB
design for this power supply; a PDF
pattern can be downloaded from the
Silicon Chip website.
The following components are
mounted off-board: T1, VR1, VR2,
LED1, LED2, Q4 and the voltmeter and
ammeter. A wiring diagram is supplied
with the PCB pattern, to show how
these are connected.
Q4, the main transistor, is in a TO-3
package and should be mounted on a
substantial heatsink as it can dissipate
up to 75W or so. Q3, its driver transistor, should have a small flag heatsink fitted.
While this circuit is based on an
old design, the parts are still available and the LM723C and 2N3055 are
still in production. The other parts are
either generic or have been replaced
with more modern versions.
Gianni Pallotti,
North Rocks, NSW. ($75)
Celebrating 30 Years
Most of the components on the prototype
PCB have been mounted vertically to keep
it compact. Note the heatsink on Q3.
May 2018 77
Personal Speedometer for jogging
I built this device to keep track of
how far and how fast I go when jogging.
I know there are plenty of smartphone
apps to track this type of activity but
since jogging is a bit of an “escape”
for me, I don’t like to carry my phone
while I’m doing it.
Also, even if I did bring my phone,
I wouldn't be able to choose between
the dozens of available apps. Most of
these apps seem to also require an internet connection while you’re jogging, making it a bit prohibitive to use.
This unit also costs a lot less to build
than buying a typical smartphone, so
I don't have to worry about breaking
or losing it.
It uses a GPS receiver to track your
jogging and has an OLED display to
show the results. I purchased the major
parts from AliExpress for around $20.
Because your route might have areas
where you backtrack, run laps or repeat
sections, I have included some buttons
to give the unit waypoints.
Basically, after you run each straight
section and are about to make a turn,
you press the “P” button to indicate to
the unit that you have just completed
a section.
This way, it will correctly track the
distance you jog even if you loop back
around.
This also serves as a kind of “lap”
button, ie, it will show the distance
78
Silicon Chip
that you’ve travelled since you last
pressed the P button, as well as the
total distance travelled in this session so far.
You can press the “Q” button when
you’ve finished jogging and it will
show you the total distance you’ve
travelled, how long it took and your
average speed in km/h.
You can do this at any time after you
have finished jogging since the data is
stored in EEPROM and only cleared
when you press the P button to start
the next session.
As shown in the circuit diagram,
there isn’t much hardware required;
you can build it using an Arduino
Uno, a Nano or a bare ATmega328P
IC.
If using the bare IC, you will need
to load it with the minimal Arduino
bootloader which can operate without a crystal.
Details on how to do this are shown
at: www.arduino.cc/en/Tutorial/
ArduinoToBreadboard
The OLED display is controlled via
an I2C serial bus so it’s wired up to the
SDA and SCL control lines at pins 27
and 28 of IC1 respectively. NMEA serial data from the GPS receiver is fed
to pin 15 of IC1 (digital input PB1).
The battery voltage is reduced by
a 330kW/390kW resistive divider and
fed to analog input ADC0 at pin 23 so
Celebrating 30 Years
that the micro can monitor the battery voltage.
The GPS receiver, micro and OLED
are all powered from a 3.3V rail produced by an HT7333-1 250mA lowdropout (LDO) regulator with power
from a single lithium-ion or lithiumpolymer cell.
These have a nominal voltage of
around 3.7V but typically vary from
4.1-4.2V fully charged, down to around
3.0-3.3V when fully discharged. There
is no cell reverse polarity protection so
ensure it is wired correctly!
I built the unit on a small piece
of double-sided prototyping matrix
board, with the Arduino Nano, OLED
display and buttons mounted on one
side and the battery and other components soldered to the opposite side.
The GPS receiver was connected
by flying leads (see photograph to the
right). Make the connections using
point-to-point wiring, as shown in the
circuit diagram.
Having built the unit, take it outdoors (so it has a clear path to the GPS
satellites) and power it up. The 1pps
LED on the GPS receiver should start
to flash and then you will get a display on the OLED screen indicating
your current latitude, longitude, the
number of satellites in view, current
time in UTC and your current speed.
Press the P button and a new line
will appear below the others, indicating the distance that you’ve travelled
siliconchip.com.au
in km, for the current segment and in
total (initially both zero), the number
of segments you have traversed (also
initially zero) and the number of seconds elapsed.
Press the Q switch and check that
the summary appears. You can then
press the P button to start a new session and take the unit out for a test jog!
The software (including header file)
will be available from the Silicon Chip
website and is labelled "ARDUINO_
GPS_OLED_speedo_meter.ino".
Bera Somnath,
Vindhyanagar, India. ($70)
Sunset Switch to discourage possums
We had trouble with possums in
a tree outside our back door. Every
morning, the ground was covered in
droppings, leaves etc. We accidentally
left on our outdoor spotlights one night
and noticed that there was a significant
reduction in possum-related mess.
Whilst it is not difficult to turn on
the spotlights as it turns dark and turn
them off again in the morning, I needed
a “sunset” switch so I wouldn't forget.
The circuit I devised is based on a
light-dependent resistor (LDR). When
it's light, the LDR's resistance is low,
so the voltage at pin 2 of comparator
IC1 (actually an LM358 op amp) is
low. The non-inverting input, pin 3,
is supplied with a reference voltage
that's derived from the 9V supply and
siliconchip.com.au
adjusted using trimpot VR1.
As darkness falls, the LDR resistance increases and the voltage at pin
2 rises. Eventually, it rises above that
of pin 3 and so output pin 1 goes low,
switching off transistor Q1 and allowing current to flow from the 9V supply
through the two 1kW resistors to the
base of Q2, which then switches on.
This energises the coil of relay RLY1,
closing the contacts and applying
230VAC to the spotlight(s) plugged
into the 3-pin mains socket.
The 11kW resistor between pins
1 and 3 of IC1 provides hysteresis,
which prevents the relay from chattering (switching on and off rapidly) at
dawn and dusk, when a cloud passes
overhead, etc.
Celebrating 30 Years
If using a different type of relay for
RLY1, ensure that its "must operate"
voltage is below 9V or it may not work
reliably. Most 12V DC coil relays will
switch on at 9V but a relay with a 9V
DC coil would certainly work if you
can find one with appropriate contact ratings.
Power for the circuit is derived from
the same mains supply that is fed
through to the spotlights, using a small
9V centre-tapped transformer with a
bridge rectifier (BR1) at its output that
feeds a 470µF filter capacitor and 7809
linear regulator (REG1).
Diode D1 quenches the relay coil
back-EMF at switch-off while a neon
and series resistor across the switched
mains supply indicate that power is
present.
I fitted a 2A fuse in the Active line
to protect the circuit and this provides
more than enough current to operate
a few 10W LED floodlights but you
would need a higher-current fuse if
you want to power halogen lamps or
similar.
I aimed one spotlight directly at the
tree trunk and another into the foliage.
You may need to experiment to get the
best result.
This circuit could be used for many
other purposes that need to sense light
levels and switch on or off in dark or
light conditions.
Jon Kirkwood,
Castlecrag, NSW. ($40)
May 2018 79
Adjustable low-pass filter
An adjustable active low-pass filter
can be useful in a number of audio
applications.
For example, it can be used to clean
up and reduce the distortion of a sinewave from a direct digital synthesiser
(DDS). Or it can be used to limit the
bandwidth of a noise source. This one
can be adjusted to have a -3dB point
between about 600Hz and 100kHz.
RC (resistor-capacitor) filters are
first-order filters and so have the slowest roll-off (6dB/octave). They also
have desirable characteristics, like a
lack of ripple in the passband without tuning, and very low noise and
distortion when the right components
are used. Hence, this filter is based on
passive RC filters but does offer some
active buffering and amplification if
required.
The input signal is AC-coupled with
a 10µF non-polarised capacitor, or DC
coupled if S1 is closed, shorting out
that capacitor. It is then fed to potentiometer VR1 which acts as a level control, with diodes D1 and D2 clipping
Frequency
Switch
1.5kHz
9/17
4.5kHz
8/16
12kHz
7/15
30kHz
6/14
83kHz
5/13
200kHz
4/12
660kHz
3/11
1MHz
2/10
the signal so it does not exceed the
supply rails and the 200W resistor limits the current through those diodes.
The level-adjusted signal is then
fed to low-noise buffer op amp IC1a.
It operates with unity gain if switch
S18 is open or two times gain if the
switch is closed.
Its output is then fed to the first passive low-pass filter stage, which uses a
fixed 1.6kW resistor and a combination
of eight capacitors from 100pF to 68nF,
selected by DIP switch bank S2-S9.
This gives a selectable -3dB point
of between 616Hz (all eight switches
closed) and 1MHz (only S2 closed).
The -3dB point can be calculated
by adding up the capacitors which
are switched into the circuit by S2-S8
and then feeding this into the following formula: f(Hz) = 1 ÷ (2π × 1600W
× C) where C is the sum of the capacitor values in farads.
The values with one switch closed
at a time are 1.5kHz, 4.5kHz, 12kHz,
30kHz, 83kHz, 200kHz, 660kHz and
1MHz. The capacitor values were cho-
sen to give a good range of intermediate frequencies between these values
and below 1.5kHz, when more than
one switch is closed.
Having passed through the first RC
filter, the signal is then buffered by another low-noise op amp, IC1b, again
with the option of two times gain, using switch S19.
The signal is then fed to another
identical filtering and buffering/amplification arrangement, this time using DIP switch bank S10-S17 and op
amp IC2a. DIP switches S10-S17 can
be left open if a single-order filter is
desired; in this case, IC1b will simply
act as a gain stage/buffer (depending
on the setting of S19).
If the two DIP switch banks are configured identically, the -3dB point will
be reduced by 36% compared to a single filter.
For example, if S2-S8 are open and
S9 is closed, the first stage will have a
-3dB point of 1463Hz (1 ÷ [2π × 1.6kW
× 68nF]). If S10-S16 are also open
and S17 also closed, the overall -3dB
Values with one switch closed
80
Silicon Chip
Celebrating 30 Years
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Circuit Ideas Wanted
Got an interesting original circuit that you have cleverly devised? We will pay
good money to feature it in Circuit Notebook. We can pay you by electronic
funds transfer, cheque or direct to your PayPal account. Or you can use the
funds to purchase anything from the SILICON CHIP on-line shop, including
PCBs and components, back issues, subscriptions or whatever. Email your
circuit and descriptive text to editor<at>siliconchip.com.au
point of the circuit will then be 936Hz
(1463Hz × 64%).
The roll-off above the -3dB point is
6dB/octave for a single stage (first-order) filter and 12dB/octave for a second-order filter.
It would be possible to configure the
two DIP switch banks differently and
this would give you a dual-slope response, with around -6dB/octave between the two corner frequencies and
then -12dB/octave above the higher
of the two.
The output from both filter banks
is fed to CON2 via a 100W resistor
(OUT1), to isolate any output capacitance from op amp IC2a and prevent
oscillation. Op amp IC2b inverts the
siliconchip.com.au
signal from IC2a and this is fed to a separate, complementary output (OUT2),
again via a 100W resistor.
Depending on the positions of
switches S18-S20, the maximum possible gain is eight times. The output
level can be fine-tuned using VR1.
For the best performance, set VR1 at
the highest level possible and enable
the minimum number of gain stages to
obtain the required output amplitude.
The circuit requires split rails to
function and these are provided from
a 15VAC plugpack by a half-wave voltage doubling rectifier, two filter capacitors and 7815/7915 linear regulators.
Petre Petrov,
Sofia, Bulgaria. ($50)
Celebrating 30 Years
May 2018 81
Using Cheap Asian Electronic Modules Part 16: by Jim Rowe
35MHz-4.4GHz digitally
controlled oscillator
This programmable frequency
module is based on the ADF4351 PLL
(Phase-Locked Loop) IC and it can
produce a sinewave from 35MHz to
4.4GHz, with crystal accuracy.
It can even be used as a sweep
generator and costs less than $30.
T
hat’s an impressive range of frequencies that can be produced by
this surprisingly compact (48 x 36.5
x 10mm) module. It is available from
various Chinese websites including
Banggood (siliconchip.com.au/link/
aajb) and AliExpress, as well as eBay,
for around $30.
It’s essentially a smaller, lower-cost
version of the ADF4351 development
board sold by Analog Devices. It runs
from 5V and has two RF outputs, one
180° out of phase with the other, allowing it to produce either single-ended
or differential signals.
It’s controlled using a serial bus
that’s connected via a 10-pin header,
which also makes connection to the
3.3V supply rail.
The ADF4351 chip at the heart of
the module is an advanced phaselocked loop (PLL) device. Before we
delve into how the ADF4351 works,
it’s a good idea to briefly cover the operation of PLLs.
Fig.1 shows the block diagram of a
basic PLL. It incorporates a negative
feedback loop, similar to the one used
to improve the performance of audio
amplifiers. But in this case, rather than
having a voltage divider providing the
feedback signal, we have a frequency
divider in the loop.
The PLL’s output signal (Fout) is
produced by the voltage-controlled
82
Silicon Chip
oscillator (VCO) at upper right. The frequency
divider divides this output frequency
by a factor of N.
The resulting signal (Ffb) is then fed
to the negative input of phase detector PD, which compares its frequency
and phase with Fref, the signal from
a low-frequency reference oscillator,
fed to its positive input.
The PD output “error” pulses are fed
to charge pump CP, which uses them to
develop a fluctuating DC voltage with
a polarity and amplitude proportional
to the frequency/phase differences between Fref and Ffb. This voltage is then
low-pass filtered and used to control
the VCO’s frequency.
This feedback action causes the
VCO frequency (Fout) to stabilise at
very close to N times the reference
frequency, Fref. The PLL is then described as being “in lock”, since the
feedback action keeps Ffb locked to
Fref in both frequency and phase.
So even if Fref is fixed, by changing
the division ratio N, we can control
the frequency of Fout. Basic PLLs like
this have been in use for many decades
but more elaborate versions have also
been developed, to overcome some of
the limitations of a basic PLL.
One of these limitations is that the
minimum change in Fout is equal to
Fref, so you need quite a low reference
frequency to have fine control over the
output frequency.
But it’s easier to produce accurate
and stable reference oscillators at higher frequencies, so one of the first enhancements to PLLs was to add a reference frequency divider between the
Fref input and the phase detector PD.
Also, if the output frequency needs
to be up in the GHz (Gigahertz) range,
it’s not easy to provide a programmable
divider working at these frequencies.
So another early PLL improvement
was to add a fixed “prescaler” to the
feedback loop, between the VCO output and the input of the main (programmable) feedback divider.
Fig.1: block diagram of
a basic phase-locked
loop. They’re typically
used to generate a
stable high-frequency
signal from a fixed lowfrequency signal.
Celebrating 30 Years
siliconchip.com.au
Fig.2: block diagram of the ADF4351 wideband synthesiser IC. The integrated voltage-controlled oscillator has an output
frequency range of 2.2 to 4.4GHz, which, when combined with the RF divider, provides the ~35MHz to 4.4GHz range. The
fractional-N PLL controls the frequency from its three registers via the equation: Fout = Ffb × (INT + FRAC ÷ MOD).
Unfortunately, this reduces the output frequency adjustment resolution.
However, this can be overcome by
adopting what’s referred to as a “dual
modulus prescaler”.
This is essentially a prescaler with
a division ratio that can be switched
from one value (say P) to another (like
P+1) by an external control signal.
We don’t have space here to fully
explain the operation of modern (and
quite elaborate) PLLs but the prior description should be enough to understand how the ADF4351 works.
Inside the ADF4351
The block diagram of the ADF4351
IC (Fig.2) is somewhat more complex
than the basic PLL shown in Fig.1.
The VCO part of the device is labelled
“VCO CORE” and shaded pink.
There are actually four VCOs inside
the core, each used to generate a different frequency range. They are all tuned
by the dual varicap diode shown to its
right, using a tuning voltage fed in via
the Vtune pin.
Above the VCO core, you can see the
phase comparator and charge pump,
both blue. The charge pump output
goes to the CPout pin, so that an external low-pass filter can be used to
smooth the pulsating output of the
charge pump before it is fed back into
siliconchip.com.au
the ADF4351 via the Vtune pin.
The differential outputs from the
bottom of the VCO core go to three
different destinations. One of these is
to the yellow “RF DIVIDER” block to
its right. This programmable frequency divider can divide the VCO output
frequency by 1 (ie, no division), 2, 4,
8, 16, 32 or 64.
This lets the chip generate low output frequencies while the VCO core is
operating at much higher frequencies
(2.2-4.4GHz).
The outputs from the RF divider
are fed directly to the chip’s main RF
output stage, which drives the A+ out
and A- out pins. The RF divider outputs also go to the inputs of two different multiplexers (digital selector
switches), shown in mauve.
The auxiliary multiplexer on the
right switches between the direct output lines from the VCO core and the
outputs from the RF divider and so
determines which is fed to the auxiliary RF output stage and then to the
B+ and B- output pins. The PDBRF
pin allows both RF output stages to be
disabled when they are not needed, to
save power.
The feedback (F/B) multiplexer at
left determines which of the same two
signal pairs go to the feedback divider,
in the yellow box. It’s also rather more
Celebrating 30 Years
complex than the simple feedback divider shown in Fig.1. That’s because
the ADF4351 offers the ability to implement either an integer-N or a fractional-N PLL, as required.
So the feedback divider needs three
registers which hold the integer division value, the fractional division
value and the modulus value, plus
control circuitry labelled “third-order
fractional interpolator”.
This circuitry effectively allows the
feedback frequency to be divided by a
rational number (fraction). The output
of this divider is then fed, via a buffer,
to the phase comparator.
The circuitry shown in the upperleft corner of Fig.2 takes the input
from the external reference oscillator
(fed into the REFin pin) and processes
it before feeding it to the other phase
comparator input.
As mentioned earlier, one of the refinements to earlier PLLs was to add a
reference signal frequency divider, so
that high-frequency reference oscillators could be used; hence the 10-bit
R counter.
But the ADF4351 also provides a
frequency doubler and an additional
divide-by-two stage for the reference
input, both of which can be switched
in or out under software control. This
gives the chip a great deal of flexibility.
May 2018 83
Fig.3: complete circuit diagram for
the ADF4351 frequency synthesiser
module.
The whole chip is controlled by
means of a simple 3-wire serial peripheral interface (SPI), shown at centre left of Fig.2.
Serial data from the PC or microcontroller is fed in via the DATA pin,
clocked into the serial data register and
function latch via clock pulses fed to
the CLK pin, and then latched into the
various control registers by feeding in
a pulse via the LE (latch enable) pin.
All functions of the ADF4351 chip
are configured using six 32-bit control
words, sent over this serial bus.
Multiplexer C and the other blocks at
the upper right of Fig.2 allow external
monitoring of the ADF4351’s status.
The “LOCK DETECT” block monitors the phase comparator and provides a high logic output on the LD pin
when the PLL is locked. Multiplexer
C allows either of the two phase comparator inputs or this lock status to be
fed to MUXout pin.
84
Silicon Chip
The fast lock switch provides a signal which can be fed into the external low pass filter (between the CPout
and Vtune pins) when in “fast lock”
mode. So that covers the operation of
the IC itself.
The synthesiser module
The full circuit of the module is
shown in Fig.3 and most of the real
work is done by IC1.
All of the programming and status
monitoring signals to and from the
module are available at CON1. This
includes the DATA, CLK and LE lines
(ie, the serial bus) and also the CE (chip
enable), LD (lock detect), MUXout and
PDBRF (power down RF buffer) lines.
The reference signal is provided by a
25MHz crystal oscillator (XO), shown
at upper left, with its output fed to the
REFin pin of IC1 via a loading/coupling
circuit comprising two 1nF capacitors
and a 51W resistor.
Celebrating 30 Years
Note that there is also provision for
feeding in a different reference signal,
via the SMA socket labelled MCLK. In
order to do this, you’d need to remove
the 0W resistor connected to pin 3 of
the onboard XO. If you are using the
onboard XO, the MCLK socket can be
used to monitor its output via a scope
or frequency counter.
The resistors and capacitors connecting the CPout and SW pins of IC1
(pins 7 and 5) to the Vtune pin (pin 20)
form the low-pass loop feedback filter.
The RF output signals from the
RFOA+ and RFOA- pins (12 and 13)
are taken to the RFout+ and RFoutSMA sockets via matching/filtering
circuits using L2, L3, L5 and L6, plus
two 1nF capacitors.
Notice that the output pins are fed
with the +3.3V supply voltage via L2
and L3. In this module, the auxiliary
RF outputs RFob+ and RFob- (pins 14
and 15) are not wired up.
siliconchip.com.au
Fig.4: when connecting the ADF4351 synthesiser module to an Arduino-based device, a few extra resistors are needed.
These resistors form a voltage divider, as the module can only handle 3.3V signals, while the Arduino’s outputs have a
swing of 5V. Note the changes needed if using a V2 module at the end of this article.
The whole module operates from a
3.3V supply, derived from the 5V input at CON2 via REG1, an ASM1117
low-dropout regulator. This AVdd rail
powers all of the analog/RF circuitry
directly.
The digital supply rail, DVdd, is derived from AVdd using LC filters comprising inductors L4 and L1 and a
number of bypass capacitors.
There are two indicator LEDs. LED1
is connected between the DVdd line and
ground and indicates when the module
has power while LED2 is connected to
the LD (lock detect) pin of IC1 (pin 25)
and indicates when the PLL is in lock.
All the remaining components are
for bypassing and stability, apart from
fuse F1 and diode D1, which prevent
damage in the event that the 5V power source is connected with reversed
polarity.
Controlling it with an Arduino
I initially hooked the module up to
an Arduino Uno using the simple circuit shown in Fig.4. The three main
control lines MOSI, SCK and LE are
not taken directly to the DAT, CLK and
LE pins of the module but instead via
1.5kW/3kW voltage dividers.
This is because the inputs of the
ADF4351 can only cope with 3.3V
signals, whereas the Arduino outputs
have a 5V output swing.
The LD signal fed back from the
module to the Arduino’s D2 pin does
not need a divider because it’s going
the other way and the Arduino inputs
function well with a signal having a
swing of 3.3V.
siliconchip.com.au
Note also that Fig.4 indicates that
the 5V supply for the module can come
from either a plugpack or from the 5V
output of the Arduino. I adapted an
Arduino sketch I found on the internet, written by French radio amateur
Alain Fort F1CJN (siliconchip.com.
au/link/aaje).
Mr Fort’s sketch was written for an
Arduino with an LCD button shield
but I decided to adapt it so that it
would work with the simple configuration shown in Fig.4, relying on the
Arduino IDE’s Serial Monitor to send
commands to the ADF4351 and to indicate the PLL’s output frequency and
whether it was locked or not.
I also connected one of the PLL
module’s RF outputs to my frequency counter, via a prescaler, so I could
monitor it.
The results were quite impressive. I
could type in any frequency between
35MHz and 4.4GHz, with a resolution
of 0.01MHz (10kHz) and the module’s
output would lock to that frequency
in the blink of an eye.
I also monitored the current drawn
by the module and found that it varied
between 110mA and 145mA, depending on the output frequency.
I also checked the accuracy of the
module’s 25MHz on-board reference
XO and found it to be 25.0000734MHz
or only 73.4Hz high. Since this equates
to an error of just +2.936ppm, it seems
quite accurate.
So that’s one easy way to get the
ADF4351 module going with an
Arduino. The sketch (“ADF4351_and_
Arduino_SC_version.ino”) is available for download from the Silicon
Chip website.
Driving it from a Micromite
I also hooked the module up to a
Micromite LCD BackPack combination and wrote some code so that
it could be controlled via the LCD
touchscreen.
The circuit is shown in Fig.5 and it’s
about as simple as you can get. In this
The bottom view of
this module is shown
at approximately
twice actual size.
The bottom
of the board
is populated
by five 10kW
10kW
pulldown resistors
for the breakout pin
connections.
Celebrating 30 Years
May 2018 85
Fig.5: when connecting the ADF4351 module to a Micromite no extra
components are needed, unlike with an Arduino. However, the newer version of
the module requires a 10kW resistor between CE and +3.3V.
case, no resistive dividers are needed
on the SCK, MOSI and LE lines because the Micromite’s logic pins have
a swing of 3.3V.
I used a “software” SPI port rather
than the hardware one used by the
Micromite to communicate with the
LCD and touchscreen, to prevent possible interaction.
The embedded C code (CFUNCTION) needed to provide this added
port is included in the MMBasic program I wrote for this approach. Software SPI port performance is limited
but that isn’t a problem as the amount
of data to transfer is small.
A USB charger was used to supply
5V to the ADF4351 module because
its current drain is a little too high for
the BackPack to provide.
The software uses just two screens,
as shown below. The initial screen (at
left) displays the current frequency
and gives you the option of touching
the button at the bottom if you want
to change it.
You will then get the second screen,
which allows you to key in a new frequency, displayed below the current
frequency.
When you’re happy with the new
figure, simply touch the OK button
and the module jumps to the new
frequency. The program returns to
the main screen, displaying the new
frequency.
So for those who would like to team
up the module with a Micromite, this
program (“Simple ADF4351 driver
program.bas”) should get you off to a
good start. Like the Arduino sketch,
it’s available from the Silicon Chip
website.
Performance
I checked the module’s RF output
performance at quite a few different
frequencies, using my Signal Hound
USB-SA44B spectrum analyser controlled by Signal Hound’s “Spike”
software.
The results were quite impressive,
as you can see from the two spectrum
plots. One plot shows the output at
275MHz, with the only significant
spurs visible being at ±50MHz with
an amplitude of -57dBm.
The other plot shows the output at
4.200GHz, with two spurs again visible but this time both on the low side:
one at 4.150GHz (far left) with an amplitude of about -53dBm and the oth-
The sample program running on a Micromite LCD BackPack. These are the only two screens the software uses, one to
enter a specific frequency for the module to output and another to display the current frequency.
86
Silicon Chip
Celebrating 30 Years
siliconchip.com.au
Spectrum analysis of the ADF4351 module’s output performance at 275MHz (left) and 4.2GHz (right). The RF output
performance over the full range was good, with only a few visible spurs outside the programmed frequency. These
normally correspond to beat frequencies or integer-multiples of the reference and oscillator frequency.
er at 4.175GHz with an amplitude of
-61dBm.
In both cases, the amplitude of the
main output carrier is very close to
0dBm. This turned out to be the case
over most of the range, in fact.
The only region where the carrier
level did drop (to around -20dBm) was
in the vicinity of 2.45GHz – perhaps by
design, to minimise interference with
WiFi and Bluetooth systems.
Overall, the ADF4351 frequency
synthesiser module is very impressive,
especially when you consider its frequency range and price.
It could even be used to make your
own VHF/UHF signal and sweep generator, teamed up with a Micromite
and a 4GHz digital attenuator module
that we will describe in next month’s
issue.
These changes will be critical to
successfully connect the module to
a micro, so here are the main details
listed below:
1. Many of the connections to the
10-way pin header (CON1) have
changed, as shown in Fig.6.
2. There is now no on-board pullup
resistor connecting IC1’s CE pin to
the +3.3V (DVdd) line, nor are there
pulldown resistors connected between the CLK, DATA and LE pins
and ground.
To ensure normal operation of the
module with either an Arduino or a
Micromite, an external 10kW resistor
must be connected between the CE
and +3.3V pins of CON1.
To ensure maximum stability, it’s
a good idea to also connect an external 10kW resistors between the LE pin
and ground.
Once the above changes are made,
version 2 of the module performs just
as well as the earlier version.
Useful links
The module from AliExpress: www.
aliexpress.com/item//32848807357.
html
The module from eBay: www.ebay.
com.au/itm/142521016834
ADF4351 data sheet: siliconchip.
com.au/link/aajc
Fundamentals of PLLs: siliconchip.
SC
com.au/link/aajd
Fig.6: CON1 has been
changed completely on
the newer version of
the ADF4351 module.
Every signal, except
for CLK, is connected
to a different pin
location.
A new version of the
ADF4351 synthesiser module
Just recently we received a second
ADF4351 Synthesiser module and
discovered that it was a “V2” module
which had been changed in a number of ways compared with the first
version.
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Celebrating 30 Years
May 2018 87
PRODUCT SHOWCASE
COMING THIS MONTH:
Entry-level R&S Spectrum Analyser
with advanced-level features
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The 2018 WIA RADIO & ELECTRONICS
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The latest Rohde & Schwarz spectrum analyser is the first analyser on the market to integrate the three most-commonly-used instruments on an RF engineer’s workbench, in one budget-friendly
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It combines a 5kHz to 1GHz Spectrum Analyser (with instant option up to 3GHz), a Network Analyser and an inbuilt Signal Generator.
The R&S FPC1500 is the world’s first spectrum analyser to include
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It is ideal for education, for applications in service and repair shops
and for advanced hobbyists.
Despite its budget-friendly concept, the R&S FPC1500 is designed to the same quality standards as high-end Rohde & Schwarz
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Spectrum analyser
For applications requiring a high sensitivity to characterise extremely weak signals, the R&S FPC1500 offers a low noise floor
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This combination of high sensitivity and high input power level
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Network analyser
Thanks to the internal VSWR bridge, the R&S FPC1500 can perform
reflection measurements. This allows users to measure impedance on
antennas or RF circuits with the Smith chart display or use distanceto-fault measurements to detect faulty locations on a long RF cable.
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88
Silicon Chip
The WIA Annual General Meeting (AGM) and Technical Forum will be held over the weekend of 18th, 19th and 20th
May 2018 at SeaWorld on the Gold Coast (Queensland).
This year’s event is being organised by the Gold Coast Amateur Radio Club (GCARC) with most of the weekend’s activities taking place at the Sea World Resort.
As has become the tradition, there will be a Friday night
dinner which will lead into a full day convention on Saturday, with a field day on the Sunday plus many unique tours.
Registration and detailed information is available at
www.wia.org.au/convention
or by emailing wiaagm<at>wia.org.au.
CeBIT IN
MAY, TOO
Immediately prior to the WIA Convention, CeBIT Australia, the largest
and longest running
business technology conference in the Asia Pacific, will take place
from 15-17 May 2018, at the International Convention Centre, Darling Harbour, Sydney.
This year’s CeBIT is themed “The Future of Business Technology”
and the FutureTech Stage will feature a host of the world’s most renowned industry experts on matters relating to the Internet of Things
(IoT), FinTech, Artifi- Contact:
cial Intelligence (AI) CeBIT
and Machine Learning. Registrations: www.cebit.com.au
Jaycar has Wireless Qi Charging
Got an iPhone®8, 8 Plus, iPhone X, Samsung Galaxy
Note 8 / S8 / S8 Plus, S7 / S7 Edge or other
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Jaycar stores now have available the new
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Contact:
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Tel: (02) 8832 3100
Web: www.jaycar.com.au
Celebrating 30 Years
siliconchip.com.au
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How good are you at remembering formulas? If you don’t
use them every day, you’re going to forget them!
In fact, it’s so useful we decided our readers would love to
get one, so we printed a small quantity – just for you!
Things like inductive and capacitive reactance? Series and
parallel L/C frequencies? High and low-pass filter frequencies?
And here it is: printed a whopping A2 size (that’s 420mm
wide and 594mm deep) on beautifully white photographic
paper, ready to hang in your laboratory or workshop.
This incredibly useful reactance, inductance, capacitance
and frequency ready reckoner chart means you don’t have
to remember those formulas – simply project along the
appropriate line until you come to the value required, then
read off the answer on the next axis!
Here at SILICON CHIP, we find this the most incredibly useful
chart ever – we use it all the time when designing or checking
circuits.
If you don’t find it as useful as we do, we’ll be amazed! In
fact, we’ll even give you a money-back guarantee if you don’t!#
Order yours today – while stocks last. Your choice of:
Supplied fold-free (mailed in a protective mailing tube);
or folded to A4 size and sent in the normal post.
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#Must be returned post paid in original (ie, unmarked) condition.
Read the feature in January 2016 Silicon Chip (or view online) to see just how useful this chart will be in your workshop or lab!
NOW AVAILABLE, DIRECT FROM www.siliconchip.com.au/shop:
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siliconchip.com.au
Celebrating 30 Years
May 2018 89
Vintage Radio
By Dr Hugo Holden
The
Royal 500
“Owl Eye” AM Radio
The Zenith Royal 500 radio appeared in
1955, one year after the Regency TR-1
which was the first commercial transistor
radio in 1954. Unlike the Regency TR-1
though, by the time that the Zenith Royal
500 was released, the technology had
rapidly progressed into the conventional
circuitry we know today as the typical “7
transistor AM radio”.
The Regency TR-1 was powered
by a 22.5V battery to help overcome
the effects of the large base-collector
junction capacitances of the very early
transistor types and it had a low intermediate frequency (IF) of 262.5kHz to
help overcome transistor bandwidth
limitations. It also had a single ClassA output stage.
However, the Zenith Royal 500 had
more advanced transistors, the conventional 455kHz IF and was powered
by 6V from four AA cells. It also had
a conventional transformer-coupled
Class-B push-pull audio output stage.
The styling of the Royal 500 could be
said to be distinctive, with the metallic surrounds for the black tuning and
volume controls and the metallic
speaker grille, so much so that in later years it became known as the “Owl
Eye” radio.
Also of interest was that its case was
labelled on the back as “Unbreakable
Nylon”. That might seem to have been
asking for trouble but my sample does
appear to have lasted well, with no
90
Silicon Chip
cracks in the case.
Also on the back and shown in the
photo below, the radio is described
as “TUBELESS - 7 TRANSISTORS”.
Circuit details
The transistors used in the Royal
500are germanium NPN types, as was
the case in other very early AM radios, such as the Regency TR-1 (www.
siliconchip.com.au/Article/3761,
April 2014) and the Sony TR-72 (www.
siliconchip.com.au/Article/6938,
March 2014).
However, by the early 1960s most
manufacturers had changed to germa-
Celebrating 30 Years
nium PNP types and by the early 1970s
there was a general shift to silicon transistors in most new equipment.
As shown in the circuit diagram of
Fig.1, while the design of the Royal
500 now looks to be conventional, it
represented a very rapid development
in solid-state radio technology.
It became the “world standard” for
an AM radio, with three IF transformers, a detector diode and a 3-transistor two-transformer audio system with
a Class-A driver stage and as already
noted, a push-pull output stage.
In one aspect, the circuit was not
world standard, in that it has separate oscillator and mixer transistors.
Most later radios had a single mixeroscillator transistor (often referred to
as a converter) and saved a transistor
by this approach.
Then again, quite a few designs
added an audio preamp transistor, so
the total transistor count remained the
same at seven.
Interestingly, the circuit has an error, because the detector diode X1
siliconchip.com.au
Fig.1: it’s important to note that the circuit diagram has an
error where the detector diode X1 (centre) is drawn reversed.
Earlier versions of this circuit had 2200W & 18kW resistors
between C15 & C16; these were changed to the current values
of 4700W & 47kW respectively, to stabilise the collector current
of the 2N35 driver transistor and increase gain.
(1N295) is drawn reversed (it is hard
to see and is at the secondary output
of the third IF transformer, T3). It is
not wired this way in the real radio
though, where the diode cathode is
returned to ground (negative).
Subsequently there were a number
of circuit variations in the Zenith Royal
500, dictated by parts supply, with
changes to the AGC design and some
versions using PNP transistors too.
The negative-going AGC voltage is
developed across C22, a 16µF 3V electrolytic capacitor.
With low signal levels this electrolytic capacitor is subject to a small voltage of the correct polarity from the bias
network of the 2N216 and first IF amplifier (the 100kW and 4700W resistors
connected to C22’s positive electrode).
This also forward-biases the detector
diode X1 a little, which helps with detecting low level signals.
However, with most reasonable signal levels from local stations, the AGC
voltage on the positive terminal of
C22 goes negative with respect to the
radio’s ground and then C22 is subject to reversed polarity; not good for
an electrolytic capacitor.
This is actually a “classic mistake”
in the design of AGC circuits in many,
but not all, transistor radios.
In fact, this problem appears to have
gone unnoticed for over half a century
siliconchip.com.au
for many transistor radio designs. The practical remedy today is to
fit a bipolar electrolytic AGC filter capacitor instead.
Perhaps not surprisingly, this AGC
filter capacitor often does go open-circuit in early transistor radios and C22
was open-circuit in my Zenith radio.
The unbypassed feedback causes oscillation of the IF stages.
That turned out to be the case when
I first switched on my Zenith radio
and it was clear from the heterodyne
sounds on tuning stations that the IF
was oscillating. It would only weakly
receive stations and there was a lot of
random noise and static too.
Investigation revealed that the mixer transistor had partially failed and
the first IF transistor was noisy. The
faulty components are indicated in
red on the circuit.
All the other electrolytic capacitors,
aside from C22, were normal on test for
capacitance, ESR and leakage which
surprised me, considering their age.
Editor’s note: modern electrolytic capacitors will tolerate a small negative
bias voltage (<1.5V) long-term without failure.
would cause oscillations in the IF
amplifier stages unless neutralisation
was employed.
On this circuit, this is effected by the
11pF and 3900W feedback components
around the two 2N216 IF transistors.
Many European-made PNP transistors for IF work such as the OC45 also
required neutralisation when used in
455kHz IF stages in typical AM radio
circuits.
When it comes to replacing the
2N916 transistors, you need an NPN
germanium type with the same feedback capacitance properties or the IF
stage will become unstable and oscillate.
The alternative would be to adjust
the feedback components to compensate. I couldn’t find any 2N194 or
2N216 transistors, however I found
some 2N94s which made suitable replacements.
In radios of the mid to late 1960s,
germanium transistors with very low
feedback capacitances became available, making the need for IF neutralisation unnecessary. These included
PNP transistors such as the AF117
or AF127.
Neutralisation
Construction
Vintage transistors such as the
2N916 have fairly high base to collector feedback capacitance and this
Two photos in this article show the
interior of the Zenith radio. Note that
all the transistors are in sockets and
Celebrating 30 Years
May 2018 91
this feature helped with the faultfinding.
While the tuning dial only lists frequencies up to 1400kHz, the radio
can still tune above that frequency (to
about 1600kHz).
The electrolytic capacitors are
housed in white ceramic tubes with
their ends sealed with hard resin.
There was no evidence of any physical leakage of electrolyte from any of
them and as noted, only one was faulty.
One thing to bear in mind when
repairing and testing vintage transistor radios is that they have phenolic
PCBs, and the adhesion of the copper
tracks to the board is nowhere near as
good as with modern fibreglass PCBs.
So it pays to avoid soldering if possible and when forced to, use a good
temperature-controlled iron with the
minimal required heat.
Also, in radios where the transistors
are soldered on, they should, if possible, have heat-extracting clips placed
on their leads while soldering.
Vintage germanium transistors are
far more sensitive to heat damage than
modern silicon devices. So the advantage of sockets for transistors is that
they do not get exposed to heat from
soldering but the disadvantage is that
the socket connections can become
intermittent.
In any case it is better to do exhaustive
tests before concluding that any component in the radio needs removal or
desoldering. Fortunately, electrolytic
capacitors can be checked in circuit
with an ESR (Equivalent Series Resistance) meter.
The first step in fault-finding is to
ensure the DC operating conditions
and voltages are correct on all the
transistors. After that, AC tests with a
signal generator and the oscilloscope
can be helpful, if available.
The manufacturer’s general alignment instructions should be followed.
However, if the IF transformers have
not been touched and the original transistors are present and working OK, it
would be better in most cases not to try
adjusting the IF transformers.
In particular, it can be very easy to
break the slugs as they can be frozen in
after 60 years without being touched.
So if the slugs can’t be easily adjusted,
leave them as they are.
If transistors have been replaced in
the IF circuits, then the transformer
slugs should be re-adjusted. Or if the IF
transformers have been tampered with
92
Silicon Chip
by another party they will most likely
require checking and adjustment.
Any test signal generator should
be as loosely coupled in as possible
or the generator itself can disturb the
tuning conditions of the circuit that it
is connected to.
The best way is to simply use one
or two turns of wire around the ferrite rod (some early transistor radio
alignment instructions did specify a
magnetic loop to do it and this was a
very wise idea).
Editor's note: the AM Transmitter featured in the March 2018 issue can be
modified to tune between 440kHz and
600kHz by replacing a single capacitor. It can then be used as an alignment
source at 450 or 455kHz. The details
are in the article at: www.siliconchip.
com.au/Article/11004
Aligning the IF stages
One useful method to adjust the IF
transformers is to temporarily deactivate the local oscillator. In this particular radio it just involved unplugging
the oscillator transistor and coupling
the signal generator in with a 1-turn
loop on the ferrite rod, set for a 1kHz
modulated 455KHz carrier.
The detected audio can be seen at
the volume control with an oscilloscope, heard in the speaker or measured with an AC millivoltmeter.
Coupling a 455kHz signal to the
ferrite rod still works without deactivating the local oscillator, but a higher
signal level will be required to break
through the mixer.
In many cases it is of little help
sweeping the IF and plotting the
response curve, because the IF coils
are all tuned to a maximum peak at the
same frequency (typically 455kHz).
The point being that the IF amplifier band-pass characteristic is largely
Operation
Input
signal
frequency
Connect inner
conductor from
oscillator to
1
455kHz
2
1620kHz
3
1260kHz
4
535kHz
5
Repeat steps 2, 3 and 4
One turn loosely
coupled to
wavemagnet
While obscured in the photos, the
Royal 500 does have a separate mono
earphone jack (J1 on Fig.1).
Source: www.transistor-repairs.com/
schematics.html
set by the design of the IF transformers themselves, not by the technician
adjusting or “stagger tuning” the IF
stages.
Therefore, in my view, an IF sweep
generator or “wobbulator” for tuning
the IF stages in AM transistor radios
has little utility for repairs and adjustments. The opposite is true in correctly adjusting analog television video IF
amplifiers though.
Also, generally, it is best to set the
IF transformers, or the radio’s other
adjustments, with a low level modulated RF signal, with the modulation
tone just slightly more audible than
noise, so that the radio’s AGC is just
below threshold.
This is because small changes in
the observed demodulated audio output voltage amplitude at the detector
are suppressed by AGC action which
occurs with stronger signals.
Connect outer
shield conductor
from oscillator to
Set dial at
Trimmers
Purpose
Chassis
600kHz
Adjust T1-T3 for
maximum output
For IF alignment
Gang wide
open
C1C
Set oscillator to
dial scale
1260kHz
C1A
Align loop antenna
Gang closed
Adjust slug in T6
Set oscillator to
dial scale
All alignment steps for the Royal 500. Check www.transistor-repairs.com/
schematics.html for a great listing of schematic diagrams on Zenith radios.
Celebrating 30 Years
siliconchip.com.au
One of the selling points of the Zenith
Royal 500 was that it worked using
just four inexpensive AA 1.5V cells.
The Royal 500 shown in this article is a model B. It was released in 1956 and
used the PCB shown above, instead of being hand-wired. The transistors are
all mounted in plug-in sockets, which makes it easy to remove and replace
them. While this version of the Royal 500 used NPN transistors, later models
made the switch to PNP transistors as they became more common.
Setting the local oscillator
The oscillator coil slug is set to calibrate the pointer with the dial (or set
the lowest tuning frequency with the
variable capacitor fully meshed) at the
low end of the band.
The oscillator trimmer capacitor is
then set at the high end of the dial to
make sure the tuning range and dial
pointer are correct.
The general rule is that the inductances set the low end of the band and
the trimmer capacitors on the tuning
gang set the high end.
The exception to this rule is when
there is an adjustable padder capacitor in series with the oscillator section
of the tuning gang. This sets the low
end of the band.
Ideally the frequencies that the local
oscillator tunes over should be set according to the manufacturer’s instructions to ensure the dial scale calibration is as good as possible. This also
requires that the IF centre frequency
is correctly set.
The antenna circuit is tuned (near
the high end of the band) for maximum signal, by adjusting the trimmer
capacitor on the relevant section of the
tuning gang.
In the case of the Zenith Royal, the
manufacturer’s instructions specified
a test frequency of 1260kHz.
siliconchip.com.au
If a radio station sits near to this
frequency, and in the absence of good
test generators, it is better used as the
signal source for this adjustment as
there are no generator loading issues
to consider. In Sydney, station 2SM at
1269kHz would be ideal.
Often the ferrite rod antenna tuning cannot be easily set for a peak at
the low end of the band, because it
requires sliding the antenna coil on
the ferrite rod to adjust the inductance.
But often the coil is held in place with
wax and it is better to leave it alone.
Mechanical considerations
On the mechanical side of things,
a small amount of lubricant can be
added to the moving metal surfaces
such as the variable capacitor shaft
and bearings.
In this radio there is a ball bearing
epicyclic reduction system where the
centre tuning knob rotates at a greater rate than the dial pointer shell surrounding it; this aids fine tuning.
Cleaning and lubrication of the onoff switch and volume control is often required.
In this radio, there was corrosion
and a white oxide on the transistor
bodies. This was carefully removed
without affecting the labels or logos
and the transistors bodies wiped with
Celebrating 30 Years
a small amount of WD40 to help protect them. A coat of clear varnish can
be added after that, if required.
Performance
After repairs my sample Zenith 500
radio performed well with good sensitivity and a reasonable tone, despite
the small sized speaker. It is as good
as any transistor radio made a decade
or more later, possibly better, because
of the quality of the case and components used.
For example the variable capacitor
frame in the radio is solid 1/8-inch
thick brass and the speaker has a goodsized magnet although it is compact
overall.
For all vintage transistor radios I
recommend using carbon zinc cells as
their current-sourcing ability is much
lower than alkaline cells for short circuit conditions. And if the carbon zinc
cells leak fluid, it is much less destructive than that from alkaline cells.
Conclusion
I think the Zenith Royal 500 transistor radio makes a very worthy member of a vintage transistor radio collection. It indicates how quickly transistor radio technology accelerated just
two years after the introduction of the
Regency TR-1.
SC
May 2018 93
SILICON
CHIP
.com.au/shop
ONLINESHOP
Looking for a specialised component to build that latest and greatest Silicon Chip project? Maybe it’s the PCB you’re
after? Or a pre-programmed micro? Or some other hard-to-get “bit”? The chances are they are available direct from the
Silicon Chip Online Shop.
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PCBs are normally IN STOCK and ready for despatch when that month’s magazine goes on sale (you don’t have to wait for them to be made!).
Even if stock runs out (eg, for high demand), in most cases there will be no longer than a two-week wait.
One low p&p charge: $10 per order, irregardless of how many items you order! (AUS only; overseas clients – check the website for a postage quote).
Our PCBs are beautifully made, very high quality fibreglass boards with pre-tinned tracks, silk screen overlays and where applicable, solder masks.
Best of all, subscribers receive a 10% discount on purchases! (Excluding subscription renewals and postage costs)
HERE’S HOW TO ORDER:
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YES! You can also order or renew your SILICON CHIP subscription via any of these methods as well!
PRE-PROGRAMMED MICROS
All micros are just $15.00 each + $10 p&p per order#
As a service to readers, the Silicon Chip Online Shop stocks micros used in new projects (from 2012 on) and some selected older
projects – pre-programmed and ready to fly!
*Some micros from copyrighted and/or contributed projects may not be available.
PIC12F675-I/P
PIC12F675-I/P
PIC16F1455-I/P
PIC16F1507-I/P
PIC16F88-E/P
PIC16F88-I/P
PIC16LF88-I/P
PIC16LF88-I/SO
PIC16LF1709-I/SO
UHF Remote Switch (Jan09), Ultrasonic Cleaner (Aug10)
PIC16F877A-I/P
6-Digit GPS Clock (May-Jun09), Lab Digital Pot (Jul10), Semtest (Feb-May12)
Ultrasonic Anti-fouling (Sep10), Cricket/Frog (Jun12), Do Not Disturb (May13)
PIC16F2550-I/SP
Batt Capacity Meter (Jun09), Intelligent Fan Controller (Jul10)
IR-to-UHF Converter (Jul13), UHF-to-IR Converter (Jul13)
PIC18F4550-I/P
GPS Car Computer (Jan10), GPS Boat Computer (Oct10)
PC Birdies *2 chips – $15 pair* (Aug13), Driveway Monitor Receiver (July15)
PIC18LF14K22
Digital Spirit Level (Aug11), G-Force Meter (Nov11)
Hotel Safe Alarm (Jun16), 50A Battery Charger Controller (Nov16)
PIC32MX795F512H-80I/PT Maximite (Mar11), miniMaximite (Nov11), Colour Maximite (Sept/Oct12)
Kelvin the Cricket (Oct17), Triac-based Mains Motor Speed Controller (Mar18)
Touchscreen Audio Recorder (Jun/Jul 14)
Heater Controller (Apr18)
PIC32MX170F256B-50I/SP Micromite Mk2 (Jan15) – also includes FREE 47F tantalum capacitor
Courtesy LED Light Delay for Cars (Oct14), Fan Speed Controller (Jan18)
Micromite LCD BackPack [either version] (Feb16), GPS Boat Computer (Apr16)
Microbridge (May17)
Micromite Super Clock (Jul16), Touchscreen Voltage/Current Ref (Oct-Dec16)
Wideband Oxygen Sensor (Jun-Jul12)
Micromite LCD BackPack V2 (May17), Deluxe eFuse (Aug17)
Hi Energy Ignition (Nov/Dec12), Speedo Corrector (Sept13)
Micromite DDS for IF Alignment (Sept17)
Auto Headlight Controller (Oct13), 10A 230V Motor Speed Controller (Feb14) PIC32MX170F256B-I/SP
Low Frequency Distortion Analyser (Apr15)
Automotive Sensor Modifier (Dec16)
PIC32MX170F256D-501P/T 44-pin Micromite Mk2
Projector Speed (Apr11), Vox (Jun11), Ultrasonic Water Tank Level (Sep11)
PIC32MX250F128B-I/SP
GPS Tracker (Nov13), Micromite ASCII Video Terminal (Jul14)
Quizzical (Oct11), Ultra LD Preamp (Nov11), 10-Channel Remote Control
PIC32MX470F512H-I/PT
Stereo Audio Delay/DSP (Nov13), Stereo Echo/Reverb (Feb 14)
Receiver (Jun13), Revised 10-Channel Remote Control Receiver (Jul13)
Digital Effects Unit (Oct14)
Nicad/NiMH Burp Charger (Mar14), Remote Mains Timer (Nov14)
Driveway Monitor Transmitter (July15), Fingerprint Scanner (Nov15)
PIC32MX470F512H-120/PT Micromite PLUS Explore 64 (Aug 16), Micromite Plus LCD BackPack (Nov16)
MPPT Lighting Charge Controller (Feb16), 50/60Hz Turntable Driver (May16)
PIC32MX470F512L-120/PT Micromite PLUS Explore 100 (Sep-Oct16)
Cyclic Pump Timer (Sep16), 60V 40A DC Motor Speed Controller (Jan17)
dsPIC33FJ128GP802-I/SP Digital Audio Signal Generator (Mar-May10), Digital Lighting Controller
Pool Lap Counter (Mar17), Rapidbrake (Jul17), Deluxe Frequency Switch (May18)
(Oct-Dec10), SportSync (May11), Digital Audio Delay (Dec11)
Garbage Reminder (Jan13), Bellbird (Dec13), GPS Analog Clock Driver (Feb17)
Quizzical (Oct11), Ultra-LD Preamp (Nov11), LED Musicolor (Nov12)
LED Ladybird (Apr13)
dsPIC33FJ64MC802-E/P
Induction Motor Speed Controller (revised) (Aug13)
Battery Cell Balancer (Mar16)
dsPIC33FJ128GP306-I/PT CLASSiC DAC (Feb-May 13)
When ordering, be sure to select BOTH the micro required AND the project for which it must be programmed.
SPECIALISED COMPONENTS, HARD-TO-GET BITS, ETC
USB PORT PROTECTOR COMPLETE KIT
(MAY 18)
AM RADIO TRANSMITTER
(MAR 18)
All parts including the PCB and a length of clear heatshrink tubing
MC1496P double-balanced mixer IC (DIP-14)
VINTAGE TV A/V MODULATOR
MC1374P A/V modulator IC (DIP-14)
SBK-71K coil former pack (two required)
(MAR 18)
ALTIMETER/WEATHER STATION
(DEC 17)
Micromite 2.8-inch LCD BackPack kit programmed for the Altimeter project
GY-68 barometric pressure and temperature sensor module (with BMP180, Cat SC4343)
DHT22 temperature and humidity sensor module (Cat SC4150)
Elecrow 1A/500mA Li-ion/LiPo charger board (optional, Cat SC4308)
PARTS FOR THE 6GHz+ TOUCHSCREEN FREQUENCY COUNTER
(OCT 17)
DELUXE EFUSE PARTS
(AUG 17)
Explore 100 kit (Cat SC3834; no LCD included)
one ERA-2SM+ & one ADCH-80A+ (Cat SC1167; two packs required)
IPP80P03P4L04 P-channel mosfets (Cat SC4318)
BUK7909-75AIE 75V 120A N-channel SenseFet (Cat SC4317)
LT1490ACN8 dual op amp (Cat SC4319)
$15.00
$2.50
$5.00
$5.00 ea.
$65.00
$5.00
$7.50
$15.00
$69.90
$15.00/pk.
$4.00 ea.
$7.50 ea.
$7.50 ea.
MICROBRIDGE COMPLETE KIT (CAT SC4264)
(MAY 17)
PCB plus all on-board parts including programmed microcontroller (SMD ceramics for 10µF) $20.00
MICROMITE LCD BACKPACK V2 – COMPLETE KIT (CAT SC4237)
(MAY 17)
includes PCB, programmed micro, touchscreen LCD, laser-cut UB3 lid, mounting hardware,
SMD Mosfets for PWM backlight control and all other on-board parts
$70.00
POOL LAP COUNTER
(MAR 17)
two 70mm 7-segment high brightness blue displays + logic-level Mosfet (Cat SC4189)
$17.50
laser-cut blue tinted UB1 lid, 152 x 90 x 3mm (Cat SC4196)
$7.50
P&P – $10 Per order#
STATIONMASTER (CAT SC4187)
(MAR 17)
Hard to get parts: DRV8871 IC, SMD 1µF capacitor and 100kW potentiometer with detent
$12.50
ULTRA LOW VOLTAGE LED FLASHER (CAT SC4125)
(FEB 17)
SC200 AMPLIFIER MODULE (CAT SC4140)
(JAN 17)
kit including PCB and all SMD parts, LDR and blue LED
hard-to-get parts: Q8-Q16, D2-D4, 150pF/250V capacitor and five SMD resistors
$12.50
$35.00
VARIOUS MODULES & PARTS
ESP-01 WiFi Module (El Cheapo Modules, Part 15, APR18)
$5.00
WiFi Antennas with U.FL/IPX connectors (Water Tank Level Meter with WiFi, FEB18):
5dBi – $12.50 ~ 2dBi (omnidirectional) – $10.00
NRF24L01+PA+NA transceiver with SNA connector and antenna (El Cheapo 12, JAN18)
$5.00
WeMos D1 Arduino-compatible boards with WiFi (SEPT17, FEB18):
ThingSpeak data logger – $10.00 ~ WiFi Tank Level Meter (ext. antenna socket) – $15.00
Geeetech Arduino MP3 shield (Arduino Music Player/Recorder, VS1053, JUL17)
$20.00
1nF 1% MKP (5mm lead spacing) or ceramic capacitor (Arduino LC Meter, JUN17)
$2.50
MAX7219 LED controller boards (El Cheapo Modules, Part 7, JUN17):
8x8 red SMD/DIP matrix display – $5.00 ~ red 8-digit 7-segment display – $7.50
AD9833 DDS module (with gain control) (for Micromite DDS, APR17)
$25.00
AD9833 DDS module (no gain control) (El Cheapo Modules, Part 6, APR17)
$15.00
CP2102 USB-UART bridge
$5.00
microSD card adaptor (El Cheapo Modules, Part 3, JAN17)
$2.50
DS3231 real-time clock with mounting spacers and screws (El Cheapo, Part 1, OCT16)
$5.00
MICROMITE PLUS EXPLORE 100 COMPLETE KIT (no LCD panel)
(SEP 16)
(includes PCB, programmed micro and the hard-to-get bits including female headers, USB
and microSD sockets, crystal, etc but does not include the LCD panel) (Cat SC3834)
$69.90
MICROMITE LCD BACKPACK V1 COMPLETE KIT (CAT SC3321)
includes PCB, micro, 2.8-inch touchscreen and includes UB3 lid (clear, matte black
or translucent blue). Also specify what project the micro should be programmed for
(FEB 16)
$65.00
THESE ARE ONLY THE MOST RECENT MICROS AND SPECIALISED COMPONENTS. FOR THE FULL LIST, SEE www.siliconchip.com.au/shop
*All items subect to availability. Prices valid for month of magazine issue only. All prices in Australian dollars and include GST where applicable. # P&P prices are within Australia. O’seas? Please email for a quote
05/18
PRINTED CIRCUIT BOARDS
NOTE: The listings below are for the PCB ONLY. If you want a kit, check our store or contact the kit suppliers advertising in this
issue. For unusual projects where kits are not available, some have specialised components available – see the list opposite.
NOTE: Not all PCBs are shown here due to space limits but the Silicon Chip Online Shop has boards going back to 2001 and beyond.
For a complete list of available PCBs etc, go to siliconchip.com.au/shop/8 Prices are PCBs only, NOT COMPLETE KITS!
PRINTED CIRCUIT BOARD TO SUIT PROJECT:
PUBLISHED:
PCB CODE:
Price:
CLASSiC DAC MAIN PCB
APR 2013
01102131 $40.00
CLASSiC DAC FRONT & REAR PANEL PCBs
APR 2013
01102132/3 $30.00
CLASSiC-D 12V to ±35V DC/DC CONVERTER
MAY 2013
11104131 $15.00
LF/HF UP-CONVERTER
JUN 2013
07106131 $10.00
10-CHANNEL REMOTE CONTROL RECEIVER
JUN 2013
15106131 $15.00
IR-TO-455MHz UHF TRANSCEIVER
JUN 2013
15106132
$7.50
“LUMP IN COAX” PORTABLE MIXER
JUN 2013
01106131 $15.00
L’IL PULSER MKII TRAIN CONTROLLER
JULY 2013
09107131 $15.00
L’IL PULSER MKII FRONT & REAR PANELS
JULY 2013
09107132/3 $20.00/set
REVISED 10 CHANNEL REMOTE CONTROL RECEIVER
JULY 2013
15106133 $15.00
INFRARED TO UHF CONVERTER
JULY 2013
15107131
$5.00
UHF TO INFRARED CONVERTER
JULY 2013
15107132 $10.00
IPOD CHARGER
AUG 2013
14108131
$5.00
PC BIRDIES
AUG 2013
08104131 $10.00
RF DETECTOR PROBE FOR DMMs
AUG 2013
04107131 $10.00
BATTERY LIFESAVER
SEPT 2013
11108131
$5.00
SPEEDO CORRECTOR
SEPT 2013
05109131 $10.00
SiDRADIO (INTEGRATED SDR) Main PCB
OCT 2013
06109131 $35.00
SiDRADIO (INTEGRATED SDR) Front & Rear Panels
OCT 2013
06109132/3 $25.00/pr
TINY TIM AMPLIFIER (identical Headphone Amp [Sept11]) OCT 2013
01309111 $20.00
AUTO CAR HEADLIGHT CONTROLLER
OCT 2013
03111131 $10.00
GPS TRACKER
NOV 2013
05112131 $15.00
STEREO AUDIO DELAY/DSP
NOV 2013
01110131 $15.00
BELLBIRD
DEC 2013
08112131 $10.00
PORTAPAL-D MAIN BOARDS
DEC 2013
01111131-3 $35.00/set
(for CLASSiC-D Amp board and CLASSiC-D DC/DC Converter board refer above [Nov 2012/May 2013])
LED Party Strobe (also suits Hot Wire Cutter [Dec 2010])
JAN 2014
16101141
$7.50
Bass Extender Mk2
JAN 2014
01112131 $15.00
Li’l Pulser Mk2 Revised
JAN 2014
09107134 $15.00
10A 230VAC MOTOR SPEED CONTROLLER
FEB 2014
10102141 $12.50
NICAD/NIMH BURP CHARGER
MAR 2014
14103141 $15.00
RUBIDIUM FREQ. STANDARD BREAKOUT BOARD
APR 2014
04105141 $10.00
USB/RS232C ADAPTOR
APR 2014
07103141
$5.00
MAINS FAN SPEED CONTROLLER
MAY 2014
10104141 $10.00
RGB LED STRIP DRIVER
MAY 2014
16105141 $10.00
HYBRID BENCH SUPPLY
MAY 2014
18104141 $20.00
2-WAY PASSIVE LOUDSPEAKER CROSSOVER
JUN 2014
01205141 $20.00
TOUCHSCREEN AUDIO RECORDER
JUL 2014
01105141 $12.50
THRESHOLD VOLTAGE SWITCH
JUL 2014
99106141 $10.00
MICROMITE ASCII VIDEO TERMINAL
JUL 2014
24107141
$7.50
FREQUENCY COUNTER ADD-ON
JUL 2014
04105141a/b $15.00
TEMPMASTER MK3
AUG 2014
21108141 $15.00
44-PIN MICROMITE
AUG 2014
24108141
$5.00
OPTO-THEREMIN MAIN BOARD
SEP 2014
23108141 $15.00
OPTO-THEREMIN PROXIMITY SENSOR BOARD
SEP 2014
23108142
$5.00
ACTIVE DIFFERENTIAL PROBE BOARDS
SEP 2014
04107141/2 $10.00/set
MINI-D AMPLIFIER
SEP 2014
01110141
$5.00
COURTESY LIGHT DELAY
OCT 2014
05109141
$7.50
DIRECT INJECTION (D-I) BOX
OCT 2014
23109141
$5.00
DIGITAL EFFECTS UNIT
OCT 2014
01110131 $15.00
DUAL PHANTOM POWER SUPPLY
NOV 2014
18112141 $10.00
REMOTE MAINS TIMER
NOV 2014
19112141 $10.00
REMOTE MAINS TIMER PANEL/LID (BLUE)
NOV 2014
19112142 $15.00
ONE-CHIP AMPLIFIER
NOV 2014
01109141
$5.00
TDR DONGLE
DEC 2014
04112141
$5.00
MULTISPARK CDI FOR PERFORMANCE VEHICLES
DEC 2014
05112141 $10.00
CURRAWONG STEREO VALVE AMPLIFIER MAIN BOARD
DEC 2014
01111141 $50.00
CURRAWONG REMOTE CONTROL BOARD
DEC 2014
01111144
$5.00
CURRAWONG FRONT & REAR PANELS
DEC 2014
01111142/3 $30.00/set
CURRAWONG CLEAR ACRYLIC COVER
JAN 2015
SC2892
$25.00
ISOLATED HIGH VOLTAGE PROBE
JAN 2015
04108141 $10.00
SPARK ENERGY METER MAIN BOARD
FEB/MAR 2015
05101151 $10.00
SPARK ENERGY ZENER BOARD
FEB/MAR 2015
05101152 $10.00
SPARK ENERGY METER CALIBRATOR BOARD
FEB/MAR 2015
05101153
$5.00
APPLIANCE INSULATION TESTER
APR 2015
04103151 $10.00
APPLIANCE INSULATION TESTER FRONT PANEL
APR 2015
04103152 $10.00
LOW-FREQUENCY DISTORTION ANALYSER
APR 2015
04104151
$5.00
APPLIANCE EARTH LEAKAGE TESTER PCBs (2)
MAY 2015
04203151/2 $15.00
APPLIANCE EARTH LEAKAGE TESTER LID/PANEL
MAY 2015
04203153 $15.00
BALANCED INPUT ATTENUATOR MAIN PCB
MAY 2015
04105151 $15.00
BALANCED INPUT ATTENUATOR FRONT & REAR PANELS MAY 2015
04105152/3 $20.00
4-OUTPUT UNIVERSAL ADJUSTABLE REGULATOR
MAY 2015
18105151
$5.00
SIGNAL INJECTOR & TRACER
JUNE 2015
04106151
$7.50
PASSIVE RF PROBE
JUNE 2015
04106152
$2.50
SIGNAL INJECTOR & TRACER SHIELD
JUNE 2015
04106153
$5.00
BAD VIBES INFRASOUND SNOOPER
JUNE 2015
04104151
$5.00
CHAMPION + PRE-CHAMPION
JUNE 2015
01109121/2 $7.50
DRIVEWAY MONITOR TRANSMITTER PCB
JULY 2015
15105151 $10.00
DRIVEWAY MONITOR RECEIVER PCB
JULY 2015
15105152
$5.00
MINI USB SWITCHMODE REGULATOR
JULY 2015
18107151
$2.50
VOLTAGE/RESISTANCE/CURRENT REFERENCE
AUG 2015
04108151
$2.50
LED PARTY STROBE MK2
AUG 2015
16101141
$7.50
PRINTED CIRCUIT BOARD TO SUIT PROJECT:
PUBLISHED:
ULTRA-LD MK4 200W AMPLIFIER MODULE
SEP 2015
9-CHANNEL REMOTE CONTROL RECEIVER
SEP 2015
MINI USB SWITCHMODE REGULATOR MK2
SEP 2015
2-WAY PASSIVE LOUDSPEAKER CROSSOVER
OCT 2015
ULTRA LD AMPLIFIER POWER SUPPLY
OCT 2015
ARDUINO USB ELECTROCARDIOGRAPH
OCT 2015
FINGERPRINT SCANNER – SET OF TWO PCBS
NOV 2015
LOUDSPEAKER PROTECTOR
NOV 2015
LED CLOCK
DEC 2015
SPEECH TIMER
DEC 2015
TURNTABLE STROBE
DEC 2015
CALIBRATED TURNTABLE STROBOSCOPE ETCHED DISC
DEC 2015
VALVE STEREO PREAMPLIFIER – PCB
JAN 2016
VALVE STEREO PREAMPLIFIER – CASE PARTS
JAN 2016
QUICKBRAKE BRAKE LIGHT SPEEDUP
JAN 2016
SOLAR MPPT CHARGER & LIGHTING CONTROLLER FEB/MAR 2016
MICROMITE LCD BACKPACK, 2.4-INCH VERSION
FEB/MAR 2016
MICROMITE LCD BACKPACK, 2.8-INCH VERSION
FEB/MAR 2016
BATTERY CELL BALANCER
MAR 2016
DELTA THROTTLE TIMER
MAR 2016
MICROWAVE LEAKAGE DETECTOR
APR 2016
FRIDGE/FREEZER ALARM
APR 2016
ARDUINO MULTIFUNCTION MEASUREMENT
APR 2016
PRECISION 50/60Hz TURNTABLE DRIVER
MAY 2016
RASPBERRY PI TEMP SENSOR EXPANSION
MAY 2016
100DB STEREO AUDIO LEVEL/VU METER
JUN 2016
HOTEL SAFE ALARM
JUN 2016
UNIVERSAL TEMPERATURE ALARM
JULY 2016
BROWNOUT PROTECTOR MK2
JULY 2016
8-DIGIT FREQUENCY METER
AUG 2016
APPLIANCE ENERGY METER
AUG 2016
MICROMITE PLUS EXPLORE 64
AUG 2016
CYCLIC PUMP/MAINS TIMER
SEPT 2016
MICROMITE PLUS EXPLORE 100 (4 layer)
SEPT 2016
AUTOMOTIVE FAULT DETECTOR
SEPT 2016
MOSQUITO LURE
OCT 2016
MICROPOWER LED FLASHER
OCT 2016
MINI MICROPOWER LED FLASHER
OCT 2016
50A BATTERY CHARGER CONTROLLER
NOV 2016
PASSIVE LINE TO PHONO INPUT CONVERTER
NOV 2016
MICROMITE PLUS LCD BACKPACK
NOV 2016
AUTOMOTIVE SENSOR MODIFIER
DEC 2016
TOUCHSCREEN VOLTAGE/CURRENT REFERENCE
DEC 2016
SC200 AMPLIFIER MODULE
JAN 2017
60V 40A DC MOTOR SPEED CON. CONTROL BOARD
JAN 2017
60V 40A DC MOTOR SPEED CON. MOSFET BOARD
JAN 2017
GPS SYNCHRONISED ANALOG CLOCK
FEB 2017
ULTRA LOW VOLTAGE LED FLASHER
FEB 2017
POOL LAP COUNTER
MAR 2017
STATIONMASTER TRAIN CONTROLLER
MAR 2017
EFUSE
APR 2017
SPRING REVERB
APR 2017
6GHz+ 1000:1 PRESCALER
MAY 2017
MICROBRIDGE
MAY 2017
MICROMITE LCD BACKPACK V2
MAY 2017
10-OCTAVE STEREO GRAPHIC EQUALISER PCB
JUN 2017
10-OCTAVE STEREO GRAPHIC EQUALISER FRONT PANEL JUN 2017
10-OCTAVE STEREO GRAPHIC EQUALISER CASE PIECES
JUN 2017
RAPIDBRAKE
JUL 2017
DELUXE EFUSE
AUG 2017
DELUXE EFUSE UB1 LID
AUG 2017
MAINS SUPPLY FOR BATTERY VALVES (INC. PANELS)
AUG 2017
3-WAY ADJUSTABLE ACTIVE CROSSOVER
SEPT 2017
3-WAY ADJUSTABLE ACTIVE CROSSOVER PANELS
SEPT 2017
3-WAY ADJUSTABLE ACTIVE CROSSOVER CASE PIECES SEPT 2017
6GHz+ TOUCHSCREEN FREQUENCY COUNTER
OCT 2017
KELVIN THE CRICKET
OCT 2017
6GHz+ FREQUENCY COUNTER CASE PIECES (SET)
DEC 2017
SUPER-7 SUPERHET AM RADIO PCB
DEC 2017
SUPER-7 SUPERHET AM RADIO CASE PIECES
DEC 2017
THEREMIN
JAN 2018
PROPORTIONAL FAN SPEED CONTROLLER
JAN 2018
WATER TANK LEVEL METER (INCLUDING HEADERS)
FEB 2018
10-LED BARAGRAPH
FEB 2018
10-LED BARAGRAPH SIGNAL PROCESSING
FEB 2018
TRIAC-BASED MAINS MOTOR SPEED CONTROLLER
MAR 2018
VINTAGE TV A/V MODULATOR
MAR 2018
AM RADIO TRANSMITTER
MAR 2018
HEATER CONTROLLER
APR 2018
DELUXE FREQUENCY SWITCH
MAY 2018
USB PORT PROTECTOR
MAY 2018
2 x 12V BATTERY BALANCER
MAY 2018
PCB CODE:
01107151
1510815
18107152
01205141
01109111
07108151
03109151/2
01110151
19110151
19111151
04101161
04101162
01101161
01101162
05102161
16101161
07102121
07102122
11111151
05102161
04103161
03104161
04116011/2
04104161
24104161
01104161
03106161
03105161
10107161
04105161
04116061
07108161
10108161/2
07109161
05109161
25110161
16109161
16109162
11111161
01111161
07110161
05111161
04110161
01108161
11112161
11112162
04202171
16110161
19102171
09103171/2
04102171
01104171
04112162
24104171
07104171
01105171
01105172
SC4281
05105171
18106171
SC4316
18108171-4
01108171
01108172/3
SC4403
04110171
08109171
SC4444
06111171
SC4464
23112171
05111171
21110171
04101181
04101182
10102181
02104181
06101181
10104181
05104181
07105181
14106181
Price:
$15.00
$15.00
$2.50
$20.00
$15.00
$7.50
$15.00
$10.00
$15.00
$15.00
$5.00
$10.00
$15.00
$20.00
$15.00
$15.00
$7.50
$7.50
$6.00
$15.00
$5.00
$5.00
$15.00
$15.00
$5.00
$15.00
$5.00
$5.00
$10.00
$10.00
$15.00
$5.00
$10.00/pair
$20.00
$10.00
$5.00
$5.00
$2.50
$10.00
$5.00
$7.50
$10.00
$12.50
$10.00
$10.00
$12.50
$10.00
$2.50
$15.00
$15.00/set
$7.50
$12.50
$7.50
$2.50
$7.50
$12.50
$15.00
$15.00
$10.00
$15.00
$5.00
$25.00
$20.00
$20.00/pair
$10.00
$10.00
$10.00
$15.00
$25.00
$25.00
$12.50
$2.50
$7.50
$7.50
$5.00
$10.00
$7.50
$7.50
$10.00
$7.50
$2.50
$2.50
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Programmable Ignition
System with a V12
I have a collection of interesting
cars, bikes and engines and have a
habit of putting what I consider to be
better engines into some of my cars.
My Audi-engine Porsche 924 was
not very brisk so some years ago I replaced it with a two-litre, six-cylinder
supercharged Toyota motor.
Although I converted it to LPG and
distributor ignition, it is very smooth
and lively and the 924 didn't have
computers to complicate things.
Three years ago, I bought a 1986 Porsche 928 in reasonable order for $6000.
It has a 5-litre V8 that is jammed into
the engine bay and has subsequently
started leaking oil and is very difficult
to service. So I replaced its engine with
a V12 from a Toyota Century. It is very
clean and compact and fitted in easily once I simplified the bulky intake
manifolds.
Like the 924, I now have the V12
running mechanically with a Jaguar V12 distributor from the exhaust
camshaft and an LPG fuel system. But
none of the 928's complicated wiring,
instruments or computer operate properly, making it undrivable.
Because the 928 injectors are batch
fired, I hope to be able to extend the
wiring to four more, put its cog sensor
ring on the V12 flywheel, use its other
sensors and air flow meter through the
existing computer to do the basic management on the V12 and just design a
separate ignition computer.
The Century V12 uses coil-on-plug
wasted spark ignition, with three coils
on the front of both banks (60° apart),
so a six-cylinder coil-on-plug driver
system, as used in the Ford Falcon,
might work.
I have a Jaycar kit (KC5442) based on
the 2007 Programmable Ignition System by John Clarke (siliconchip.com.
au/Series/56) that I was going to use
on the 924. Could I add a low-tension,
timed feed to the six wasted spark coils
and add an appropriate advance to the
existing ignition kit?
96
Silicon Chip
Both banks have the usual 1-5-3-6-24 firing order. The 928 computer may
need to be tricked into thinking that
it is firing eight cylinders.
I have not altered any of the existing wiring or mechanical systems in
the 928 in case I have to put the V8
back at some stage, hence my attempt
to adapt the new engine to the existing systems. (I. I., via email)
• The Programmable Ignition System
would work with the V12 in a wasted
spark system that is essentially a 6-cylinder firing sequence as far as the ignition system is concerned. It would
fire two spark plugs simultaneously,
one of which is on a cylinder to be
fired and the other on a cylinder that
has opposite phase, ie, between the
exhaust and intake stroke.
You would need a trigger (Reluctor,
Hall Effect or similar) that runs from
the distributor and presumably this is
already in place. I am not sure if the
Porsche 928 computer would co-operate with this system. Presumably,
since you are planning on using the
original V8 cog sensor from the 928,
it should be none the wiser that you
are running a V12.
WiFi Water Tank Level
Meter for remote tanks
Can you estimate how much data the
WiFi Water Tank Level Meter (February 2018; siliconchip.com.au/Article/
10963) would use when transmitting
the data via WiFi, at the default timing settings?
Many farms will not have access to
WiFi due to the distances. The only
solution would be a cheap prepaid
3G/4G modem/WiFi-Router. $10/
month will buy 1.5GB.
In my case, the tank is 600 metres
away and would be line-of-sight but
for a heavily wooded area. In the past,
I have tried external directional antennas and high powered WiFi repeaters
but the signal at the tank is always
unusable.
The same kit but using 433MHz or
one of the CB data channels would
Celebrating 30 Years
be a winner for farmers. However, I
do not have the technical expertise to
modify the kit and would lose the data
in the cloud facility. (N. McM., Yass
River, NSW)
• The data transmitted for a single update should be under 1KB. One update
every 10 minutes means 144 updates
per day or around 4,500 per month.
So around 4.5MB per month. Clearly,
1.5GB is more than enough.
We may look at doing a 4G version
of the project at some point in the future but as you have suggested, it’s
probably easier to power a "personal
hotspot" from the same 5V supply as
the main unit.
They don't draw a lot of current as
they often have an internal, rechargeable lithium-ion battery which lasts
for many hours of use and they automatically go into a low-power mode
when there is no traffic.
Cost and output power
of AM Transmitter
I am interested in building the AM
Radio Transmitter project from the
March 2018 issue (siliconchip.com.
au/Article/11004). Can you please tell
me the approximate cost of the parts
and the output power I can expect. (S.
C., via email)
• Assuming you purchase the PCB
and main IC from us and the remainder
of the parts from Jaycar, the total will
cost around $45 without the optional USB output. While there is 700mV
RMS across L1, it is so inefficient and
the wire antenna is so much shorter
than ¼ of a wavelength (which would
be 75m) that the radiated power is only
a few microwatts.
Running Water Tank
Level Meter from mains
I am interested in building the WiFi
Water Tank Level Meter project which
was published in the February 2018
issue (siliconchip.com.au/Article/
10963).
As we have mains power at our
siliconchip.com.au
How does the Full-Wave Motor Speed Controller's mains supply work?
I can't make sense of the 5V
power supply circuit in the FullWave 10A Motor Speed Controller
(March 2018; siliconchip.com.au/
Article/10998).
There seems to be no return path
for that portion of mains energy being dumped through D1 on one cycle
and then through D2 on the reverse
mains polarity.
Are the two GNDs connected or
should the 5V ground be connected
to Active or am I missing something?
(D. McI., Eastwood, NSW)
• The 5.1V rail is connected to
mains Active via the 47W resistor
and the wire passing through the
centre of T1. So the 5.1V rail "floats"
at mains Active potential with GND
being 5.1V below this.
Supply current is coupled from
the Neutral conductor, through the
470nF X2 capacitor and series 1kW
tanks, is it possible to power it from
a 5V power supply and do away with
the charger/solar cells/power saving
circuitry or would this involve changing the software? (B. S., Dunedin, New
Zealand)
• Yes, you certainly can run it from
a USB charger fed into the micro USB
socket on the ESP8266 board. This is
mentioned in passing as a possibility
in the article.
We set up the prototype in the same
manner, without the Elecrow charger
board, and it worked fine. We ended
up putting the mains USB charger in
a separate IP65 enclosure and used
silicone to seal the holes in the box
for the mains input cable and USB
output cable.
Resistor burned out
due to short circuit
In December 2015, EPE Magazine
re-published the High-Energy MultiSpark Capacitor Discharge Ignition
design by John Clarke (originally published in Silicon Chip in December
2014 and January 2015; siliconchip.
com.au/Series/279). I have just finished building it.
I powered it up using a 12V DC
bench supply but as soon as I did so,
the 10W ¼W resistor in series with
16V 1W zener diode ZD1 burned out.
siliconchip.com.au
resistor and then through either D1
or D2 into the 5V supply.
We covered the operation of this
type of supply in detail in an article about SPICE simulations in the
June 2017 issue, starting on page 38
(siliconchip.com.au/Article/10677).
In brief, we can consider what
happens when the Neutral voltage is
above the Active voltage and is rising,
which will be the case during roughly
one-quarter of the mains 50Hz cycle.
In this case, current will flow
from Neutral into the 470nF capacitor, charging it up but also coupling
some current through the 1kW series
resistor, diode D1 and the 47W resistor, back to Active.
During this time, assuming the
470µF supply filter capacitor was
charged up to 12V initially, it will
be discharging as there is no source
of current to replenish it
I looked at the schematic again. When
the rail voltage isn't near 16V DC, that
zener will remain off.
Won't this result in the 10W resistor frying? Obviously, the resistor and
zener values are wrong. (J. J., South
Africa)
• When the supply voltage is below
16V and ZD1 does not conduct, this
should not damage the 10W resistor
as very little current will be flowing
through it. We had no such problems
on our prototype.
If this resistor burns out with a 12V
DC supply, that strongly suggests that
either ZD1 has been fitted backwards
or there is a short circuit across either IC1, IC2 or one of their bypass
capacitors.
Check for correctly oriented components and that you have no accidental
solder bridges. You may have to isolate
sections of the circuit to find where the
short circuit is located.
Question about zero
ohm resistors
I am interested in the Earthquake
Early Warning Alarm project featured
in the March 2018 issue (siliconchip.
com.au/Article/10994).
However, I live on a reasonably busy
road with speed humps not far from
the house and heavy trucks can make
Celebrating 30 Years
But when the Neutral voltage
starts to fall (still being above active, but reducing), the 470nF capacitor will discharge via the 1kW
series resistor and diode D2 into
circuit ground.
In doing so, it charges the 470µF
supply filter capacitor back up to
12V, with current flowing via the
47W resistor back to Active. This
"returns" much of the energy drawn
earlier back to the mains, leaving just
the desired 12V across ZD1.
This same current flow will continue as Neutral becomes negative
compared to Active, except now
the 470nF X2 capacitor is charging
up in the opposite direction. In the
final mains quadrant, the 470nF capacitor discharges again while the
470µF filter capacitor also discharges, albeit more slowly. Then the process repeats.
quite a rattle when they bounce over
them (particularly if they are speeding, which unfortunately often happens).
However, I assume that I should
be able to circumvent this by adjusting VR1, as suggested at the end of
the article.
There is one thing that puzzles me,
though: what's the story with the zero
ohm resistors? Until I read the article,
I was not aware that such a component
even existed! Why did you use these
in the prototype when two bits of wire
would do, as you suggest?
One final query, surely that photo on
the cover and at the start of the article is a still from a movie? Surely that
is not genuine?! Scary, if it is! (G. G.,
Figtree, NSW)
• Zero ohm resistors are (or at least
were) commonly used where wire
links are required since they can easily
be bent to standard lengths, can be
inserted by automated equipment
designed for handling resistors and
provide some insulation.
For example, this allows you to have
wire links passing under the zero ohm
resistors without them shorting.
There are also surface-mount zero
ohm resistors and these can be handy
to allow signals to jump over tracks on a
two-layer board when there are already
tracks in the way on the other layer.
May 2018 97
Also, purchased in sufficient quantities, zero ohm resistors work out
cheaper than tinned copper wire.
We've seen them supplied in kits
where wire links are required.
In this case, we needed links about
the same length as a resistor so using
zero ohm resistors was the simplest
approach.
Stationmasters not
working properly
I had two Stationmaster train controllers built for me by someone who
advertises in your magazine.
Both are exhibiting the same strange
symptoms. With a 15V DC supply, I
measured a triangular waveform at pin
7 of IC1 but it was only about 880Hz,
not 8kHz as stated in the article. The
amplitude was about 840mV.
I also measured a square wave at
pin 1 of IC1 of about 900Hz, with an
amplitude just under 3V. The voltage
at the Vcc test point was 5V and 2.5V
at the Vcc ÷ 2 test point.
I am able to adjust VR1 to get the
LEDs to switch off and on (as per the
instructions).
I can also measure a triangle wave
on pins 9 and 11 of IC1 but nothing on
pins 10 and 13, as shown in the dia-
gram on page 37 of the article. The output waveforms on the TRACK terminals look like PWM but only at about
5V peak-to-peak.
Strangely, as I rotate the speed control clockwise, while the output pulse
width increases, the whole waveform
shifts down the Y-axis. At maximum
speed (forward or reverse), the waveform disappears completely.
I contacted the person who assembled the two kits for me and his response was to contact you! Can you
help me? (P. S., Banyo, Qld)
• The frequency may be incorrect if
the resistors connecting to IC1a and
IC1b are incorrect or the 10nF capacitor is actually 100nF. Check the
resistors, especially the 1kW resistor
between pins 7 and 3 and the 10kW
resistor between pins 1 and 6.
The waveforms at pins 10 and 13
of IC1c/IC1d should not be triangular but rather a DC level, as shown in
blue in Fig.4. The caption of Fig.4 is
incorrect. It should be referring to the
yellow and red traces as the IC1 pin 9
and pin 12 signals.
If you don't have the full voltage
swing at the track, IC3 may not be
receiving the required voltage at pin
5. That voltage will depend on the
supply applied to CON1. Check also
Fitting a modern mains cord to a vintage radio
I am currently restoring a vintage
Kreisler 1954 Duplex radio. It’s an
11-51 5-valve console radiogram.
I’ve hit a snag regarding the mains
power cable.
By today’s electrical standards
it’s highly illegal and potentially
dangerous.
I’d like to replace the cable with
a legal, safer one but I have no way
to do it safely. The Active wire is
soldered to two tags on the on/off
pot and the Neutral soldered to another tag. There is no Earth connection. How can I get around this? (R.
B., Nowra, NSW)
• Without a view of the chassis,
it is not possible to make a specific
suggestion. However, in most cases,
it is possible to fit a 3-core flex with
a 3-pin plug.
You can always find a point to
attach a solder or crimp lug for the
chassis to Earth and while it would
be better to have an insulated termi98
Silicon Chip
nal block for the Active and Neutral
connections, if they are sleeved, that
will improve safety.
The 2-core flex or cotton-covered
3-core cord in all old sets should be
replaced as a matter of course. They
are usually perished, frayed or both.
And throw out the old mains plug –
it is usually hazardous.
There are several ways to securely
anchor the cord inside the chassis.
You could have it enter via a hole
(fitted with a rubber grommet) in the
rear of chassis and then fit a separate
cord clamp.
Alternatively, you could take the
modern approach and fit a cord-grip
gland that's super glued tight as we
do in many of our mains operated
projects these days.
We know that most restorers don't
bother but you never know when a
poorly anchored power cord may
create a serious hazard to you or
someone in your family.
Celebrating 30 Years
that pins 7 and 1 are connected to
ground.
Also, make sure your oscilloscope
is DC coupled and correctly grounded.
Where to get acoustic
filling for speakers
Can you tell me where you got the
acoustic BAF filling for the Majestic
speakers? It's hard to find any kind
of acoustic filling, but especially the
bonded acetate fibre kind. (P. T., Casula, NSW)
• This wadding is known by several names: innerbond, acoustic filling,
BAF (bonded acetate fibre) etc. Jaycar
have it, their catalog code is AX3694.
Using a three-terminal
coil for Jacob's Ladder
I have a three-terminal ignition coil
(rather than the VS Commodore one
specified, which has two terminals).
Can this be used for the project (February 2013; siliconchip.com.au/Article/
2369) and if so, how do I wire it up?
(P. M., Alfredton, Vic)
• As far as we are aware, three-terminal ignition coils include an IGBT to
switch current to the primary winding.
So there is a +12V terminal for the coil
primary and the other end of the coil is
switched to ground via the IGBT. The
second terminal is the ground/chassis
terminal and the third terminal is the
IGBT gate connection.
For the Jacob's Ladder project, you
could bypass the IGBT driver that's in
the coil assembly and connect directly
to the coil. Alternatively, remove the
driver IGBT from the Jacob's Ladder
PCB and connect the gate drive to the
IGBT gate connection of the coil.
Induction Motor Speed
Controller at 60Hz
I wonder if it is possible to change
the 1.5kW Induction Motor Speed
Controller from the April and May
2012 issues (siliconchip.com.au/
Series/25) to operate from 0 to 60Hz.
(B. F. S., Sao Paolo, Brazil)
• If you set the over-speed (O/S) DIP
switch on, the range is 0-75Hz. You
could limit it to 0-60Hz by inserting
a resistor between the +3.3V rail and
the speed pot.
For a 10kW pot, use 2.4kW. Or use
a second potentiometer wired as a
rheostat (variable resistor) and adjust
siliconchip.com.au
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Double precision floating point maths for the Micromite
Is there any thought to have a version of MMBasic that supports 64bit floating point maths, ie, double
precision?
This would allow the Micromite
Plus to be more easily used for astronomical projects. (G. L., Wynn
Vale, NSW)
• Geoff Graham replies: As it
happens, I have been experimenting with double precision floating
it until you get 60Hz output with the
speed pot at maximum.
Dual transducer AntiFouling fuse blown
We purchased your excellent kits for
anti-fouling our NOELEX 30 yacht using two transducers (New Marine Ultrasonic Anti-Fouling Unit, May-June
2017; siliconchip.com.au/Series/312).
They were assembled and installed,
then switched on December 3rd, 2017.
They have operated continuously, except for the odd time when they were
inadvertently switched off by mistake, usually for only a few minutes
each time.
The performance was good and fully up to the standard expected in your
articles in the Silicon Chip magazine
sent with the electronic kits. We are
very pleased with the unit and with
your whole professional sales process.
However, yesterday we discovered
the 3A fuse had blown. I replaced this
fuse but now I find it does not power
up as usually expected.
Now, when switched on, the power
light comes on as before, but then goes
off and the only light working is the
fault light which blinks roughly every
two seconds.
I tried switching off, disconnecting
the two transducers then switching on
again, but we found this made no difference. What else could be at fault?
What faults activate the fault light?
Your help will be appreciated. (C. B.,
Christchurch, NZ)
• A blown fuse probably means a
shorted Mosfet or shorted turn in a
transformer or a short in the ultrasonic
transducer wiring.
For each Mosfet, check for a dead
short between the drain and source of
Q1, Q2, Q3 or Q4. Depending on your
100
Silicon Chip
point on the Micromite Plus and if
you would like to try it out you can
download it from: http://geoffg.net/
Downloads/Micromite/Micromite_
V5.04.09_Beta.zip
This beta also includes other
changes introduced in previous
betas.
For example, it includes the fix
for image corruption of 5-inch displays, the ability to use display drivmultimeter, you may need to desolder
each Mosfet to get a sensible reading.
A Mosfet will read high ohms (megohms) if it is OK or near to zero ohms
if shorted. In each case, before making the measurement, short the gate
to the source to ensure the Mosfet is
not switched on.
It’s also best to swap the multimeter
leads and check each Mosfet in both
polarities to ensure that the body diode is not affecting the reading. If the
Mosfet is shorted, the resistance reading will be low with both polarities.
The resistance of the wiring to the
transducer (when disconnected from
the Anti-Fouling unit) should be very
high after its capacitance charges via
the multimeter. If the Mosfets and
transducer wiring are OK, the transformer is the remaining suspect.
Questions on safe
mains wiring
I have a few questions related to
mains wiring for projects. I notice that
the Currawong amplifier wiring shown
on pages 93 & 94 of the December 2014
issue (and page 47 of the October 2016
issue) has a piece of heatshrink on both
ends of the active wire from the IEC
socket fuse to the power switch and
is referred to as "heatshrink-covered
wire to Active".
Other Silicon Chip amplifier and
mains-powered projects I have looked
at do not appear to have that exact requirement. Can you please tell me the
purpose of the heatshrink tubing? Can
I solder the mains Earth to an uninsulated ring lug rather than crimping to
an insulated ring lug?
I'm using an IEC power connector from Jaycar with mains connection, fuse and a double pole switch.
In view of my initial question about
Celebrating 30 Years
ers written in BASIC, static variables, etc.
My plan for future beta versions is
to keep adding small improvements
(incrementing the beta number) and
keep the beta open for some months
until it has accumulated enough
changes and is stable enough to warrant a full release. If you find any
bugs in this new version of the firmware, please let me know.
heatshrink, does the short active wire
required from the fuse terminal to the
switch need the heatshrink on each
end and is soldering acceptable rather
than crimp terminals?
All connections will be insulated
with heatshrink, cable-tied to minimise movement and covered with a
heatshrink hood as detailed in the Currawong project. (M. N., North Rocks,
NSW)
• The reason behind covering the IEC
connector with large diameter heatshrink is to prevent any accidental
contact of wires from the right speaker terminals to mains connections,
should they come adrift. The Active
and Neutral wires and the metal strip
connecting the fuse to Active on the
back of the IEC connector are covered.
You could also use a moulded rubber cover (Jaycar PM-4016) instead of
the heatshrink tubing. We don't always
use this full enclosure method of protection as it depends on whether low
voltage wiring is close by.
The rear of an IEC fused connector
does have exposed metal where the
fuse connects to the Active terminal
(and we recommend covering this with
silicone sealant) and insulated crimp
connectors still have a small amount
of bare metal exposed on the IEC connector terminals between where the insulation on the crimp connector ends
before meeting the IEC housing.
While fingers might not make easy
contact with the very small gap of exposed bare metal, a loose wire can.
Yes, you can use uninsulated lugs
for the mains Earth connections and
you can solder rather than crimp them.
This is because accidental contact with
Earth is safe.
Any Neutral or Active wire terminal
connection that is exposed should be
covered with insulation such as heatsiliconchip.com.au
shrink tubing to prevent direct accidental contact with mains voltages.
That includes wiring on the mains
switch and the spare terminal(s) of a
double throw switch.
Soldering is acceptable rather than
crimping so long as the wires are cable
tied together (which is required anyway). It is important when soldering
to the IEC connector to check that the
terminals are correctly soldered with
sufficient heat and flux to ensure the
joints fully adhere to the terminals and
do not form dry joints.
Programming Arduino
projects with a Mac
I’m very interested in the WiFi Water
Tank Level Meter in the February 2018
issue (siliconchip.com.au/Article/
10963). Being dependent on a large
concrete tank for our farm household
water I need such a device.
Currently, I bribe grandchildren to
do this but as they become older, the
idea of climbing up on a 3.6m high
concrete tank appeals less despite generous bribes.
During the course of the article,
many mentions are made of using a
PC to program and upload data to the
Arduino-based unit. My question is,
will an Apple MacBook do this task?
The article seems to read as though it’s
a Windows-based program. My confusion is that often PC is used to denote
a Windows-based personal computer
or laptop. (D. C., Cambooya, Qld)
• The Arduino IDE is available for
Windows, Mac OS X 10.7 or newer
and Linux. See: www.arduino.cc/en/
Main/Software So if your MacBook
runs Mac OS X 10.7 or newer (or it
can be upgraded) then you should be
able to follow the procedures set out
in the magazine.
Older versions of the Arduino IDE
(10.6) will work on older versions of
Mac OS X (eg, 10.6.8 and before).
Note though that we are not sure
whether the sensors used are safe to
place in drinking water tanks.
Control DC motor speed
with AC motor current
I have made an automatic saw which
is mounted on slides and driven by a
speed adjustable geared DC motor. The
speed is altered by a variable voltage
supply so the saw motor is not overloaded by the forward travel into the
siliconchip.com.au
work. The saw motor is a universal
type.
I want to know how to link the forward travel speed to the load being
encountered by the saw motor for a
new saw. The load will vary during
the cut operation.
I am planning to control the DC
motor speed using either Jaycar kit
KC5502 (20A 12/24V DC Motor
Speed Controller Mk.2, June 2011;
siliconchip.com.au/Article/1035) or
KC5225 (High-Current Speed Controller For 12V/24V Motors, June 1997;
siliconchip.com.au/Article/4868). But
both of these motor speed controllers
are manually controlled.
The first stage will be the fast approach of the saw to the work, a second stage is a very slow approach as
the moving blade contacts the work
and then the automatic stage where the
current draw of the saw motor varies
the forward travel speed. It will have
to be reversible but I can do that with
a toggle switch.
The new saw motor I am planning
to use draws 9A at full load. I would
like to be able to set the automatic load
speed to maintain around 8-8.5A to get
the best forward cut speed without erratic loading of the cut motor.
Thank you for any help you can give.
(G. T., Londonderry, NSW)
• Take a look at the circuit of our Full
Wave, 230VAC Universal Motor Speed
Controller in the March 2018 issue. In
particular, observe the use of the current transformer, rectifier and filtering to measure the motor current of
the mains-powered motor. You could
copy that part of the circuit to measure your saw motor current.
The current transformer provides
mains isolation as the insulated mains
wire only passes through the centre
core of the transformer and the secondary winding of the transformer is
isolated.
The voltage obtained can be used
to provide the speed control for the
Jaycar kit KC5502 motor speed controller, where the speed potentiometer can be replaced with a DC control
voltage applied to where the wiper
would connect.
Note that you will need to provide
amplification, voltage inversion and
level shifting using an op amp to get
the required speed control against saw
motor current. The voltage inversion
is important since you want the DC
motor speed to reduce as the saw moCelebrating 30 Years
tor's current draw increases when it is
heavily loaded.
Motor Speed Controller
thermistor woes
I have purchased and built three
K6036 kits for the 10A/230V Universal Motor Speed Controller design
published in the February and March
2014 issues (siliconchip.com.au/
Series/195). I had no problems with
assembly and all three ran fine for a
short time.
I connected a 1600W vacuum cleaner to test. I can vary the speed easily
all the way down to stop. But after
running for about three minutes at
say 75% load, the speed pot (VR1) no
longer allows me to get full power.
If I run with the top off the box and
use a vacuum cleaner (with plastic
piping for safety) close to the NTC
thermistor, after about 15 seconds,
the speed increases to full speed or
near full speed. I can repeat this on
all the kits
I have emailed Altronics and they
were helpful and suggested contacting
you and one of your technical gurus
who designed this circuit.
What do you recommend? Should
the thermistor be removed? It is hot
to touch but technically the resistance
should drop. Am I misunderstanding
something?
I shorted out the NTC thermistor but
used a heat gun with heating turned off
to reduce the current demand. Once
running, I turned up the heat and increased load but the motor speed becomes erratic and it will not run at full
speed. So perhaps the thermistor was
just clouding the issue.
My plan is to control these kits from
a PC via an opto-isolation circuit, to
control 2000W vacuum cleaners. It
is to control boundary layers in my
10% scale wind tunnel. (J. B., Surrey
Hills, Vic)
• The heat gun is probably producing
interference that is making the controller run erratically.
We still suspect the NTC thermistors are at fault as they should drop
in resistance with more heat and not
restrict the maximum speed.
Your tests suggest that the thermistors are working the other way and this
may indicate that they are a Positive
Temperature Coefficient (PTC) type
and not the NTC type specified.
We suggest you check for any markMay 2018 101
ings on the thermistors and check
the kit notes to see if a part code is
supplied, in an attempt to determine
whether they are PTC or NTC.
Failing that, connect a DMM set to
measure resistance across one thermistor and heat it with a heat gun or
similar. If the resistance increases as
it gets hotter, you have been supplied
the wrong part.
Relay problem with
Arduino LC Meter
I have built the Arduino LC Meter
project (June 2017; siliconchip.com.
au/Article/10676) and have encountered two problems.
Firstly, the relay appears to have incorrect pin connections. The impulse
to the relay coil should go to pin 13,
not pin 2 as in the circuit diagram.
Wired up as per the article, the relay coil does not receive the calibration pulse required as the coil is not
energised. Pin 2 not being connected
to anything in the relay.
Secondly, the Arduino sketch, in
the comments, mentions that the serial interface with the new chip should
have the serial address revised in the
code, but the actual revised address is
not provided.
My inexperience may be the problem, but changing the address to 38
did not work. (W. S., Lake Cathie,
NSW)
• According to the data sheet of the
relay we specified in the parts list, pins
2 and 13 are internally joined. So the
circuit and wiring seem to be correct
as presented. Are you sure you have
the correct relay? It should be labelled
PRMA1A12 or TRR1A05D00.
Which serial interface address to
use was explained on pages 82 and 83
of the March 2017 issue, in the article
on the serial LCD module (siliconchip.
com.au/Article/10584).
If your module has the PCF8574AT
chip, it will probably be set up for an
address of 3F hex.
ers are a bit of a worry. I figure they’re
bound to end up getting pranged before too long. I was thinking of fitting
a grille to each woofer, Altronics Cat
C3715.
I was wondering if this would compromise the sound quality. Would you
recommend fitting something like that
or should I use a conventional speaker grille made from grille cloth on a
frame? (B. D., Ashburton, Vic)
• If you have pets or young children
in your home, protective grilles are
prudent insurance. They will have
no effect on the sound quality. Grille
cloth may look better but it offers less
protection and may rattle or buzz at
high bass levels.
Nicholas Vinen attached grilles to
his Majestics (see the photo below). He
bought them from eBay rather than using the Altronics grilles, only because
the photo on the Altronics website
makes them look rather "chunky" and
he preferred a finer mesh.
He attached them using the clips
supplied with the grilles but had to add
small springs and rubber pads (from
Bunnings) to space them off from the
face of the speaker, as the speaker surround sits about 10mm proud of the
front panel.
The supplied screws were long
enough to pass through and compress
the springs to hold the clips in place.
Fitting a grille to the
Majestic speakers
I am building a pair of Majestic
speakers and looking forward to getting them working soon. I noticed there
was an error with the specification of
the screws to attach the Celestion horn.
They should be M6 size, not 6BA.
Also, the exposed cones of the woof102
Silicon Chip
Celebrating 30 Years
You could also mount the clips at
45° angles rather than 90° as some
constructors may prefer the resulting
appearance.
Is lower amplifier
distortion noticeable?
I have an Electronics Australia Mosfet-based amp I built sometime around
1990. There is a Silicon Chip amplifier
design (March - May 2012; siliconchip.
com.au/Series/27) which appears to
have about 10 times less distortion.
I was wondering whether the reduction in distortion provided by the
newer design was actually audible.
Given the best speakers create distortion of about 0.5% THD, does the
elimination of a tiny fraction of a percent distortion from the power amplifier actually matter? Or are there other
factors involved apart from sinewave
distortion such as response to transients?
I would be interested to understand
more about this. I think other readers
would also be interested in this. By
the way, thanks for a great magazine.
(B. D., via email)
• The Ultra-LD Mk3 (described in
2012; siliconchip.com.au/Series/27)
and the Ultra-LD Mk4 (described in
2015; siliconchip.com.au/Series/289)
are superior to anything we described
in S ilicon C hip ten years before
and orders of magnitude better than
anything ever described in Electronics Australia or in any other magazine,
for that matter.
Also as Douglas Self points out,
Mosfet-based amplifiers are not capable of achieving the low levels of
distortion of a good bipolar transistor
based design.
Unless you have cloth ears, you will
certainly notice a big improvement
in sound quality when listening to
CDs. Do not bother making comparisons with MP3 recordings unless they
have the highest possible bit-rate and
even then they are not as good as the
best CDs.
While it might seem that the higher
distortion from loudspeakers would
mask the much lower distortion of
amplifiers, that is not the case.
The quality of distortion from loudspeakers tends to be quite different to
that from amplifiers. With that said,
your system will sound even better if you have low distortion loudspeakers.
SC
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WARNING!
SILICON CHIP magazine regularly describes projects which employ a mains power supply or produce high voltage. All such
projects should be considered dangerous or even lethal if not used safely.
Readers are warned that high voltage wiring should be carried out according to the instructions in the articles. When working
on these projects use extreme care to ensure that you do not accidentally come into contact with mains AC voltages or high
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advised not to attempt work on them. Silicon Chip Publications Pty Ltd disclaims any liability for damages should anyone be
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siliconchip.com.au
Celebrating 30 Years
May 2018 103
Coming up in Silicon Chip
Altium Designer 2018 review
We have been using Altium Designer to draw up circuits and design PCBs for
many years now. In that time, quite a few improvements have been made to
the software. We'll describe the new features and also point out some of the
pre-existing features that have been improved or are particularly useful.
Advertising Index
Altronics................................ FLYER
Dave Thompson......................... 103
Digi-Key Electronics....................... 3
Emona........................................ IBC
El Cheapo Modules – RF attenuators
Hare & Forbes.......................... OBC
Jim Rowe describes a programmable, 63-step, 4GHz RF digital step attenuator module with a range of applications.
Jaycar............................... IFC,49-56
Introduction to programming the Cyprus CY8CKIT
LD Electronics............................ 103
This low-cost module incorporates a 32-bit microcontroller and a set of
reprogrammable analog circuitry which can be used for a wide range of tasks.
Touchscreen GPS Frequency Reference
This new design is much more compact with many new features including
multiple programmable-frequency outputs, ultra low-drift operation, improved
status display and 5V operation.
The Latest Agricultural Technology
The rapid advancement of technology is having a huge effect on agriculture
and Australia is at the forefront. We take a look at some of the latest robots
and monitoring devices aimed at increasing crop yields and food quality and
reducing the environmental impact of farming.
LiFePO4-based Uninterruptable Power Supply
The second article in this series will have details of the control circuit and
shield PCB, and describe how to build the case and wire up the components.
Note: these features are planned or are in preparation and should appear
within the next few issues of Silicon Chip.
The June 2018 issue is due on sale in newsagents by Thursday, May 24th.
Expect postal delivery of subscription copies in Australia between May
23rd and June 8th.
Keith Rippon Kit Assembly......... 103
LEACH Co Ltd.............................. 27
LEDsales.................................... 103
Master Instruments.................... 103
Microchip Technology..................... 5
Ocean Controls.............................. 6
PCBcart........................................ 9
Sesame Electronics................... 103
Silicon Chip Shop............. 42,94-95
Silicon Chip Subscriptions.......... 99
Silicon Chip Wallchart................. 89
SC Radio, TV & Hobbies DVD...... 13
The Loudspeaker Kit.com............ 81
Tronixlabs................................... 103
Vintage Radio Repairs............... 103
Wagner Electronics........................ 7
WIA Radio & Electronics Conv..... 11
Notes & Errata
Majestic Speakers, June & September 2014: In the September issue, the two screws used to attach the tweeter to the
horn are listed as 6BA x 20mm when they should be M6 x 20mm. These same two screws are not mentioned in the parts
list in the June issue.
Battery-Pack Cell Balancer, March 2016: there is a risk of damage to IC1 and IC2 when batteries with many cells are initially plugged in. Two small (¼W) 10kW through-hole resistors can be added to solve this. Solder them between pin 2 and
pin 15 of both IC1 and IC2. These pins are adjacent but on opposite sides of the IC packages. The resistor bodies will need
to be kept close to the ICs to avoid interfering with the battery header (CON1). Alternatively, they can be soldered from pin
15 of IC3 to ground (pin 20), and the other from pin 16 of IC3 to ground.
WiFi Water Tank Level Meter, February 2018: the WeMos D1 R2 board we used in this project was actually a clone made
by Robotdyn; the original D1 R2 does not have a connection for an external antenna. The boards in our shop (Cat SC4414)
are the same as the board shown in the article.
6-Element VHF TV Yagi Antenna, February 2018: a photo caption on page 40 says that the dipole ends are made using
39mm lengths of aluminium tubing but they are closer to 30mm; refer to Fig.1 on page 39 which correctly shows the distance between the semicircular cut-outs at each end as 27mm.
AM Radio Transmitter, March 2018: the circuit diagram on page 67 (Fig.2) shows the 10nF antenna coupling capacitor
connected to the wrong end of antenna coil L1. Also, Mosfet Q3 has the wrong part number in the parts list. It should be
IPP80P03P4L04, as in the circuit and overlay diagrams.
The Clayton’s “GPS” Time Signal Generator, April 2018: the parts list gave an incorrect Jaycar part number for the D1
Mini ESP8266 module. It should be XC3802.
104
Silicon Chip
Celebrating 30 Years
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